U.S. patent number RE47,412 [Application Number 14/716,014] was granted by the patent office on 2019-05-28 for tuning matching circuits for transmitter and receiver bands as a function of the transmitter metrics.
This patent grant is currently assigned to BLACKBERRY LIMITED. The grantee listed for this patent is BlackBerry Limited. Invention is credited to Matthew Russell Greene.
![](/patent/grant/RE047412/USRE047412-20190528-D00000.png)
![](/patent/grant/RE047412/USRE047412-20190528-D00001.png)
![](/patent/grant/RE047412/USRE047412-20190528-D00002.png)
![](/patent/grant/RE047412/USRE047412-20190528-D00003.png)
![](/patent/grant/RE047412/USRE047412-20190528-D00004.png)
![](/patent/grant/RE047412/USRE047412-20190528-D00005.png)
![](/patent/grant/RE047412/USRE047412-20190528-D00006.png)
![](/patent/grant/RE047412/USRE047412-20190528-D00007.png)
![](/patent/grant/RE047412/USRE047412-20190528-D00008.png)
United States Patent |
RE47,412 |
Greene |
May 28, 2019 |
Tuning matching circuits for transmitter and receiver bands as a
function of the transmitter metrics
Abstract
A system can obtain an operational metric associated with the
transceiver, determine a target figure of merit based on a
compromise between a desired transmitter performance and a desired
receiver, determine a current figure of merit based on the
operational metric, and adjust the variable reactance component of
the impedance matching circuit based on a comparison of the current
figure of merit with the target figure of merit. Other embodiments
are disclosed.
Inventors: |
Greene; Matthew Russell
(Crystal Lake, IL) |
Applicant: |
Name |
City |
State |
Country |
Type |
BlackBerry Limited |
Waterloo |
N/A |
CA |
|
|
Assignee: |
BLACKBERRY LIMITED (Waterloo,
CA)
|
Family
ID: |
1000002625615 |
Appl.
No.: |
14/716,014 |
Filed: |
May 19, 2015 |
Related U.S. Patent Documents
|
|
|
|
|
|
|
Application
Number |
Filing Date |
Patent Number |
Issue Date |
|
|
13168529 |
Jun 24, 2011 |
8428523 |
|
|
|
11940309 |
Nov 14, 2007 |
7991363 |
|
|
|
13168529 |
Jun 14, 2011 |
8428523 |
|
|
Reissue of: |
13693388 |
Dec 4, 2012 |
8798555 |
Aug 5, 2014 |
|
|
Current U.S.
Class: |
1/1 |
Current CPC
Class: |
H04W
24/02 (20130101); H03H 7/40 (20130101); H04B
1/0458 (20130101); H04B 1/0458 (20130101); H03H
7/40 (20130101); H04W 24/02 (20130101) |
Current International
Class: |
H04B
1/40 (20150101); H03H 7/40 (20060101); H04W
24/02 (20090101); H04B 1/04 (20060101) |
Field of
Search: |
;455/77,522,73,125 |
References Cited
[Referenced By]
U.S. Patent Documents
Foreign Patent Documents
|
|
|
|
|
|
|
101640949 |
|
Feb 2010 |
|
CN |
|
201765685 |
|
Mar 2011 |
|
CN |
|
19614655 |
|
Oct 1997 |
|
DE |
|
102008050743 |
|
Apr 2010 |
|
DE |
|
102009018648 |
|
Oct 2010 |
|
DE |
|
EP0909024 |
|
Apr 1999 |
|
EM |
|
0685936 |
|
Jun 1995 |
|
EP |
|
0909024 |
|
Apr 1999 |
|
EP |
|
1079296 |
|
Feb 2001 |
|
EP |
|
1137192 |
|
Sep 2001 |
|
EP |
|
1298810 |
|
Apr 2006 |
|
EP |
|
2214085 |
|
Aug 2010 |
|
EP |
|
2328233 |
|
Jun 2011 |
|
EP |
|
2388925 |
|
Nov 2011 |
|
EP |
|
2424119 |
|
Feb 2012 |
|
EP |
|
2638640 |
|
Jul 2014 |
|
EP |
|
3131157 |
|
Feb 2017 |
|
EP |
|
03276901 |
|
Mar 1990 |
|
JP |
|
02-077580 |
|
Sep 1991 |
|
JP |
|
9321526 |
|
Dec 1997 |
|
JP |
|
10209722 |
|
Aug 1998 |
|
JP |
|
2000124066 |
|
Apr 2000 |
|
JP |
|
2005-130441 |
|
May 2005 |
|
JP |
|
100645526 |
|
Nov 2006 |
|
KR |
|
10-0740177 |
|
Jul 2007 |
|
KR |
|
01/71846 |
|
Sep 2001 |
|
WO |
|
2006/031170 |
|
Mar 2006 |
|
WO |
|
2008/030165 |
|
Mar 2008 |
|
WO |
|
2009/064968 |
|
May 2009 |
|
WO |
|
2009/108391 |
|
Sep 2009 |
|
WO |
|
2009/155966 |
|
Dec 2009 |
|
WO |
|
2010028521 |
|
Mar 2010 |
|
WO |
|
2010121914 |
|
Oct 2010 |
|
WO |
|
2011/044592 |
|
Apr 2011 |
|
WO |
|
2011/084716 |
|
Jul 2011 |
|
WO |
|
2011084716 |
|
Jul 2011 |
|
WO |
|
2011102143 |
|
Aug 2011 |
|
WO |
|
2011/133657 |
|
Oct 2011 |
|
WO |
|
2011028453 |
|
Oct 2011 |
|
WO |
|
2012/067622 |
|
May 2012 |
|
WO |
|
2012067622 |
|
May 2012 |
|
WO |
|
2012/085932 |
|
Jun 2012 |
|
WO |
|
2012085932 |
|
Jun 2012 |
|
WO |
|
2012112831 |
|
Aug 2012 |
|
WO |
|
Other References
Du Toit, "Tunable Microwave Devices With Auto-Adjusting Matching
Circuit", U.S. Appl. No. 13/302,649, filed Nov. 22, 2011. cited by
applicant .
Eiji, N., "High-Frequency Circuit and Its Manufacture", Patent
Abstracts of Japan, vol. 1998, No. 13, Nov. 30, 1998 & JP 10
209722 A (Seiko Epson Corp), Aug. 7, 1998. cited by applicant .
Hoirup, "Method and Apparatus for Radio Antenna Frequency Tuning",
U.S. Appl. No. 13/030,177, filed Feb. 18, 2011. cited by applicant
.
Huang, Libo et al., "Theoretical and experimental investigation of
adaptive antenna impedance matching for multiband mobile phone
applications", IEEE, Sep. 7, 2005, 13-17. cited by applicant .
Hyun, S. , "Effects of strain on the dielectric properties of
tunable dielectric SrTi03 thin films", Applied Physics Letters,
vol. 79, No. 2, Jul. 9, 2001. cited by applicant .
Katsuya, K. , "Hybrid Integrated Circuit Device", Patent Abstracts
of Japan, Publication No. 03-276901, Date of publication of
application: Sep. 12, 1991. cited by applicant .
Patent Cooperation Treaty, "International Search Report and Written
Opinion", Nov. 16, 2011, International Application No.
PCT/US/2011/038543. cited by applicant .
Payandehjoo, Kasra et al., "Investigation of Parasitic Elements for
Coupling Reduction in MultiAntenna Hand-Set Devices", Published
online Jan. 22, 2013 in Wiley Online Library
(wileyonlinelibrary.com). cited by applicant .
Pervez, N.K. , "High Tunability barium strontium titanate thin
films for RF circuit applications", Applied Physics Letters, vol.
85, No. 19, Nov. 8, 2004. cited by applicant .
Petit, Laurent , "MEMS-Switched Parasitic-Antenna Array for
Radiation Pattern Diversity", IEEE Transactions on Antennas and
Propagation, vol. 54, No. 9, Sep. 2009, 2624-2631. cited by
applicant .
Qiao, et al., "Antenna Impedance Mismatch Measurement and
Correction for Adaptive COMA Transceivers", IEEE, Jan. 2005. cited
by applicant .
Qiao, et al., "Measurement of Antenna Load Impedance for Power
Amplifiers", The Department of Electrical and Computer Engineering,
University of California, San Diego, Sep. 13, 2004. cited by
applicant .
Stemmer, Susanne , "Low-loss tunable capacitors fabricated directly
on gold bottom electrodes", Applied Physics Letters 88, 112905,
Mar. 15, 2006. cited by applicant .
Taylor, T.R. , "Impact of thermal strain on the dielectric constant
of sputtered barium strontium titanate thin films", Applied Physics
Letters, vol. 80, No. 11, Mar. 18, 2002. cited by applicant .
Xu, Hongtao , "Tunable Microwave Integrated Circuits using BST Thin
Film Capacitors with Device", Integrated Ferroelectrics, Department
of Electrical Engineering and Computer Engineering, University of
California, 2005, Apr. 2005. cited by applicant .
Zuo, S. , "Eigenmode Decoupling for Mimo Loop-Antenna Based on 180
Coupler", Progress in Electromagnetics Research Letters, vol. 26,
Aug. 2011, 11-20. cited by applicant .
Canadian Office Action, Application No. 2,821,173, Oct. 17, 2016.
cited by applicant .
"European Search Report", 16151299.1 search report, 2016. cited by
applicant .
"Extended European Search Report", EP Application No. 16155235.1,
May 3, 2016. cited by applicant .
"Search Report", ROC (Taiwan) Patent Application No. 101117467,
English Translation, Apr. 12, 2016, 1 page. cited by applicant
.
Canadian IPO, "Office Action mailed Mar. 10, 2017", Mar. 10, 2017,
1-3. cited by applicant .
EPO, "Extended European Search Report, EP16188956.3,", Jan. 9,
2017, 1-9. cited by applicant .
Extended European Search Report for 12749235.3 dated Jun. 8, 2017.
cited by applicant .
Communication pursuant to Article 94(3) EPC issued by the European
Patent Office, dated Nov. 16, 2017, European Patent Application
12177197.6. cited by applicant .
Communication pursuant to Article 94(3) EPC, Application No.
10822849.5, dated Oct. 11, 2017, 5 pages. cited by applicant .
Communication pursuant to Article 94(3) EPC, EPO application No.
16151299.1, dated Jun. 22, 2018. cited by applicant .
Office Action dated Nov. 7, 2018, Canadian Patent Application
2,826,573, 4 pages. cited by applicant .
India, Patent O., "Examination Report", for Application No.
9844/DELNP/2013, dated Apr. 25, 2018, 5 pages. cited by applicant
.
Intellectual Property India, "First Examination Report", for
Application No. 3160/CHE/2013 dated Jun. 5, 2018, dated Jun. 5,
2018, 5 pages. cited by applicant .
Bezooijen, A. et al., "A GSM/EDGE/WCDMA Adaptive Series-LC Matching
Network Using RF-MEMS Switches", IEEE Journal of Solid-State
Circuits, vol. 43, No. 10, Oct. 2008, 2259-2268. cited by applicant
.
Du Toit, , "Tunable Microwave Devices With Auto Adjusting Matching
Circuit", U.S. Appl. No. 13/302,617, filed Nov. 22, 2011. cited by
applicant .
Du Toit, , "Tunable Microwave Devices With Auto-Adjusting Matching
Circuit", U.S. Appl. No. 13/302,659, filed Nov. 22, 2011. cited by
applicant .
Greene, , "Method and Apparatus for Tuning a Communication Device",
U.S. Appl. No. 13/108,463, filed May 16, 2011. cited by applicant
.
Greene, , "Method and Apparatus for Tuning a Communication Device",
U.S. Appl. No. 13/108,589, filed May 16, 2011. cited by applicant
.
Hyun, S. , "Effects of strain on the dielectric properties of
tunable dielectric SrTi03 thin films", Applied Physics Letters,
2004 American Institute of Physics. cited by applicant .
Ida, I. et al., "An Adaptive Impedence Matching System and Its
Application to Mobile Antennas", TENCON 2004, IEEE Region 10
Conference, See Abstract ad p. 544, Nov. 21-24, 2004, 543-547.
cited by applicant .
Manssen, , "Method and Apparatus for Managing Interference in a
Communication Device", U.S. Appl. No. 61/326,206, filed Apr. 20,
2010. cited by applicant .
Manssen, , "Method and Apparatus for Tuning Antennas in a
Communication Device", U.S. Appl. No. 12/941,972, filed Nov. 8,
2010. cited by applicant .
Manssen, , "Method and Apparatus for Tuning Antennas in a
Communication Device", U.S. Appl. No. 13/005,122, filed Jan. 12,
2011. cited by applicant .
McKinzie, , "Adaptive Impedance Matching Module (AIMM) Control
Architectures", U.S. Appl. No. 13/293,544, filed Nov. 10, 2011.
cited by applicant .
McKinzie, , "Adaptive Impedance Matching Module (AIMM) Control
Architectures", U.S. Appl. No. 13/293,550, filed Nov. 10, 2011.
cited by applicant .
McKinzie, , "Method and Apparatus for Adaptive Impedance Matching",
U.S. Appl. No. 13/217,748, filed Aug. 25, 2011. cited by applicant
.
Mendolia, "Method and Apparatus for Tuning a Communication Device",
U.S. Appl. No. 13/035,417, filed Feb. 25, 2011. cited by applicant
.
Paratek Microwave, Inc., , "Method and Appartus for Tuning Antennas
in a Communication Device", International Application No.
PCT/US11/59620, filed Nov. 7, 2011. cited by applicant .
Patent Cooperation Treaty, , "International Search Report and
Written Opinion", International Application No. PCT/US2010/046241,
Mar. 2, 2011. cited by applicant .
Patent Cooperation Treaty, , "International Search Report and
Written Opinion", International Application No. PCT/US2010/056413,
Jul. 27, 2011. cited by applicant .
Patent Cooperation Treaty, , "International Search Report and
Written Opinion", PCT Application No. PCT/US08/005085, Jul. 2,
2008. cited by applicant .
Spears, , "Methods for Tuning an Adaptive Impedance Matching
Network With a Look-Up Table", U.S. Appl. No. 13/297,951, filed
Nov. 16, 2011. cited by applicant .
Tombak, Ali , "Tunable Barium Strontium Titanate Thin Film
Capacitors for RF and Microwave Applications", IEEE Microwave and
Wireles Components Letters, vol. 12, Jan. 2002. cited by
applicant.
|
Primary Examiner: Nguyen; Minh Dieu
Attorney, Agent or Firm: Guntin & Gust, PLC Trementozzi;
Ralph
Parent Case Text
CROSS-REFERENCE TO RELATED APPLICATIONS
.Iadd.Notice: More than one reissue application has been filed for
the reissue of U.S. Pat. No. 8,798,555. The Reissue applications
are this application, application Ser. No. 14/716,014, and
application Ser. No. 16/372,838, filed on Apr. 2,
2019..Iaddend.
This application is .Iadd.a reissue application of U.S. Pat. No.
8,798,555 issued Aug. 5, 2014 from U.S. patent application Ser. No.
13/693,388 filed Dec. 4, 2012, which is .Iaddend.a continuation of
.[.co-pending of.]. U.S. patent application Ser. No. 13/168,529
filed on Jun. 24, 2011.Iadd., now U.S. Pat. No. 8,428,523.Iaddend.,
which is a continuation of U.S. patent application Ser. No.
11/940,309 filed on Nov. 14, 2007, now U.S. Pat. No. 7,991,363, the
disclosures of all of which are hereby incorporated by reference in
their entirety.
Claims
What is claimed is:
1. A method comprising: obtaining, by a processor of a
communication device, .[.an.]. .Iadd.a non-receiver
.Iaddend.operational metric for a transceiver of the communication
device; identifying a desired transmitter performance and a desired
receiver performance; determining, by the processor, a target
figure of merit based on a compromise between the desired
transmitter performance and the desired receiver performance;
determining, by the processor, a current figure of merit based on
the .Iadd.non-receiver .Iaddend.operational metric; comparing, by
the processor, the current figure of merit to the target figure of
merit; and adjusting, by the processor, a variable reactance
component of an impedance matching circuit .[.operably.]. coupled
.[.with.]. .Iadd.between the transceiver and .Iaddend.an antenna of
the communication device .Iadd.to obtain an adjusted variable
reactance.Iaddend., the adjusting of the variable reactance
component being performed based on the comparing of the current and
the target figures of merit.Iadd., wherein the adjusted variable
reactance facilitates operation during a transmit mode of the
transceiver and during a receive mode of the communication
device.Iaddend..
2. The method of claim 1, wherein the obtaining of the
.Iadd.non-receiver .Iaddend.operational metric is during .[.a.].
.Iadd.the .Iaddend.transmit mode of the transceiver, wherein the
variable reactance component is adjusted without utilizing
operational metrics measured during .[.a.]. .Iadd.the
.Iaddend.receive mode of the communication device.
3. The method of claim 1, comprising communicating, by the
communication device, utilizing frequency division
multiplexing.
4. The method of claim 1, wherein the determining of the target
figure of merit includes selecting a mid-point between the desired
transmitter performance and the desired receiver performance.
5. The method of claim 1, comprising: storing a tuning value based
on the adjusting of the variable reactance component; and utilizing
the tuning value as a default value for subsequent tuning of the
antenna.
6. The method of claim 5, comprising: determining an operational
state of the communication device; and utilizing information
associated with the operational state as a default value for
subsequent tuning of the antenna.
7. The method of claim 6, wherein the operational state comprises a
use case scenario selected from the group consisting essentially of
hand held operation, antenna position and slider position.
8. The method of claim 1, wherein the compromise between the
desired transmitter performance and the desired receiver
performance is based on an evaluation of total radiated power.
9. The method of claim 1, wherein the compromise between the
desired transmitter performance and the desired receiver
performance is based on an evaluation of total isotropic
sensitivity.
10. The method of claim 1, wherein the compromise between the
desired transmitter performance and the desired receiver
performance is based on an evaluation of transmitter linearity.
11. The method of claim 1, wherein the compromise between the
desired transmitter performance and the desired receiver
performance is based on an evaluation of transmitter
efficiency.
12. A communication device comprising: an antenna; a transceiver;
an impedance matching network coupled .[.with.]. .Iadd.between
.Iaddend.the antenna and the transceiver, wherein the impedance
matching network includes a variable reactance component; a memory
to store computer instructions; and a controller coupled with the
memory and the impedance matching network, wherein the controller,
responsive to executing the computer instructions, performs
operations comprising: obtaining .[.an.]. .Iadd.a non-receiver
.Iaddend.operational metric associated with the transceiver;
identifying a desired transmitter performance and a desired
receiver performance; determining a target figure of merit based on
a compromise between the desired transmitter performance and the
desired receiver performance; determining a current figure of merit
based on the .Iadd.non-receiver .Iaddend.operational metric; and
adjusting the variable reactance component of the impedance
matching .[.circuit.]. .Iadd.network .Iaddend.based on a comparison
of the current figure of merit with the target figure of merit
.Iadd.to obtain an adjusted variable reactance, wherein the
adjusted variable reactance facilitates operation during a transmit
mode of the transceiver and during a receive mode of the
communication device.Iaddend..
13. The communication device of claim 12, wherein the variable
reactance component includes a voltage tunable capacitor, and
wherein the operations of the controller further comprise:
determining a use case for the communication device; and performing
an initial adjustment of the voltage tunable capacitor based on the
use case without utilizing any operational metrics associated with
the transceiver, wherein the initial adjustment of the voltage
tunable capacitor is performed prior to the adjusting based on the
comparison of the current figure of merit with the target figure of
merit.
14. The communication device of claim 12, wherein the variable
reactance component includes a Micro-Electro-Mechanical Systems
(MEMS) variable reactance component.
15. The communication device of claim 12, wherein the operations of
the controller further comprise: storing a tuning value based on
the adjusting of the variable reactance component; and utilizing
the tuning value as a default value for subsequent tuning of the
antenna.
16. The communication device of claim 12, wherein the obtaining of
the .Iadd.non-receiver .Iaddend.operational metric is during
.[.a.]. .Iadd.the .Iaddend.transmit mode of the transceiver, and
wherein the variable reactance component is adjusted without
utilizing operational metrics measured during .[.a.]. .Iadd.the
.Iaddend.receive mode of the communication device.
17. The communication device of claim 12, wherein the adjusting of
the variable reactance component is associated with a communication
session that utilizes frequency division multiplexing.
18. A method comprising: obtaining .[.an.]. .Iadd.a non-receiver
.Iaddend.operational metric for a transceiver of a communication
device; determining a target figure of merit based on transceiver
performance of the communication device; determining a current
figure of merit based on the .Iadd.non-receiver
.Iaddend.operational metric.[., wherein the determining of the
target figure of merit is not based on phase information.].;
comparing the current figure of merit to the target figure of merit
to determine a figure of merit comparison; .[.and.].
.Iadd.monitoring previous tuning results by determining a change in
the current figure of merit based on different reactance values for
a variable reactance component of an impedance matching circuit
coupled between the tranceiver and an antenna of the communication
device; and.Iaddend. adjusting, by a processor of the communication
device, .[.a.]. .Iadd.the .Iaddend.variable reactance component of
.[.an.]. .Iadd.the .Iaddend.impedance matching circuit
.[.operably.]. coupled .[.with an.]. .Iadd.between the transceiver
and the .Iaddend.antenna of the communication device, the adjusting
of the variable reactance component being performed based on the
figure of merit comparison and based on .Iadd.the .Iaddend.previous
tuning results associated with previous adjusting of the variable
reactance component.
.Iadd.19. The method of claim 18, wherein the non-receiver
operational metric for the transceiver comprises a return
loss..Iaddend.
.Iadd.20. The method of claim 18, wherein the variable reactance
component includes a Micro-Electro-Mechanical Systems (MEMS)
variable reactance component..Iaddend.
.Iadd.21. The method of claim 18, wherein the variable reactance
component includes a voltage tunable capacitor..Iaddend.
.Iadd.22. A communication device comprising: an antenna; a
transceiver; an impedance matching network coupled between the
antenna and the transceiver, wherein the impedance matching network
includes a variable reactance component; a memory that stores
computer instructions; and a controller coupled with the memory and
the impedance matching network, wherein the controller, responsive
to executing the computer instructions, performs operations
comprising: obtaining a non-receiver operational metric associated
with the transceiver; identifying a first desired performance of
the communication device; identifying a second desired performance
of the communication device; determining a target figure of merit
based on a compromise between the first desired performance and the
second desired performance; determining a current figure of merit
based on the non-receiver operational metric; and adjusting the
variable reactance component of the impedance matching network
based on a comparison of the current figure of merit with the
target figure of merit..Iaddend.
.Iadd.23. The communication device of claim 22, wherein the first
desired performance is associated with a first component of the
communication device, and wherein the second desired performance is
associated with a second component of the communication
device..Iaddend.
.Iadd.24. The communication device of claim 22, wherein the
variable reactance component includes a Micro-Electro-Mechanical
Systems (MEMS) variable reactance component..Iaddend.
.Iadd.25. The communication device of claim 22, wherein the
variable reactance component includes a voltage tunable
capacitor..Iaddend.
.Iadd.26. A communication device comprising: an antenna; a
transceiver; an impedance matching network coupled between the
antenna and the transceiver, wherein the impedance matching network
includes a variable reactance component; a memory that stores
computer instructions; and a controller coupled with the memory and
the impedance matching network, wherein the controller, responsive
to executing the computer instructions, performs operations
comprising: obtaining a non-receiver operational metric for
communications of a communication device; determining a target
figure of merit based on communications performance of the
communication device; determining a current figure of merit based
on the non-receiver operational metric; comparing the current
figure of merit to the target figure of merit to determine a figure
of merit comparison; and adjusting the variable reactance component
based on the figure of merit comparison and based on previous
tuning results associated with previous adjusting of the variable
reactance component..Iaddend.
.Iadd.27. The communication device of claim 26, wherein the
non-receiver operational metric comprises a return
loss..Iaddend.
.Iadd.28. The communication device of claim 26, wherein the
communications performance is associated with total radiated power,
total isotropic sensitivity, linearity or a combination
thereof..Iaddend.
.Iadd.29. The communication device of claim 26, wherein the
variable reactance component includes a Micro-Electro-Mechanical
Systems (MEMS) variable reactance component..Iaddend.
.Iadd.30. The communication device of claim 26, wherein the
variable reactance component includes a voltage tunable
capacitor..Iaddend.
Description
FILED OF THE DISCLOSURE
The present invention is directed towards impedance matching
circuits and more particularly, adaptive impedance matching
circuits to improve transceiver operation in a variety of
scenarios.
BACKGROUND OF THE INVENTION
As more technology and features are incorporated into small
packages, engineering teams must get more and more creative,
especially in the face of lagging miniaturization of parts and
components. One of the areas that engineers focus on is
multipurpose circuitry or, circuitry that meets a variety of
functions. A good example of this focus is with regards to antenna
matching circuits within cellular telephone devices.
Cellular telephone devices have migrated from single cellular
technology supporting devices to multi-cellular technology devices
integrating a variety of other consumer features such as MP3
players, color displays, games, etc. Thus, not only are the
cellular telephone devices required to communicate at a variety of
frequencies, they are also subjected to a large variety of use
conditions. All of these factors can result in a need for different
impedance matching circuits for the antenna. However, by utilizing
tunable components, a single matching circuit can be used under a
variety of circumstances. Tunable matching circuits generally
operate to adjust the impedance match with an antenna over a
frequency range to maximize the output power. However, difficulties
arise when attempting to tune the matching circuit for signal
reception. What is needed in the art is an adaptive impedance
matching module that can operate to optimize performance of both
the transmitter and the receiver under a variety of circumstances.
Further, what is needed is an adaptive impedance matching module
that optimizes performance of the transceiver based on optimizing
the operation in view of a figure of merit.
BRIEF SUMMARY OF THE INVENTION
In general, embodiments of the invention include a tunable matching
circuit and an algorithm for adjusting the same. More particularly,
the tuning circuit is adjusted primarily based on transmitter
oriented metrics and is then applied to attain a desired tuning for
both transmitter and receiver operation. In a time division
multiplexed (TDM) system in which the transmitter and the receiver
operate at different frequencies but are only keyed in their
respective time slots (i.e. transmit time slot and receive time
slot), this is accomplished by identifying an optimal tuning for
the transmitter and then adding an empirically derived adjustment
to the tuning circuit in receive mode. In a frequency division
multiplexed (FDM) system in which the transmitter and receiver
operate simultaneously and at different frequencies, this is
accomplished by identifying a target operation for the transmitter,
and then adjusting the tuning circuit first to the target value for
the transmitter and then adjusting the values to approach a
compromised value proximate to an equal or desired target value for
the receiver.
An exemplary embodiment of the present invention provides a method
for controlling a matching circuit for interfacing an antenna with
a transceiver. The matching circuit includes one or more tunable
components. The tuning of the matching circuit is based on a figure
of merit that incorporates one or more operation metrics. One
aspect of the present invention is that the operation metrics can
be transmitter based but still provide desired adjustment results
for receiver operation. The operation metric(s) is monitored and
measured and then compared to the figure of merit. If the desired
operation is not attained, the variable component(s) of the
matching circuit is adjusted using one or more of a variety of
techniques to attain the figure of merit. This process is performed
to maintain operation at the figure of merit.
In one embodiment of the invention more particularly suited for TDM
systems, an offset, scaling factor, translation or other change or
modification is applied to the adjustments of the variable
components when switching from the transmit mode to the receive
mode. This translation is a function of the values obtained while
adjusting during the transmit time slot. The translation is then
removed upon return to the transmitter mode and the adjustment
process is resumed.
In another embodiment of the invention particularly suited for FDM
systems, the figure of merit not only incorporates the transmit
metrics, but also incorporates an element to attain a compromise
between optimal transmitter and optimal receiver operation. This is
accomplished by identifying a target operation goal, such as a
desired transmitter and receiver reflection loss and then
identifying an operational setting that is a close compromise
between the two. This embodiment thus incorporates not only
transmitter metrics but also tuning circuit settings or preferences
into the algorithm. The tuning preferences can be empirically
identified to ensure the desired operation.
These and other aspects, features and embodiments of the present
invention will be more appreciated upon review of the figures and
the detailed description.
BRIEF DESCRIPTION OF THE SEVERAL VIEWS OF THE DRAWING
FIG. 1 is a block diagram illustrating an exemplary environment for
deployment of one or more embodiments of the present invention.
FIG. 2 is a circuit diagram illustrating further details of an
exemplary matching circuit that could be included in the AIMM in an
exemplary embodiment of the present invention.
FIG. 3 is a flow diagram illustrating the general steps taken in an
exemplary embodiment of the present invention.
FIG. 4 and FIG. 4A are a plots of the transmitter reflection losses
for four operating frequencies.
FIG. 5 is a flow diagram illustrating the steps involved in an
exemplary embodiment of the present invention operating in a TDM
environment.
FIG. 6 is a return loss contour diagram in the PTC plane for a
particular frequency (i.e., 825 MHz/870 MHz operation).
FIG. 7 is a flow diagram illustrating the steps involved in an
exemplary embodiment of the present invention in obtaining the
preference values for PTC1 and PTC2.
FIG. 8 is a contour plot showing the magnitude and the phase of the
reflection coefficient.
DETAILED DESCRIPTION OF THE INVENTION
The present invention, as well as features and aspects thereof, is
directed towards providing an impedance matching circuit, module or
component that in response to sensing the matching condition by
monitoring one or more metrics or parameters of the transmitter,
can be adjusted to optimize the match.
More specifically, embodiments of the present invention include
adaptive impedance matching circuits, modules, IC's etc., that
operate to sense the matching condition of the transmit signal or
other transmitter related metric and then optimizes the matching
characteristics by adjusting the values of one or more tunable
devices in view of attaining or reaching a figure of merit. The
figure of merit can be based on a variety of elements, such as the
input return loss, output power, current drain, linearity metrics,
as well as others. In the embodiments of the present invention that
are presented herein, the figure of merit is typically described or
defined as being based on the input return loss. However, it is to
be understood that this is just a non-limiting example of the
present invention, and although it may in and of itself be
considered as novel, other transmitter, or non-receiver, related
metrics may be incorporated into the figure of merit in addition to
or in lieu of the input return loss or reflection loss.
In an exemplary embodiment, an adaptive impedance matching module
(AIMM) detects transmitter related metrics and optimizes the
matching circuit keyed on the transmit signal. A benefit associated
with focusing on the transmit signal, as well as other transmitter
metrics, is that the transmit signal is higher in power than the
receive signal and thus, is easier to detect. However, it will be
appreciated by those skilled in the art that it is desirable to
improve the matching conditions for both the transmit signal and
the receive signal. Advantageously, the present invention operates
to optimize a figure of merit that achieves a desired operation of
both signals even though the matching adjustments performed by the
AIMM are only based on sensing the transmitter related metrics.
One embodiment of the invention is particularly well suited for
operating in a time division multiplexed (TDM) system. In a TDM
system, the radio transmits and receives in different time slots.
Typically, the transmitter and receiver also operate on different
frequencies; however, it will be appreciated that some systems
utilize the same frequency for transmission and reception.
Nonetheless, in a TDM system, the transmitter and receiver are not
active at the same time. In this environment, the AIMM can be
adjusted to optimal settings for the transmitter during a transmit
time slot and then the AIMM can be adjusted to optimal setting for
the receiver during the receive time slot. As such, the AIMM tuner
can be set differently during transmit and receive time slots.
During the transmit time slot, an adjustment algorithm is applied
to determine the appropriate settings of the AIMM to optimize the
match or attain a figure of merit that results in achieving or
approaching a desired level of operation. Because any frequency
offset between the transmit signal and the receive signal is known,
an adjustment or modification of the setting of the AIMM in the
form of a translation or some other function is applied to the AIMM
during the receive time slot. The adjustment improves the matching
characteristics at the receiver frequency based on knowledge
determined during the transmit time slot and the general operation
of the receiver. During the next transmit time slot, the
translation is removed from the AIMM and the adjustment algorithm
regains control of the AIMM. Upon returning to the receive time
slot, the modification can be reapplied or, if the settings during
the transmit time slot have been changed, then the new settings can
be modified for the subsequent receive time slot.
The adjustment applied to the AIMM during the receive time slot can
be obtained in a variety of manners. For instance, in one
embodiment the adjustment may be a translation derived empirically
by characterizing the tuner at the transmitter and receiver
frequencies and then deriving a mapping function to describe the
translation. Alternatively, the translation may be derived by using
the known (or theoretical) S-parameters of the tuner network.
Another embodiment of the present invention is particularly suited
for a Frequency Division Multiplexed (FDM) system. In an FDM
system, the radio transmits and receives at the same time but at
different frequencies. Unlike the embodiment suited for a TDM
application, the FDM application requires the AIMM to use the same
tuning condition for both transmitter and receiver operation. In
this embodiment, the tuner is adjusted to provide a desired
compromise between matching at the transmit frequency and matching
at the receive frequency. It will be appreciated that this
compromise could be attained by simply defining a figure of merit
that incorporates both a transmitter metric and a receiver metric.
However, as previously mentioned, the receive signal is typically
lower than the transmit signal and as such, it may be difficult to
accurately sense and use as a metric.
Thus, in this embodiment, non-receiver related metrics are used to
find a desired compromised state for tuning the AIMM. It will be
appreciated that the desired compromised state can vary based on
embodiment and operational requirements. For instance, in some
embodiments, transmission of data may be more important than
reception and as such, preference may be given to optimizing the
transmitter. Such a situation may exist in an emergency radio
system that is used by people in the field and that need to report
back to a central location, but are not necessarily dependent upon
information from that central location. In other embodiments, the
reception of data may be more important than the transmission. For
instance, the reception of weather related information as an
emergency warning system. In such an embodiment, preference may be
given to optimizing the receiver. Yet in other embodiments, both
the reception and transmission of data may be equally important and
as such, a setting that gives a compromised performance or attempts
to equalize the performance of both the transmitter and receiver is
desired. Such an embodiment is typical of cellular telephone
operation.
The FDM suitable embodiments of the present invention operate to
obtain a desired level of operation based on one or more
transmitter related metrics, and also incorporate known
characteristics about the tuning circuits to achieve the desired
operating state. The desired operating state typically reflects a
state of operation that is a compromise from the optimal states for
the transmitter and receiver. For instance, one embodiment of the
present invention may include the tuning states of the tunable
devices in the matching circuit within a transmit signal based
figure of merit. Advantageously, this aspect of the present
invention enables improved performance in the receive band without
having to take a receiver measurement.
Another embodiment of the invention deployable within an FDM
environment is to tune the matching circuit to a figure of merit
that is based on a vector measurement of the transmitter reflection
coefficient. In this embodiment, the phase information in the
vector measurement is incorporated into the figure of merit and the
optimal compromise between the transmitter and receiver operation
occurs at a particular phase of the transmitter reflection
coefficient.
Now turning to the figures, the various embodiments, features,
aspects and advantages of the present invention are presented in
more detail.
FIG. 1 is a block diagram illustrating an exemplary environment for
deployment of one or more embodiments of the present invention. The
illustrated embodiment includes an adaptive impedance matching
module (AIMM) 100, however, it should be appreciated that the
invention can be incorporated into embodiments that utilize
discrete components, integrated circuits, a combination of
software, firmware and hardware, or the like, and that the
embodiment presented as a module is a non-limiting example.
Further, although the present invention is described within the
context of an AIMM, it will be appreciated that various aspects,
features and embodiments equally apply to other configurations. The
AIMM 100 includes a tuner 110 that includes a matching circuit with
one or more tunable elements or components. An exemplary embodiment
of a tuner includes tunable capacitances and more specifically, two
tunable capacitances, but it will be appreciated that the present
invention can be applied to a wide variety of tunable impedance
matching circuits. Operating in conjunction with sensor 127, a
first detector 120 is used to detect the forward transmit power and
a second detector 125 is used to detect the reflected transmit
power. These values are measured in order to determine the
transmitter return loss (i.e., TxRL=20 Log|S11|) where S11 is known
by those skilled in the art to be the ratio between the reflected
and incident power on port 1. The environment may further include a
high-voltage ASIC (HV-ASIC) 130 containing a DC/DC converter and at
least two DACs to generate the high voltage bias signals 132 and
134 required to control the tunable components. A micro-controller,
microprocessor or other processing unit (PU) 140 receives output
signals from the forward detector 120 and the reflected detector
125 and can calculate the reflected loss of the transmitted signal
and thus, characterize the impedance matching of the circuit. Not
illustrated, the PU 140 also interfaces or includes one or more
memory elements including, but not limited to various forms of
volatile and non-volatile memory. For instance, the PU may
periodically write values to memory and read values from memory,
such as settings for the variable components in the AIMM.
FIG. 2 is a circuit diagram illustrating further details of an
exemplary matching circuit 200 that could be included in the AIMM
100 for an exemplary embodiment of the present invention. The
illustrated matching circuit 200 includes a first tunable
capacitance PTC1, a first impedance L1, a second impedance L2 and a
second tunable capacitance PTC2 where PTC is a Paratek Tunable
Capacitor. The first tunable capacitance PTC1 is coupled to ground
on one end and to the output of a transceiver on the other end. The
node of PTC1 that is coupled to the transceiver is also connected
to a first end of the first impedance L1. The second impedance L2
is connected between the second end of the first impedance L1 and
ground. The second end of the first impedance L1 is also coupled to
a first end of the second tunable capacitance PTC2. The second end
of the second tunable capacitance PTC2 is then coupled to an
antenna 210. The tunable capacitances can be tuned over a range
such as 0.3 to 1 times a nominal value C. For instance, if the
nominal value of the tunable capacitance is 5 pF, the tunable range
would be from 1.5 to 5 pF. In an exemplary embodiment of the
present invention, PTC1 has a nominal capacitance of 5 pf and is
tunable over the 0.3 to 1 times range, the first impedance L1 as a
value of 3.1 nH, and the second impedance L2 has a value of 2.4 nH
and the second tunable capacitance PTC2 has a nominal value of 20
pF and can be tuned over a range of 0.3 to 1 times the nominal
value. It will be appreciated that the tunable capacitances in the
illustrated embodiment could be tuned oar adjusted over their
ranges in an effort to optimize the matching characteristics of the
AIMM under various operating conditions. Thus, under various use
conditions, operating environments and at various frequencies of
operation, the tunable capacitances can be adjusted to optimize
performance or attain a desired level of performance.
FIG. 3 is a flow diagram illustrating the general steps taken in an
exemplary embodiment of the present invention. The basic flow of
the algorithm 300 initially includes measuring the performance
parameters or metrics 310 used as feedback pertaining to the
performance of the AIMM or the impedance match between a
transceiver and an antenna. The performance metrics utilized may
vary over embodiments of the present invention, over various usage
scenarios, over technology being utilized (i.e. FDM, TDM, etc.),
based on system settings and/or carrier requirements, etc. For
instance, in an exemplary embodiment of the present invention, the
performance metrics include one or more of the following
transmitter related metrics: the transmitter return loss, output
power, current drain, and transmitter linearity.
Next, a current figure of merit (FOM) is calculated 320. The
current FOM is based on the one or more performance metrics, as
well as other criteria. The current FOM is then compared to a
target FOM 325. The target FOM is the optimal or desired
performance requirements or objective for the system. As such, the
target FOM can be defined by a weighted combination of any
measurable or predictable metrics. For instance, if it is desired
to maximize the efficiency of the transmitter, the target FOM can
be defined to result in tuning the matching network accordingly.
Thus, depending on the goal or objective, the target FOM can be
defined to tune the matching network to achieve particular goals or
objectives. As a non-limiting example, the objectives may focus on
total radiated power (TRP), total isotropic sensitivity (TIS),
efficiency and linearity. Furthermore, the target FOM may be
significantly different for a TDM system and an FDM system. It
should be understood that the target FOM may be calculated or
selected on the fly based on various operating conditions, prior
measurements, and modes of operation or, the target FOM could be
determined at design time and hardcoded into the AIMM 100.
If it is determined that the current FOM is not equal to the target
FOM, or at least within a threshold value of the target FOM 330,
new tuning values for the AIMM 100 are calculated or selected 335.
However, if the current FOM is equal to or within the defined
threshold, then processing continues by once again measuring the
performance metrics 310 and repeating the process. Finally, if the
current FOM needs to be adjusted towards the target FOM, the AIMM
100 is adjusted with the new tuning values in an effort to attain
or achieve operation at the target FOM 340. In some embodiments,
this new tuning value may also be stored as a new default tuning
value of the transmitter at the given state of operation. For
instance, in one embodiment, a single default value can be used for
all situations, and as such, the latest tuning values could be
stored in the variable location. In other embodiments, a default
tuning state may be maintained for a variety of operational states,
such as band of operation, use case scenario (i.e., hand held,
antenna up/down, slider in/out, etc.) and depending on the current
operational state, the new tuning values may be stored into the
appropriate default variable.
In one exemplary embodiment, the AIMM 100 is adjusted by tuning one
or more of the tunable components 340, measuring the new FOM (i.e.,
based on the transmitter reflected loss) 320-330, and re-adjusting
or retuning the AIMM 100 accordingly 335-340 in a continuous loop.
This process is referred to as walking the matching circuit because
is moves the circuit from a non-matched state towards a matched
state one step at a time. This process is continued or repeated to
attain and/or maintain performance at the target FOM. Thus, the
process identified by steps 310 to 340 can be repeated
periodically, a periodically, as needed, or otherwise. The looping
is beneficial because even if performance at the target FOM is
attained, adjustments may be necessary as the mode of operation
(such as usage conditions) of the device change and/or the
performance of the transmitter, the antenna and the matching
circuitry change over time. In other embodiments, the tunable
components can be set based on look-up tables or a combination of
look-up tables and performing fine-tuning adjustments. For
instance, the step of calculating the AIMM tuning values 335 may
involve accessing initial values from a look-up table and then, on
subsequent loops through the process, fine tuning the values of the
components in the AIMM 100.
In an exemplary embodiment of the present invention operating
within a TDM environment, the AIMM 100 can be adjusted to optimize
the operation of the transmitter during the transmit time slot. In
such an embodiment, the performance metric may simply be the
transmitter return loss. In addition, the target FOM in such an
embodiment may also simply be a function of the transmitter return
loss. In this exemplary embodiment, the AIMM 100 can be tuned to
minimize the FOM or the transmitter return loss.
More particularly, for the circuit illustrated in FIG. 2, this
embodiment of the present invention can operate to tune the values
of PTC1 and PTC2 to minimize the transmitter return loss during the
transmit time slot. For this particular example, the algorithm of
FIG. 3 includes measuring the transmitter return loss, calculating
adjustment values for PTC1 and PTC2 to optimize a FOM that is a
function of the transmitter return loss, tuning the AIMM 100 by
adjusting the values of PTC1 and PTC2 and then repeating the
process.
The adjustment values for PTC1 and PTC2 can be determined in a
variety of manners. For instance, in one embodiment of the
invention the values may be stored in memory for various
transmitter frequencies and usage scenarios. In other embodiments,
the values may be heuristically determined on the fly by making
adjustments to the tuning circuit, observing the effect on the
transmitter return loss, and compensating accordingly. In yet
another embodiment, a combination of a look-up table combined with
heuristically determined fine tuning can be used to adjust the AIMM
100.
During the receiver time slot, the AIMM 100 can be readjusted to
optimize or improve the performance of the receiver. Although,
similar to the adjustments during the transmit time slot,
particular performance parameters may be measured and used to
calculate a current FOM, as previously mentioned it is difficult to
measure such performance parameters for the receiver. As such, an
exemplary embodiment of the present invention operates to apply a
translation to the tuning values of the AIMM 100 derived at during
the transmitter time slot, to improve the performance during the
receive time slot. During the design of the transmitter and
receiver circuitry, the characteristics of performance between the
transmitter operation and receiver operation can be characterized.
This characterization can then be used to identify an appropriate
translation to be applied. The translation may be selected as a
single value that is applicable for all operational states and use
cases or, individual values can be determined for various
operational states and use cases.
FIG. 4 is a plot of the transmitter reflection losses for four
operating frequencies of a transceiver. The contours show the
increasing magnitude of the reflection loss in 1 dB increments. For
instance, in FIG. 4A, the inside contour for the transmitter 406 is
20 dB and the bolded contour is 404 14 dB. Obviously, operation at
the center of the contours 402 is optimal during transmitter
operation. In the illustrated example, it is apparent that simply
by adjusting the value of PTC2 by adding an offset, significant
performance improvements can be achieved in the receiver time slot
by moving the operation towards point 412. The translation varies
depending on a variety of circumstances and modes of operation
including the frequency of operation, and similarly, may vary based
on usage of the device housing the circuitry. In the illustrated
example, the performance is determined to be greatly improved for
the receiver time slot if the value of PTC2 for receiver operation
is adjusted to be 0.6 times the value of PTC2 used for the optimal
transmitter setting and the value of PTC1 remains the same. This is
true for each of the illustrated cases except at the 915 MHz/960
MHz operational state. At 960 MHz, it is apparent that significant
receiver improvement can be realized by also adjusting the value of
PTC1 from its transmitter value. In the illustrated example, by
examining the characteristics of the circuitry it can be
empirically derived that a suitable equation for operation of the
receiver at 960 MHz is: PTC1_Rx=PTC1_Tx+1-1.8*PTC2_Tx.
It should be noted that this equation is only a non-limiting
example of an equation that could be used for a particular circuit
under particular operating conditions and the present invention is
not limited to utilization of this particular equation.
FIG. 5 is a flow diagram illustrating the steps involved in an
exemplary embodiment of the present invention operating in a TDM
environment. During the transmitter time slot, the AIMM algorithm
presented in FIG. 3, or some other suitable algorithm, can be
applied on a continual basis to move operation of the transmitter
towards the target FOM. However, when the receive time slot is
activated 505, the AIMM should be adjusted to match for the
receiver frequency. The adjustment to the receiver mode of
operation may initially involve determining the current operating
conditions of the device 510. Based on the current operating
conditions, a translation for tuning of the various circuits in the
AIMM 100 are identified 520. For instance, various states,
components or conditions can be sensed and analyzed to determine or
detect a current state or a current use case for the device. Based
on this information, a particular translation value or function may
be retrieved and applied. It should also be appreciated that such
translations can be determined during the design phase and loaded
into the device. Finally, the translations are applied to the AIMM
100 530. When operation returns to the transmitter time slot 535,
the AIMM algorithm again takes over to optimize operation based on
the target FOM.
It should be understood that the translation applied to tuning of
the AIMM 100 during the receiver time slot is based on the
particular circuit and device and can be determined during design
or even on an individual basis during manufacturing and testing. As
such, the specific translations identified herein are for
illustrative purposes only and should not be construed to limit the
operation of the present invention.
Thus, for TDM systems, embodiments of the present invention operate
to optimize operation of a device by tuning the matching circuit
for an antenna to optimize operation based on a target FOM. During
the receiver time slot, a translation is applied to the tuned
components to improve receiver performance. The target FOM can be
based on a variety of performance metrics and a typical such metric
is the reflection loss of the transmitter. The values for the tuned
components can be set based on operational conditions and using a
look-up table, can be initially set by using such a look-up table
and then heuristically fine tuned, or may be heuristically
determined on the fly during operation. The translations applied
during the receiver operation are determined empirically based on
the design of the circuitry and/or testing and measurements of the
operation of the circuit. However, a unique aspect of the present
invention is tuning of the matching circuit during transmit mode
and based on non-receiver related metrics and then retuning the
circuit during receive mode operation based on a translation to
optimize or attain a desired level of receiver operation.
In an exemplary embodiment of the present invention operating
within an FDM environment, the AIMM 100 can be adjusted to so that
the matching characteristics represent a compromise between optimal
transmitter and receiver operation. Several techniques can be
applied to achieve this compromise. In one technique, the
translation applied in the TDM example could be modified to adjust
the AIMM 100 as a compromise between the optimal transmit and
receive settings. For instance, in the example illustrated in FIG.
2, the value of PTC1 and PTC2 can be determined and adjusted
periodically, similar to TDM operation (even though such action
would temporarily have an adverse effect on the receiver). Then, a
translation could be applied to the values of PTC1 and PTC2 for the
majority of the operation time. For instance, in the TDM example
shown in FIG. 4, the transmitter values were adjusted by
multiplying the PTC2 value by 0.6 in three modes of operation and
using the above-identified equation during a forth mode of
operation. This same scheme could be used in the FDM mode of
operation however, the scaling factor would be different to obtain
operation that is compromised between the optimal transmitter
setting and optimal receiver setting. For example, multiplying the
PTC2 value by 0.8 could attain an acceptable compromise.
However, another technique of an embodiment of the present
invention is to apply an algorithm that operates to attain a target
FOM that is based on one or more transmitter related metrics (such
as return loss) and the values of the adjustable components in the
AIMM. Advantageously, this aspect of the present invention
continuously attempts to maintain a compromised state of operation
that keeps the operation of the transmitter and the receiver at a
particular target FOM that represents a compromise performance
metric level.
In the particular example illustrated in FIG. 2, such an algorithm
could be based on a target FOM that is an expression consisting of
the transmitter return loss and the values of PTC1 and PTC2.
Because the algorithm is not operating to minimize the transmitter
return loss in this embodiment of an FDM system, a compromised
value is specified. For instance, a specific target transmitter
return loss can be pursued for both transmitter and receiver
operation by tuning the AIMM based on a FOM that is not only a
function of the return loss, but also a function of the values of
PTC1 and PTC2 that will encourage operation at a specific level.
The target FOM is attained when the actual transmitter return loss
is equal to the target transmitter return loss and, specified
preferences for PTC1 and PTC2 are satisfied. The preferences
illustrated are for the value of PTC1 to be the highest possible
value and the value of PTC2 to be the lowest possible value while
maintaining the transmit return loss at the target value and
satisfying the PTC1 and PTC2 preferences.
FIG. 6 is a return loss contour diagram in the PTC plane for a
particular frequency (i.e., 825 MHz/870 MHz operation). Obviously,
optimal operation in an FDM system cannot typically be attained
because the settings for optimal transmitter operation most likely
do not coincide with those for optimal receiver operation. As such,
a compromise is typically selected. For instance, a compromise may
include operating the transmitter at a target return loss value of
-12 dB and at a point at which the transmitter -12 dB contour is
closest to a desired receiver contour (i.e., -12 dB).
The operational goal of the system is to attempt to maintain the
matching circuit at a point where the operational metrics for the
transmitter are at a target value (eg. -12 dB) and the estimated
desired receiver operation is most proximate. In an exemplary
embodiment of the present invention, an equation used to express
the target FOM for such an arrangement can be stated as follows:
Target FOM=f(Tx_RL,TX_RL_Target)+f(PTC2,PTC1) Where: TX_RL is the
measure transmitter return loss TX_RL_Target is the targeted
transmitter return loss
In an exemplary embodiment suitable for the circuit provided in
FIG. 2, the FOM may be expressed as:
FOM=(Tx_RL-Tx_RL_Target)+C2*PTC2-C1*PTC1), where, C1 and C2 are
preference constants or scaled values, and if Tx_RL>Tx_RL_Target
then Tx_RL=Tx_RL_Target.
In operation, exemplary embodiments of the present invention
optimize the transmitter based on the target reflected loss to
attain operation on the desired contour 610 (as shown in FIG. 6)
and also adjusts the values of PTC1 and PTC2 to attain operation at
the desired location 630 (or minimum FOM) on the contour. The
portion of the FOM equation including the TxRL and TX_RL_Target
values ensures operation on the targeted RL contour 610 (i.e., the
-12 db RL contour). By observing the contour 610, it is quite
apparent that not all points on the target reflected loss contour
have the same value for the PTC1 and PTC2. Because of this, the
values of PTC1 and PTC2 can be incorporated into the target FOM
equation to force or encourage operation at a particular location
on the reflected loss contour. In the illustrated example, the
target FOM is the point at which the reflected loss contour is
closest to the expected same valued reflected loss contour for the
receiver. However, it will be appreciated that other performance
goals may also be sought and the present invention is not limited
to this particular example. For instance, in other embodiments, the
target FOM may be selected to encourage operation at a mid-point
between optimal transmitter performance and expected optimal
receiver performance. In yet another embodiment, the target FOM may
be selected to encourage operation at a point that is mid-point
between a desired transmitter metric and an estimated or measured
equivalent for the receiver metric.
In the provided example illustrated in FIG. 6, the optimum,
compromised or desired point on the target contour is the point
that minimizes the value of PTC2 and maximizes the value of PTC1 in
accordance with the equation C2*PTC2-C1*PTC1. Thus, the portion of
the expression including PTC1 and PTC2 ensures that operation is at
a particular location on the contour that is desired--namely on the
lower portion of the contour and closest to the RX_RL contour 620.
In general, the algorithm operates to optimize the current FOM or,
more particularly in the illustrated embodiment, to minimize the
expression of C2*PTC2-C1*PTC1 as long as the desired TX_RL
parameter is also met. It should be appreciated that the details
associated with this example are associated with a specific circuit
design and a wide variety of relationships between the adjustable
components of the AIMM would apply on a circuit by circuit basis
and as such, the present invention is not limited to this specific
example.
Another embodiment of the present invention may take into
consideration historical performance of the tunable components as
well as current values. As an example, as the tunable components
are adjusted, changes in the current FOM will occur in a particular
direction (i.e., better or worse). As an example, if the AIMM
adjustments 26 result in the current FOM falling on the top portion
of a desired performance contour, making a particular adjustment
may result in making the current FOM worse or better. If the
adjustment was known to cause a certain result when the current FOM
is located on the bottom of the contour and this time, the opposite
result occurs, then this knowledge can help identify where the
current FOM is located on the contour. Thus, knowing this
information can be used in combination with the operation metric to
attain the operation at the target FOM. For instance, the target
FOM may be a function of the operational metrics, the current
states of the tunable components, and the knowledge of previous
results from adjusting the tunable components.
Stated another way, when a current FOM is calculated, the
adjustments to reach the target FOM may take into consideration
past reactions to previous adjustments. Thus, the adjustment to the
tunable components may be a function of the FOM associated with a
current setting and, the change in the current FOM resulting from
previous changes to the tunable components.
In another embodiment of the present invention operating in an FDM
environment, the FOM may be optimized similar to operation in the
TDM environment. For example, the FOM may be a function of the
transmitter reflected loss metric and the system may function to
optimize the FOM based on this metric. Once optimized, the tunable
components can be adjusted based on a predetermined translation to
move the FOM from the optimized for the transmitter position to a
position that is somewhere between the optimal transmitter setting
and the optimal receiver setting.
FIG. 7 is a flow diagram illustrating the steps involved in an
exemplary embodiment of the present invention in obtaining the
preference values for PTC1 and PTC2. Initially, the process 700
involves plotting of the return loss contours for the various modes
of operation, or a reasonable subset thereof 710. FIG. 6 is an
example of such a plot generated as a result of performing this
step. Next, the compromised tuning location is identified 720. As
previously mentioned, a variety of factors may be weighed to
determine the compromised tuning location and one example, as
illustrated in FIG. 6, is the point at which a target reflected
loss for the transmitter is the most proximate to a target
reflected loss for the receiver. In a typical embodiment, this is
the point at which the target transmitter and receiver contours at
the desired reflected loss are closest to each other and nearly
parallel. Once the compromised location is determined, the
preference values can be characterized 730. For instance, in the
example in FIG. 6, by drawing a perpendicular line between the two
contours and passing through the compromised location, the slope
and hence the preferences can be identified. These preference
values can then be determined and then applied across the broad
spectrum of frequencies and usage scenarios 740.
It should be appreciated that the values of C1 and C2 are constants
and can vary among embodiments of the invention, as well as among
devices employing the invention. As such, the values are determined
empirically as described above. In an exemplary embodiment, the
values of C1 and C2 are 0.7 and 2 respectively for a given circuit
and a given antenna, given mode of operation, etc. Thus, any given
set of constants are determined empirically and only apply to a
specific antenna design, circuit and mode of operation and,
although the use of these specific values may in and of itself be
considered novel, the present invention is not limited to the
particular expression. In fact, depending on particular goals,
design criteria, operational requirements, etc. different values
may be required to attain the compromised performance. It will also
be appreciated that in various embodiments, it may be desired to
have a different targeted reflection loss for the transmitter than
for the receiver.
In another embodiment of the present invention, rather than
analyzing the transmitter reflected power as the performance
metric, the reflection coefficient vector may be measured. In this
embodiment, the phase information of the reflection coefficient may
be included within the FOM. For example, FIG. 8 is a contour plot
showing the magnitude and the phase of the reflection coefficient.
The preferred point of operation 830 is shown as falling on the -12
dB contour 810 and at a phase of 45 degrees. In such an embodiment,
the components of the matching circuit of the AIMM 100 can be
adjusted to meet a reflected loss value that falls on the -12 db
contour and that also approaches the specific point on the contour
namely at the point where the reflection coefficient differs by 45
degrees.
As mentioned, mobile and transportable transceivers are subjected
to a variety of use cases. For instance, a typical cellular
telephone could be operated in various scenarios including speaker
phone mode, ear budded, with the antenna in the up position or the
down position, in the user's hand, holster, pocket, with a slider
closed or extended, in a holster or out of a holster, etc. All of
these scenarios, as well as a variety of other environmental
circumstances can drastically alter the matching characteristics of
the cellular telephone's antenna circuitry. As such, not only do
the various embodiments of the present invention operate to tune
the matching circuitry based on the operational frequency, but in
addition, adjust the matching characteristics based on changes in
the modes of operation. Advantageously, this greatly improves the
performance of the device without requiring separate matching
circuitry for the various modes of operation of the device. Thus,
it will be appreciated that various other parameters can be
monitored to identify various use cases and then adjustments to the
tuning circuitry can be immediately deployed followed by fine
tuning adjustments to optimize the FOM. The other parameters in
which the embodiments of the present invention may function are
referred to as modes of operation. The various modes of operation
include the use cases as previously described, along with operating
environments, bands of operation, channel frequencies, modulation
formats and schemes, and physical environments. Thus, the various
embodiments of the present invention may make changes, select
default values, calculate adjustment values, etc., all as a
function of one or more of the modes of operation.
One embodiment of the present invention may maintain a set of
initial starting values based on the various use cases and
operational environments. For instance, each use case may include a
default value. Upon detection or activation of the device in a new
use case, the default value is obtained from memory and the
components in the AIMM are tuned accordingly. From that point on,
the adjustment algorithm can then commence fine tuning of the
operation. As previously mentioned, each time the target FOM is
attained for a particular use case, the new values may be written
into the default location as the new default values. Thus, every
time the operational state of the device changes, such as changing
between bands of operation etc., the default values are obtained
and applied, and then adjustments can resume or, operation can
simply be held at the default value.
Numerous specific details have now been set forth to provide a
thorough understanding of the invention. However, it will be
understood by those skilled in the art that the present invention
may be practiced without these specific details. In other
instances, well-known methods, procedures, components and circuits
have not been described in detail so as not to obscure the present
invention.
Unless specifically stated otherwise, as apparent from the
description, it is appreciated that throughout the specification
discussions that different electronic devices could be used to
create a variable tuner network. The embodiments used in the
examples discussed were specific to variable capacitor devices,
however variable inductors, or other tunable networks, built out of
elements such as Micro-Electro-Mechanical Systems (MEMS) and/or
other tunable variable impedance networks could be used in such an
AIMM system.
Unless specifically stated otherwise, as apparent from the
description, it is appreciated that throughout the specification
discussions utilizing terms such as "processing," "computing,"
"calculating," "determining," or the like, refer to the action
and/or processes of a microprocessor, microcontroller, computer or
computing system, or similar electronic computing device, that
manipulate and/or transform data represented as physical, such as
electronic, quantities within the computing system's registers
and/or memories into other data similarly represented as physical
quantities within the computing system's memories, registers or
other such information storage, transmission or display
devices.
Embodiments of the present invention may include apparatuses for
performing the operations herein. An apparatus may be specially
constructed for the desired purposes, or it may comprise a general
purpose computing device selectively activated or reconfigured by a
program stored in the device. Such a program may be stored on a
storage medium, such as, but not limited to, any type of disk
including floppy disks, optical disks, compact disc read only
memories (CD-ROMs), magnetic-optical disks, read-only memories
(ROMs), random access memories (RAMs), electrically programmable
read-only memories (EPROMs), electrically erasable and programmable
read only memories (EEPROMs), magnetic or optical cards, or any
other type of media suitable for storing electronic instructions,
and capable of being coupled to a system bus for a computing
device.
The processes presented herein are not inherently related to any
particular computing device or other apparatus. Various general
purpose systems may be used with programs in accordance with the
teachings herein, or it may prove convenient to construct a more
specialized apparatus to perform the desired method. The desired
structure for a variety of these systems will appear from the
description below. In addition, embodiments of the present
invention are not described with reference to any particular
programming language. It will be appreciated that a variety of
programming languages may be used to implement the teachings of the
invention as described herein. In addition, it should be understood
that operations, capabilities, and features described herein may be
implemented with any combination of hardware (discrete or
integrated circuits) and software.
Use of the terms "coupled" and "connected," along with their
derivatives, may be used. It should be understood that these terms
are not intended as synonyms for each other. Rather, in particular
embodiments, "connected" may be used to indicate that two or more
elements are in direct physical or electrical contact with each
other. "Coupled" may be used to indicated that two or more elements
are in either direct or indirect (with other intervening elements
between them) physical or electrical contact with each other,
and/or that the two or more elements co-operate or interact with
each other (e.g. as in a cause an effect relationship).
In the description and claims of the present application, each of
the verbs, "comprise," "include," and "have", and conjugates
thereof, are used to indicate that the object or objects of the
verb are not necessarily a complete listing of members, components,
elements, or parts of the subject or subjects of the verb.
The present invention has been described using detailed
descriptions of embodiments thereof that are provided by way of
example and are not intended to limit the scope of the invention.
The described embodiments comprise different features, not all of
which are required in all embodiments of the invention. Some
embodiments of the present invention utilize only some of the
features or possible combinations of the features. Variations of
embodiments of the present invention that are described and
embodiments of the present invention comprising different
combinations of features noted in the described embodiments will
occur to persons of the art.
It will be appreciated by persons skilled in the art that the
present invention is not limited by what has been particularly
shown and described herein above. Rather the scope of the invention
is defined by the claims that follow.
* * * * *