U.S. patent number 3,811,128 [Application Number 05/352,034] was granted by the patent office on 1974-05-14 for electrically scanned microstrip antenna.
This patent grant is currently assigned to Ball Brothers Research Corporation. Invention is credited to Robert E. Munson.
United States Patent |
3,811,128 |
Munson |
May 14, 1974 |
ELECTRICALLY SCANNED MICROSTRIP ANTENNA
Abstract
A microstrip antenna including a dielectric layer loaded with a
ferrite material disposed between a ground plane and a generally
planar or single layer arrangement of electrical conductors
constituing both r.f. radiators and r.f. feedlines. Either or both
of the r.f. radiators and feedlines include special d.c. circuits
for passing d.c. electrical currents. When the d.c. electrical
currents are passed through the r.f. radiators, the permeability of
the ferrite loaded dielectric is altered thus scanning the resonant
frequency of a radiator in accordance with the applied d.c. current
or voltage. Furthermore, when the d.c. currents are passed through
the r.f. feedline, or portions thereof, the magnetic fields set up
in the ferrite loaded dielectric causes controlled phase shifts to
occur in r.f. energy passing there along thus effecting controlled
phase shifts and hence beam scanning of an array of such radiators
as a function of the d.c. current or voltage.
Inventors: |
Munson; Robert E. (Boulder,
CO) |
Assignee: |
Ball Brothers Research
Corporation (Boulder, CO)
|
Family
ID: |
23383513 |
Appl.
No.: |
05/352,034 |
Filed: |
April 17, 1973 |
Current U.S.
Class: |
343/787; 342/371;
343/846 |
Current CPC
Class: |
H01Q
3/44 (20130101); H01Q 9/0407 (20130101) |
Current International
Class: |
H01Q
3/44 (20060101); H01Q 9/04 (20060101); H01Q
3/00 (20060101); H01q 001/00 (); H01q 003/26 () |
Field of
Search: |
;343/769,787,846,854
;333/84M |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Lieberman; Eli
Claims
1. An antenna structure comprising:
an electrically conducting ground surface,
a single layer arrangement of electrical conductors including at
least one r.f. radiator and r.f. feedline connected thereto,
a dielectric layer loaded with a ferrite material disposed between
said ground surface and said single layer arrangement, and
said single layer arrangement including d.c. circuit means for
passing d.c. electrical current through at least a predetermined
portion of said
2. An antenna structure as in claim 1 wherein said d.c. circuit
means is connected to said r.f. radiator whereby the resonant
frequency of the radiator can be controlled by controlling the
permeability of said ferrite
3. An antenna structure as in claim 2 wherein said d.c. circuit
means comprises r.f. blocking-d.c. passing means for connecting
said radiator
4. An antenna structure as in claim 1 wherein said d.c. circuit
means is connected to said r.f. feedline whereby controlled phase
shifts in r.f. energy travelling therealong can be achieved by
controlling the d.c.
5. An antenna structure as in claim 4 wherein said d.c. circuit
means comprises:
d.c. blocking-r.f. passing means disposed in said r.f. feedline for
isolating predetermined portions of the r.f. feedline with respect
to d.c. electrical currents, and
r.f. blocking-d.c. passing means disposed for interconnecting said
isolated
6. An antenna structure as in claim 5 wherein said d.c.
blocking-r.f. passing means comprises:
two closely spaced but physically separated parallel electrical
conductors
7. An antenna structure as in claim 5 wherein said r.f.
blocking-d.c. passing means comprises:
electrical conductors including open circuited stubs disposed to
reflect an r.f. open circuit condition at an anticipated r.f.
operating frequency
8. An antenna structure as in claim 1 wherein:
said at least one r.f. radiator comprises a plurality of r.f.
radiators disposed to form a phased antenna array providing a beam
pattern of radiation along a predetermined direction,
said r.f. feedline comprises a corporate structure feedline for
dividing an r.f. input energy between the r.f. radiators at
predetermined relative phase angles in the absence of said d.c.
electrical current, and
said d.c. circuit means includes d.c. electrical current paths
along selectively predetermined portions of the r.f. feedline to
control said relative phase angles as a function of said d.c.
electrical current whereby the predetermined direction of said beam
patterns of radiation is
9. An antenna structure as in claim 8 wherein said d.c. circuit
means comprises:
d.c. blocking-r.f. passing means disposed in said r.f. feedline for
isolating predetermined portions of the r.f. feedline with respect
to d.c. electrical currents, and
r.f. blocking-d.c. passing means disposed for interconnecting said
isolated
10. An antenna structure as in claim 8 wherein:
said plurality of r.f. radiators are disposed in a two dimensional
phased array, and
said d.c. circuit means comprises:
a first d.c. circuit for passing a first d.c. electrical current to
control the predetermined direction of the beam pattern in a
corresponding first coordinate direction, and
a second d.c. circuit for passing a second d.c. electrical current
to control the predetermined direction of the beam pattern in a
corresponding
11. An antenna structure as in claim 8 further comprising
controllable switch means connected to at least one of said r.f.
feedline and said d.c. circuit means for providing further
selectable changes in the relative
12. An antenna structure as in claim 11 wherein said controllable
switch means comprises at least one diode.
Description
This application is related to my co-pending U.S. application Ser.
No. 352,005 filed concurrently herewith. It is also related to
commonly assigned United States Pat. No. 3,713,162 and to the
commonly assigned co-pending application Ser. No. 99,481 filed Dec.
18, 1970.
This invention relates generally to antenna structures utilizing a
ferrite loaded dielectric layer disposed between a ground plane and
another layer of conductors comprising the antenna elements and/or
feedlines. In particular, it relates to an antenna structure of
this kind wherein the resonant frequency of an r.f. radiator and/or
the beam direction of an array of such radiators is controlled by
passing d.c. electrical currents through the radiator and/or
feedlines respectively.
The antenna structure to be described below is a form of microstrip
antenna wherein the actual r.f. feedlines and/or r.f. radiators are
preferably formed on one face of a dielectric sheet using
conventional photo-resist/etching techniques as are used in forming
electrical circuit boards.
As will be appreciated by those in the art, it is often desirable
to increase the bandwidth or range of possible operating
frequencies for any given antenna structure whether that structure
is utilized alone or in an array of similar structures. As will be
explained in more detail below, when the dielectric substrate of a
microstrip antenna is loaded with a ferrite material the resonant
frequency for the microstrip radiator may be altered by passing a
direct current through the radiator thus changing the permeability
of the ferrite loaded dielectric in the vicinity of the radiator.
Such changes in the relative permeability of the dielectric will
change the effective electrical length or other dimension of the
microstrip radiator thus altering the operating frequency as will
become apparent. Accordingly, the antenna structure of this
invention permits controlled increases in the effective bandwidth
for any given antenna dimensions.
An electronically scanned antenna array is usually a costly and
complex apparatus. However, as will be explained in more detail
below, the antenna structure of this invention may be formed
through economical printed circuit board techniques to provide a
microstrip antenna array having a radiation beam direction that may
be selectively or controllably scanned as a function of a variable
voltage or current. One variable voltage will permit scanning in
one coordinate direction while two variable voltages will permit
two dimensional scanning along two coordinate directions as will
become apparent. Accordingly, this antenna structure provides an
extremely simple, reliable, and cheap scannable array. Furthermore,
it is extremely simple to operate the scanned array of this
invention since all that is required is a variable d.c. voltage or
current. Since techniques are readily available for providing
variable voltages/currents having complex predetermined wave
shapes, it should readily be apparent that the antenna array of
this invention may be easily controlled to follow complex scanning
patterns.
Furthermore, since the antenna structure of this invention is
extremely thin compared to conventional antenna structures, it is
readily adaptable for use in streamlined vehicles such as airplanes
and rockets where design considerations necessitate the minimum
possible protuberance either inside or outside of the vehicular
skin. As will be appreciated, since the antenna is really in the
nature of a thin printed circuit board, the whole structure will be
flexible if the dielectric material is properly chosen thus making
it easy to conform the entire antenna structure with the skin of
such a vehicle or to any other desired shape.
These and many other objects and advantages of this invention will
be more clearly understood from the following detailed description
taken in conjunction with the accompanying drawings, of which:
FIG. 1 is a plan view of an exemplary microstrip antenna array
according to this invention which permits beam scanning in one
dimension by controlling a d.c. current along portions of the r.f.
feedline therein;
FIG. 2 is a cross sectional view of the exemplary antenna array
shown in FIG. 1;
FIG. 3 is a sequence of schematic diagrams illustrating the
variation of beam direction with a d.c. current for the exemplary
antenna structure of FIG. 1;
FIG. 4 is an exemplary plan view of one microstrip radiator
including a d.c. circuit for altering its resonant frequency;
FIG. 5 illustrates an exemplary modification of the FIG. 1
embodiment using switchable diodes to further selectively alter the
beam steering characteristics of the array; and
FIG. 6 is a schematic illustration of an exemplary two dimensional
microstrip antenna array including two separate d.c. current
circuits in the r.f. feedlines for steering the beam direction of
the two dimensional array along two coordinate axes.
The printed circuit board 10 shown in FIG. 1 is shown in cross
section at FIG. 2. Broadly stated, it comprises the usual printed
circuit board construction wherein a conductive layer 12 is
selectively etched away from a dielectric layer 14 to result in a
generally planar or single layer arrangement of electrical
conductors on top of the dielectric substrate 14. In the case of
this invention, the planar arrangement of conductors 12 comprises
r.f. feedlines as well as r.f. radiator sections and superposed
d.c. electrical circuits as will be explained. The dielectric
substrate 14 has been loaded with conventional microwave quality
ferrite materials as indicated in FIG. 2 and is disposed between
the planar arrangement of electrical conductors 12 and a ground
plane surface of electrically conducting material 16. As will be
appreciated by those in the art, the ground plane 16 may, in fact,
comprise a layer of conductive material adhered to the backside of
the dielectric layer 14 thus being co-extensive with the dielectric
substrate 14. On the other hand, the ground plane 16 might also
comprise part of a conducting vehicular surface such as an airplane
or missile skin, etc., as will be appreciated.
As indicated in FIG. 2, the ferrite loaded dielectric 14 may
comprise a conventional dielectric material in which conventional
microwave quality ferrite powder has been dispersed by conventional
techniques. Alternatively, it is possible to load the dielectric
substrate with a sheet of ferrite material as will be apparent to
those in the art. In the preferred embodiment, the planar or single
layer arrangement of electrical conductors 12 is formed by
conventional photo resist-chemical etching processes commonly used
in the manufacture of printed circuit boards.
As seen in FIG. 1, a linear array of microstrip radiators N.sub.1,
N.sub.2, N.sub.3 and N.sub.4 is provided. Each of these radiators
is fed from an r.f. feedline emanating from an overall corporate
feedline structure wherein the original r.f. input signal at 18 is
first divided at point 20 into two equal power signals as should be
apparent. In the absence of any d.c. electrical current (as will be
described in more detail below), these divided half power signals
will also be of equal phase relative to one another as they travel
along the corporate structure r.f. feedline.
These half power signals are again divided at points 22 and 24 into
quarter power signals of equal power and equal relative phases
which are then fed directly to the microstrip radiators as shown in
FIG. 1. Accordingly, as will be appreciated, in this case of zero
d.c. current, all elements of the linear array will be fed with
equal power and equal relative phase signals so that the resultant
radiation will be a high gain beam pattern directed normally to the
plane of the array and as is schematically illustrated in the top
line of FIG. 3.
Ferrite materials have been used in the past to cause relative
phase shifts in r.f. signals as shown for instance in United States
Pat. No. 3,553,733 to Buck and in United States Pat. No. 3,377,592
to Robieux et al. However, these prior structures have involved
bulky waveguides and/or external electromagnet assemblies that have
made them relatively complex and costly.
It has now been discovered that the antenna structure of this
invention utilizing a ferrite loaded dielectric may be conveniently
modified to produce the necessary phase shifts between the array
radiators thus achieving beam steering capability for the array.
For example, as shown in FIG. 1, a variable d.c. electrical current
source 26 is connected to a d.c. circuit within the generally
planar arrangement of electrical conductors 12 for achieving the
necessary relative phase shifts. Of course, as those in the art
will appreciate, the current source 26 could be just as well be
replaced with a voltage source; however, since the phase shifting
and/or other effects to be described herein are believed to be
proportional to the d.c. current, the exemplary embodiment has been
explained using a variable d.c. current source for explanatory
purposes.
In essence, the exemplary embodiment in FIG. 1 provides for a d.c.
electrical current to flow along the isolated segments 28, 30 and
32 of the r.f. feedline structure. It has been discovered, that
when d.c. currents are passed through these microstrip feedlines
above the ferrite loaded dielectric, a controlled phase shift may
be introduced into r.f. signals also passing therealong.
Accordingly, as can be appreciated from FIG. 1, the r.f. signals
routed to the microstrip radiator N.sub.1 will not experience any
further additional relative phase shifts. However, those r.f.
signals routed to microstrip radiator N.sub.2 will experience an
additional phase shift proportional to the current being passed
along isolated segment 28 and to the length of segment 28.
Likewise, the r.f. signal being passed to radiator N.sub.3 will
experience a similar added relative phase shift (since the d.c.
circuit is a series circuit exactly the same d.c. current must be
flowing in segment 30 as in segment 28) but since the length of
segment 30 is twice the length of segment 28, these signals will
have experienced twice as much relative phase shifting as those
which are supplied to radiator N.sub.2. Similarly, the signals
supplied to radiator N.sub.4 undergo a still further phase shift
along segment 32 of the d.c. circuit which is equal in length to
one-half of segment 30 and to the full length of segment 28.
Accordingly, the signals reaching radiator N.sub.4 will be shifted
three times as much in relative phase as those signals which are
supplied the radiator N.sub.2.
The segments 28, 30 and 32 of the r.f. feedline in FIG. 1 are
isolated from the other portions of the r.f. feedline with respect
to d.c. currents by d.c. blocking-r.f. passing means 34 which are
somewhat analogous to the d.c. blocking capacitors used in low
frequency electronics circuits. Here, to insure maximum passage of
r.f. currents, the "plates" of these coupling means should be
approximately one-fourth of a wave length long (taking into account
the dielectric and magnetic parameters of the ferrite loaded
dielectric) and spaced, preferably, no more than two to three
thousandths of an inch apart.
These isolated segments of the r.f. feedline are interconnected by
d.c. passing-r.f. blocking means 36, 38 and 40. These d.c.
passing-r.f. blocking segments of the d.c. circuit are somewhat
analagous to r.f. chokes commonly used in electrical circuits. To
minimize the interference with r.f. currents in the r.f. feedlines,
the d.c. circuits 36, 38 and 40 should include any necessary open
circuited line segments 42 dimensioned and spaced to reflect an
r.f. open circuit condition at the actual points of connection to
the r.f. feedline for the anticipated operating frequency.
Thus, as should now be appreciated, a complete d.c. circuit has
been described within the planar or single layer arrangement of
electrical conductors 12. This circuit comprises the d.c.
passing-r.f. blocking portions 36, 38 and 40 together with the
isolated r.f. feedline segments 28, 30 and 32. Of course, the d.c.
circuit is returned to ground as at 44 to complete the electrical
circuit.
Referring now to FIG. 3, the situation as it would exist with no
current flowing in the d.c. circuit from current source 26 is shown
at the top line of FIG. 3 wherein all four of the microstrip
radiators are receiving equal power and equally phased excitations
to result in a beam direction normal to the plane of the linear
array. However, when the current source 26 is activated to produce
some current I.sub.1 relative phase shifts will be introduced in
the r.f. signals traversing isolated segments 28, 30 and 32 which
phase shifts will be proportional to the magnitude of the current
I.sub.1 and to the length of r.f. feedline conducting such d.c.
currents along which the various r.f. signals are propagating.
Accordingly, for some value I.sub.1 a situation can be expected as
shown in line 2 of FIG. 3 where the relative phase angles between
the excitation or driving signals to the four microstrip radiators
differ by 10.degree. to cause the beam direction to be deviated as
shown in the second line of FIG. 3.
For a further increase in the d.c. current to a second higher value
I.sub.2, a situation will be reached as depicted in line 3 of FIG.
3 where the array elements are excited by signals 30.degree. out of
phase with respect to their nearest neighbors to even further
deviate the beam direction as is also indicated in FIG. 3.
Accordingly, as should now be apparent, the beam of the linear
array may be swept along the dimension of the array (i.e., rotated
with respect to the fixed array) by merely sweeping the current or
voltage source 26.
Besides sweeping the beam direction of such an array, it has also
been discovered that it is possible to change the actual resonant
frequency of the microstrip radiators with this antenna structure
as is schematically depicted in FIG. 4. Here, one of the microstrip
radiators 50 has been connected into a d.c. circuit via the d.c.
passing-r.f. blocking segments 52 and 54 with a d.c. current or
voltage source 56. Thus, as the d.c. current or voltage source 56
is varied, the ferrite material is caused to take on different
values of magnetic permeability which will, in turn, change the
effective electrical length (approximately one-half wavelength at
resonance) of the radiator 50 according to the well-known
electrical formula .lambda../2.sqroot..mu..sub.r .epsilon..sub.r
which, of course, will change the effective resonant frequency of
the microstrip radiator 50 as should now be apparent. Accordingly,
in spite of the fact that microstrip antennas are relative narrow
bandwidth radiators, the resonant frequency may be changed by this
technique to effectively increase the potential operating bandwidth
of the microstrip radiators.
As should now be apparent, the scanning of the resonant frequency
of the radiators as depicted for one radiator in FIG. 4 may be
utilized with a single microstrip radiator as shown in FIG. 4 or
for one or more of the microstrip radiators of an array such as,
for example, the array of FIG. 1.
Since d.c. electrical currents are being utilized within the r.f.
feedline of FIG. 1, it is also possible to selectively alter the
beam sweeping or scanning operation of the array as a function of
the voltage by using switchable diodes such as shown in FIG. 5. The
diodes may be Zener type diodes which are selectively actuated by
various d.c. voltage levels and/or they may be controllable diodes
that are under the control of a mini-computer or some other
conventional control means to alter either the r.f. and/or the d.c.
elecrical circuits to obtain further selected changes in the
relative phase shifts to be attained between the various radiators
in the array as should now be appreciated by those in the art.
A two dimensional array of microstrip radiators is depicted in FIG.
6 together with an arrangement for scanning the pencil beam of
radiation produced by such a two dimensional array in two
coordinate directions. For instance, as shown in FIG. 6, four
linear arrays 100, 102, 104 and 106 may be placed side by side to
provide the two dimensional array. Each of the linear arrays
includes a corporate structured r.f. feedline as shown in FIG. 1
together with appropriate d.c. circuits for scanning the beam in
the X direction (that is between the bottom and top of FIG. 6) in
response to variations in the I.sub.x current from current source
108 as should now be apparent from the previous discussion.
In addition, each of the r.f. inputs 110, 112, 114 and 116 are
carried upward to another corporate structured r.f. feedline which
includes a d.c. electrical circuit by which the relative phases of
the r.f. signals being input to each of the linear arrays may be
selectively shifted for causing the beam to scan in the Y direction
between left and right in FIG. 6). That is, selective phase changes
proportional to the current I.sub.y from current source 118 are
introduced for r.f. signals traversing the isolated r.f. feedline
portions 120, 122 and 124, which isolated segments are
interconnected by d.c. passing-r.f. blocking circuits 126, 128 and
130 as shown in FIG. 6.
The operation of the two dimensional array is exactly analagous to
the one dimensional array previously discussed and it should now be
apparent that a pencil beam of radiation produced by the two
dimensional array may be selectively directed to any desired
direction along the X and Y coordinates by selectively choosing the
appropriate current magnitudes for current I.sub.x and I.sub.y from
current sources 108 and 118 respectively.
Although only a few specific embodiments of this invention have
been described in detail above, those in the art will readily
appreciate that there are many possible modifications to the
exemplary embodiments without departing from the spirit and
teaching of this invention. Accordingly, this invention is intended
to encompass all such modifications and/or variations.
* * * * *