U.S. patent application number 16/295844 was filed with the patent office on 2019-12-05 for device for controlling inverter.
The applicant listed for this patent is LSIS CO., LTD.. Invention is credited to Hak-Jun LEE.
Application Number | 20190372453 16/295844 |
Document ID | / |
Family ID | 65724326 |
Filed Date | 2019-12-05 |
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United States Patent
Application |
20190372453 |
Kind Code |
A1 |
LEE; Hak-Jun |
December 5, 2019 |
DEVICE FOR CONTROLLING INVERTER
Abstract
Disclosed is a device for controlling an inverter. The device
achieves a minimum switching loss in a discontinuous modulation
duration regardless of a power factor. The device includes: a
command voltage transform unit configured for transforming each of
3 phases command voltages into each of pole command voltages using
the DC stage voltage, a pulse width modulation index, a
discontinuous modulation angle corresponding to a discontinuous
modulation duration, and each phase difference between each of the
3 phase command voltages and each of 3 phases output currents of
the inverting module; and a controller configured for generating a
control signal based on a comparison between each pole command
voltage and a triangular carrier wave, wherein the control signal
controls upper and lower switching elements of each phase leg.
Inventors: |
LEE; Hak-Jun; (Anyang-si,
KR) |
|
Applicant: |
Name |
City |
State |
Country |
Type |
LSIS CO., LTD. |
Anyang-si |
|
KR |
|
|
Family ID: |
65724326 |
Appl. No.: |
16/295844 |
Filed: |
March 7, 2019 |
Current U.S.
Class: |
1/1 |
Current CPC
Class: |
H02M 1/12 20130101; H02M
7/5395 20130101; H02M 1/08 20130101; H02M 2001/0048 20130101; H02P
27/08 20130101; H02M 2001/0054 20130101; H02M 3/335 20130101; H02P
21/22 20160201; H02M 7/48 20130101; H02M 7/53875 20130101 |
International
Class: |
H02M 1/08 20060101
H02M001/08; H02M 7/48 20060101 H02M007/48; H02P 27/08 20060101
H02P027/08; H02P 21/22 20060101 H02P021/22 |
Foreign Application Data
Date |
Code |
Application Number |
May 31, 2018 |
KR |
10-2018-0062310 |
Claims
1. A device for controlling an inverter, wherein the device
achieves a minimum switching loss in a discontinuous modulation
duration regardless of a power factor, wherein the inverter
includes an inverting module for converting a direct current (DC)
stage voltage to an alternate current (AC) voltage, wherein the
inverting module includes 3 legs corresponding to 3 phases, wherein
each leg has upper and lower switching elements, the device being
characterized in that the device includes: a command voltage
transform unit and configured for transforming each of 3 phases
command voltages into each of pole command voltages using the DC
stage voltage, a pulse width modulation index, a discontinuous
modulation angle corresponding to a discontinuous modulation
duration, and each phase difference between each of the 3 phase
command voltages and each of 3 phases output currents of the
inverting module; and a controller configured for generating a
control signal based on a comparison between each pole command
voltage and a triangular carrier wave, wherein the control signal
controls upper and lower switching elements of each phase leg.
2. The device of claim 1, wherein the command voltage transform
unit includes: an offset command voltage calculation unit for
calculating an offset command voltage from the phase command
voltages, the DC stage voltage, the pulse width modulation index,
the discontinuous modulation angle, and each phase difference; and
a pole command voltage calculation unit for calculating each pole
command voltage from each phase command voltage and the offset
command voltage.
3. The device of claim 2, wherein the offset command voltage
calculation unit 10 includes: a first coordinate transform unit for
transforming the 3 phases command voltages to stationary reference
frame-based d and q axis command voltages; an angular transform
unit for transforming each phase-difference between each phase
command voltage and each output current into each virtual
phase-difference; a rotation transform unit for
rotationally-transforming the stationary reference frame-based d
and q axis command voltages by each virtual phase-difference; a
second coordinate transform unit for transforming the
rotation-transformed d and q axis command voltages into virtual
3-phases command voltages; and an offset command voltage generation
unit for generating the offset command voltage using the phase
command voltages, the DC stage voltage, the pulse width modulation
index, the discontinuous modulation angle, and the virtual phase
command voltages.
4. The device of claim 3, wherein the offset command voltage
generation unit includes: a first determination unit for
determining a maximum value and a minimum value among the actual 3
phases command voltages; a second determination unit for
determining a maximum value and a minimum value among the virtual 3
phases command voltages; and a third determination unit for
determining the offset command voltage using the DC stage voltage,
the pulse width modulation index, the discontinuous modulation
angle, the maximum and minimum values among the actual phase
command voltages, and the maximum and minimum values among the
virtual phase command voltages.
5. The device of claim 4, wherein the third determination unit is
configured for determining the offset command voltage using a
following equation: { v sn * = V d c 2 - v max * , ( if , v max V
> k V d c 2 ) v sn * = - V d c 2 - v min * , ( if , v min V <
- k V d c 2 ) v sn * = - v max * + v min * 2 , ( if , v max V <
k V d c 2 , v min V > - k V d c 2 ) ##EQU00039## where
.nu..sub.sn* denotes the offset command voltage, V.sub.dc denotes
the DC stage voltage, k is defined as MI cos .theta..sub.D, MI
denotes the pulse width modulation index, .theta..sub.D denotes the
discontinuous modulation angle, .nu..sub.max* and .nu..sub.min*
denote the maximum and minimum values among the actual phase
command voltages respectively, and .nu..sub.max.sup.V and
.nu..sub.min.sup.V denote the maximum and minimum values among the
virtual phase command voltages respectively.
6. The device of claim 3, wherein the phase-difference .PHI. has a
relationship 0 .ltoreq. .phi. < .pi. 3 - .theta. D ,
##EQU00040## the angular transform unit is configured for
determining the virtual phase-difference .PHI..sub.V to have a
relationship .PHI..sub.V=.PHI..
7. The device of claim 3, wherein the phase-difference .PHI. has a
relationship .pi. 3 - .theta. D .ltoreq. .phi. < .pi. 2 -
.theta. D , ##EQU00041## the angular transform unit 13 is
configured for determining the virtual phase-difference .PHI..sub.V
to have a relationship .phi. V = .pi. 3 - .theta. D .
##EQU00042##
8. The device of claim 3, wherein the phase-difference .PHI. has a
relationship .pi. 2 - .theta. D .ltoreq. .phi. < .pi. 2 ,
##EQU00043## the angular transform unit 13 is configured for
determining the virtual phase-difference .PHI..sub.V to have a
relationship .phi. V = .phi. - .pi. 6 . ##EQU00044##
9. The device of claim 3, wherein the controller includes: a
comparison unit configured for: comparing each polar command
voltage with a triangular carrier wave; when a difference between
each polar command voltage and the triangular carrier wave is
positive or zero, outputting as a switching function of an upper
switching element of each leg; or when a difference between each
polar command voltage and the triangular carrier wave is negative,
outputting as a switching function of an upper switching element of
each leg; and an inversion unit configured for inverting the output
of the comparison unit and for outputting the inverted output as a
switching function of a lower switching element of each leg.
10. The device of claim 9, wherein a period of the triangular
carrier wave corresponds to a switching frequency, and maximum and
minimum values of the triangular carrier wave are V d c 2 and - V d
c 2 ##EQU00045## respectively.
Description
CROSS-REFERENCE TO RELATED APPLICATION
[0001] Pursuant to 35 U.S.C. .sctn. 119(a), this application claims
the benefit of earlier filing date and right of priority to Korean
Application No. 10-2018-0062310, filed on May 31, 2018, in the
Korean Intellectual Property Office, the disclosure of which is
incorporated herein in its entirety by reference.
TECHNICAL FIELD
[0002] The present disclosure relates to a device for controlling
an inverter.
BACKGROUND
[0003] With a development of a power semiconductor technology, a
power of VVVF (Variable Voltage and Variable Frequency) may be
relatively easily implemented using a power element capable of
high-speed switching. An example of a circuit for generating the
VVVF may include a voltage-type inverter which convert a DC voltage
as an input to an AC variable voltage as an output.
[0004] The voltage-type inverter may be mainly used in energy
storage system (ESS), photo-voltaic (PV) inverter, and motor drive
technology.
[0005] Various pulse width modulation schemes have been developed
for an application of such voltage type inverters. The pulse width
modulation schemes includes a sinusoidal pulse width modulation
(SPWM) and a space vector pulse width modulation (SVPWM). The above
SPWM and SVPWM may belong to a continuous pulse width modulation
scheme.
[0006] A discontinuous pulse width modulation scheme is also used
to reduce a switching loss in a power semiconductor. A 60.degree.
discontinuous pulse width modulation (DPWM) scheme is the most
representative discontinuous pulse width modulation scheme. This
discontinuous pulse width modulation scheme may be implemented by
appropriately selecting an offset voltage in a pulse width
modulation scheme using an offset voltage and a triangular carrier
wave comparison PWM.
[0007] Alternatively, the discontinuous pulse width modulation
scheme may include a discontinuous pulse width modulation scheme of
adjusting a discontinuous pulse width modulation period. This
scheme may achieve an optimal current total harmonic distortion
(THD) and loss at each operating point by freely adjusting a
duration of the discontinuous pulse width modulation period. This
scheme always has a minimum loss when a power factor is 1. Thus, it
is necessary to have a minimum loss regardless of the power
factor.
SUMMARY
[0008] The present disclosure aims to provide an
inverter-controlling device which allows a user to control a
trade-off between a switching loss and a current THD via adjustment
of a discontinuous modulation duration, such that at a given
discontinuous modulation duration, there is always a minimum loss
regardless of a power factor.
[0009] The purpose of the present disclosure is not limited to the
above-mentioned purposes. Other purposes and advantages of the
present disclosure that are not mentioned may be understood by
following descriptions, and will be more clearly understood by
embodiments of the present disclosure. It is to be further
understood that the purposes and advantages of the present
disclosure may be realized and attained by means of means and
combinations thereof recited in the appended claims.
[0010] In one aspect of the present disclosure, there is provided a
device for controlling an inverter, wherein the device achieves a
minimum switching loss in a discontinuous modulation duration
regardless of a power factor, wherein the inverter includes an
inverting module for converting a direct current (DC) stage voltage
to an alternate current (AC) voltage, wherein the inverting module
includes 3 legs corresponding to 3 phases, wherein each leg has
upper and lower switching elements, the device being characterized
in that the device includes: a command voltage transform unit
configured for transforming each of 3 phases command voltages into
each of pole command voltages using the DC stage voltage, a pulse
width modulation index, a discontinuous modulation angle
corresponding to a discontinuous modulation duration, and each
phase difference between each of the 3 phase command voltages and
each of 3 phases output currents of the inverting module; and a
controller configured for generating a control signal based on a
comparison between each pole command voltage and a triangular
carrier wave, wherein the control signal controls upper and lower
switching elements of each phase leg.
[0011] In one implementation, the command voltage transform unit
includes: an offset command voltage calculation unit for
calculating an offset command voltage from the phase command
voltages, the DC stage voltage, the pulse width modulation index,
the discontinuous modulation angle, and each phase difference; and
a pole command voltage calculation unit for calculating each pole
command voltage from each phase command voltage and the offset
command voltage.
[0012] In one implementation, the offset command voltage
calculation unit includes: a first coordinate transform unit for
transforming the 3 phases command voltages to stationary reference
frame-based d and q axis command voltages; an angular transform
unit for transforming each phase-difference between each phase
command voltage and each output current into each virtual
phase-difference; a rotation transform unit for
rotationally-transforming the stationary reference frame-based d
and q axis command voltages by each virtual phase-difference; a
second coordinate transform unit for transforming the
rotation-transformed d and q axis command voltages into virtual
3-phases command voltages; and an offset command voltage generation
unit for generating the offset command voltage using the phase
command voltages, the DC stage voltage, the pulse width modulation
index, the discontinuous modulation angle, and the virtual phase
command voltages.
[0013] In one implementation, the offset command voltage generation
unit includes: a first determination unit for determining a maximum
value and a minimum value among the actual 3 phases command
voltages; a second determination unit for determining a maximum
value and a minimum value among the virtual 3 phases command
voltages; and a third determination unit for determining the offset
command voltage using the DC stage voltage, the pulse width
modulation index, the discontinuous modulation angle, the maximum
and minimum values among the actual phase command voltages, and the
maximum and minimum values among the virtual phase command
voltages.
[0014] In one implementation, the third determination unit is
configured for determining the offset command voltage using a
following equation:
{ v sn * = V dc 2 - v max * , ( if , v max V > k V dc 2 ) v sn *
= - V dc 2 - v min * , ( if , v min V < - k V dc 2 ) v sn * = -
v max * + v min * 2 , ( if , v max V < k V dc 2 , v min V > -
k V dc 2 ) ##EQU00001##
[0015] where .nu..sub.sn* denotes the offset command voltage,
V.sub.dc denotes the DC stage voltage, k is defined as MI cos
.theta..sub.D, MI denotes the pulse width modulation index,
.theta..sub.D denotes the discontinuous modulation angle,
.nu..sub.max* and .nu..sub.min* denote the maximum and minimum
values among the actual phase command voltages respectively, and
.nu..sub.max.sup.V and .nu..sub.min.sup.V denote the maximum and
minimum values among the virtual phase command voltages
respectively.
[0016] In one implementation, the phase-difference .PHI. has a
relationship
0 .ltoreq. .phi. < .pi. 3 - .theta. D , ##EQU00002##
the angular transform unit is configured for determining the
virtual phase-difference .PHI..sub.V to have a relationship
.PHI..sub.V=.PHI..
[0017] In one implementation, the phase-difference .PHI. has a
relationship
.pi. 3 - .theta. D .ltoreq. .phi. < .pi. 2 - .theta. D ,
##EQU00003##
the angular transform unit is configured for determining the
virtual phase-difference .PHI..sub.V to have a relationship
.phi. V = .pi. 3 - .theta. D . ##EQU00004##
[0018] In one implementation, the phase-difference .PHI. has a
relationship
.pi. 2 - .theta. D .ltoreq. .phi. < .pi. 2 , ##EQU00005##
the angular transform unit is configured for determining the
virtual phase-difference .PHI..sub.V to have a relationship
.phi. V = .phi. - .pi. 6 . ##EQU00006##
[0019] In one implementation, the controller includes: a comparison
unit configured for: comparing each polar command voltage with a
triangular carrier wave; when a difference between each polar
command voltage and the triangular carrier wave is positive or
zero, outputting 1 as a switching function of an upper switching
element of each leg; or when a difference between each polar
command voltage and the triangular carrier wave is negative,
outputting 0 as a switching function of an upper switching element
of each leg; and an inversion unit configured for inverting the
output of the comparison unit and for outputting the inverted
output as a switching function of a lower switching element of each
leg.
[0020] In one implementation, a period of the triangular carrier
wave corresponds to a switching frequency, and maximum and minimum
values of the triangular carrier wave are
V dc 2 and - V dc 2 ##EQU00007##
respectively.
[0021] The control device in accordance with the present disclosure
uses the phase-difference between the command voltage and output
current, and the discontinuous modulation angles that are used to
control the discontinuous pulse width modulation duration. Further,
the control device in accordance with the present disclosure may
use the generated virtual command voltage, thereby to always
exhibit the possible minimum loss at a given discontinuous pulse
width modulation duration regardless of the power factor.
[0022] According to the present disclosure, the virtual phase
command voltage may be generated via the rotational transformation
of the actual phase command voltage. The rotation angle used for
this rotation transformation may be determined using the
phase-difference between the command voltage and the output current
and the discontinuous modulation angle. In this way, the pulse
width modulation may be performed using the virtual phase command
voltage, the actual phase command voltage and the discontinuous
modulation angle. The discontinuous modulation duration may be
adjusted to properly control the trade-off between the switching
loss and current THD. In addition, the present scheme always result
in a minimum loss in a given discontinuous modulation duration
regardless of the power factor.
[0023] Further specific effects of the present disclosure as well
as the effects as described above will be described in conduction
with illustrations of specific details for carrying out the
invention.
BRIEF DESCRIPTION OF THE DRAWINGS
[0024] FIG. 1 shows a schematic circuit diagram of a 2-level
3-phase voltage type inverter.
[0025] FIG. 2 shows an example to illustrate a triangular carrier
wave comparison-based PWM controlled by a PWM controller in FIG.
1.
[0026] FIG. 3 shows an example of conversion of an output phase
voltage according to a switching function into a space vector.
[0027] FIG. 4 shows an operation of an a-phase based 60-degree
discontinuous pulse width modulation scheme when a phase command
voltage is expressed as a command voltage vector V* in a space
vector system.
[0028] FIG. 5 is an exemplary diagram for illustrating another
implementation of the discontinuous pulse width modulation
scheme.
[0029] FIG. 6 shows an example to illustrate ADPWM (Adjustable
Discontinuous PWM) as another discontinuous pulse width modulation
scheme.
[0030] FIG. 7 shows a circuit configuration for an implementation
of the ADPWM.
[0031] FIG. 8 is an example of converting a phase command voltage
to a pole command voltage in an inverter-controlling device
according to one embodiment of the present disclosure.
[0032] FIG. 9 shows a detailed configuration of an offset command
voltage calculation unit in FIG. 8.
[0033] FIG. 10 is a detailed configuration diagram of an embodiment
of an offset command voltage generation unit of FIG. 9.
[0034] FIG. 11 is an example diagram for illustrating a relation
between a phase difference .PHI. between a command voltage and a
current and a virtual phase-difference .PHI..sub.V as an angular
information used for generation of a virtual phase command voltage
according to one embodiment of the present disclosure.
[0035] FIG. 12 is an example diagram to illustrate an operation of
an angular transform unit in FIG. 9.
[0036] FIG. 13 is an example diagram for illustrating a switching
loss in an inverter-controlling device in accordance with one
embodiment of the present disclosure.
DETAILED DESCRIPTION
[0037] Hereinafter, a device for controlling an inverter in
accordance with the present disclosure will be described with
reference to the accompanying drawings.
[0038] For simplicity and clarity of illustration, elements in the
figures are not necessarily drawn to scale. The same reference
numbers in different figures denote the same or similar elements,
and as such perform similar functionality. Further, descriptions
and details of well-known steps and elements are omitted for
simplicity of the description. Furthermore, in the following
detailed description of the present disclosure, numerous specific
details are set forth in order to provide a thorough understanding
of the present disclosure. However, it will be understood that the
present disclosure may be practiced without these specific details.
In other instances, well-known methods, procedures, components, and
circuits have not been described in detail so as not to
unnecessarily obscure aspects of the present disclosure.
Embodiments are described in sufficient detail to enable those
skilled in the art in the art to easily practice the technical idea
of the present disclosure. It is intended to cover alternatives,
modifications, and equivalents as may be included within the spirit
and scope of the present disclosure as defined by the appended
claims.
[0039] Unless defined otherwise, all terms used herein have the
same meaning as commonly understood by one of ordinary skill in the
art. When the terms used herein are in conflict with a general
meaning of the term, the meaning of the term is in accordance with
a definition used herein.
[0040] The terminology used herein is for the purpose of describing
particular embodiments only and is not intended to be limiting of
the present disclosure. As used herein, the singular forms "a" and
"an" are intended to include the plural forms as well, unless the
context clearly indicates otherwise. It will be further understood
that the terms "comprises", "comprising", "includes", and
"including" when used in this specification, specify the presence
of the stated features, integers, operations, elements, and/or
components, but do not preclude the presence or addition of one or
more other features, integers, operations, elements, components,
and/or portions thereof. As used herein, the term "and/or" includes
any and all combinations of one or more of the associated listed
items. Expression such as "at least one of" when preceding a list
of elements may modify the entire list of elements and may not
modify the individual elements of the list.
[0041] It will be understood that, although the terms "first",
"second", "third", and so on may be used herein to describe various
elements, components, regions, layers and/or sections, these
elements, components, regions, layers and/or sections should not be
limited by these terms. These terms are used to distinguish one
element, component, region, layer or section from another element,
component, region, layer or section. Thus, a first element,
component, region, layer or section described below could be termed
a second element, component, region, layer or section, without
departing from the spirit and scope of the present disclosure.
[0042] In addition, it will also be understood that when a first
element or layer is referred to as being present "on" a second
element or layer, the first element may be disposed directly on the
second element or may be disposed indirectly on the second element
with a third element or layer being disposed between the first and
second elements or layers. It will be understood that when an
element or layer is referred to as being "connected to", or
"coupled to" another element or layer, it can be directly on,
connected to, or coupled to the other element or layer, or one or
more intervening elements or layers may be present. In addition, it
will also be understood that when an element or layer is referred
to as being "between" two elements or layers, it can be the only
element or layer between the two elements or layers, or one or more
intervening elements or layers may also be present.
[0043] Hereinafter, an inverter-controlling device and method
according to an embodiment of the present disclosure will be
described with reference to FIGS. 2A to 5.
[0044] FIG. 1 is a schematic circuit diagram of a 2-level 3-phase
voltage type inverter, which is an example of an inverter used for
the energy storage system (ESS), photo-voltaic (PV) inverter, and
motor drive technology.
[0045] The inverter 100 may include a direct current (DC) stage 101
and an inverting module 102. n of the DC stage 101 represents a
virtual DC stage neutral point position. The inverting module 102
includes three-phases power switches. S.sub.a, S.sub.b, and S.sub.c
of the inverting module 102 refer to switching functions of
three-phase power switches, respectively. S.sub.a=1 means that an
a-phase upper switch electrically conducts, and S.sub.a=0 means
that an a-phase lower switch electrically conducts. That is,
S.sub.a and S.sub.a have a complementary relationship. This may be
equally applied to S.sub.b and S.sub.c. An alternating voltage from
the inverting module 102 is transferred to a load 200 such as a
motor.
[0046] Command voltages of 3 phases may be input to a pulse width
modulation (PWM) controller 110. The PWM controller 110 determines
a switching function to be applied to the inverting module 102 and
provides the determined switching function to the inverting module
102.
[0047] A triangular carrier wave comparison-based modulation as
controlled by the PWM controller 110 will be described with
reference to FIG. 2.
[0048] FIG. 2 shows an example to illustrate a triangular carrier
wave comparison-based PWM controlled by a PWM controller in FIG. 1.
In FIG. 2, (a) is an example diagram to illustrate generation of
pole voltages, and (b) shows a triangular carrier wave
comparison-based PWM.
[0049] An offset command voltage calculation unit 111 calculates an
offset command voltage .nu..sub.sn* using three-phase phase command
voltages 2A. A pole command voltage calculation unit 112 calculates
pole command voltages 2B using the three phase command voltages 2A
and the offset command voltage .nu..sub.sn*. This process may be
expressed as Equation 1 as follows:
.nu..sub.an*=.nu..sub.as*+.nu..sub.sn*
.nu..sub.bn*=.nu..sub.bs*+.nu..sub.sn*
.nu..sub.cn*=.nu..sub.cs*+.nu..sub.sn* [Equation 1]
[0050] The offset voltage is a component that is common to the
three-phase pole voltages. Since the offset voltage means a
zero-sequence voltage, the offset voltage does not affect synthesis
of an inter-line voltage.
[0051] Referring to (b) in FIG. 2, a period of a triangular carrier
wave 2C, which is to be compared with the pole command voltages 2B
corresponds to a switching frequency Maximum and minimum values of
the carrier wave 2C are
V dc 2 and - V dc 2 ##EQU00008##
respectively.
[0052] A comparison unit 113 compares the pole command voltages 2B
with the triangular carrier wave 2C. When, as a result of
comparison, a difference between each of the pole command voltages
2B and the triangular carrier wave 2C is positive or zero, the
switching function may be output as 1. When, as a result of
comparison, a difference between each of the pole command voltages
2B and the triangular carrier wave 2C is negative, the switching
function may be output as 0.
[0053] When we define the triangular carrier wave as .nu..sub.tri,
each switching function is expressed as each of following Equations
2, 3 and 4:
{ S a = 1 v an * .gtoreq. v tri S a = 0 v an * < v tri [
Equation 2 ] { S b = 1 v bn * .gtoreq. v tri S b = 0 v bn * < v
tri [ Equation 3 ] { S c = 1 v cn * .gtoreq. v tri S c = 0 v cn *
< v tri . [ Equation 4 ] ##EQU00009##
[0054] An inversion unit 114 may obtain a switching function of
each lower switching element of the inverting module 102. Since
each lower switching element operates complementarily with each
upper switching element, the switching function may be obtained by
inverting an output of the comparison unit 113.
[0055] FIG. 3 shows a diagram of conversion of an output phase
voltage according to a switching function into a space vector. The
output phase voltages according to the switching functions may be
expressed as Equation 5 below:
V as = V dc 3 ( 2 S a - S b - S c ) V bs = V dc 3 ( 2 S b - S c - S
a ) V cs = V dc 3 ( 2 S c - S a - S b ) [ Equation 5 ]
##EQU00010##
[0056] The output phase voltages are composed of a total of 8
voltages V.sub.0 to V.sub.7 based on the switching functions. For
voltage vectors V.sub.0 and V.sub.7, an voltage is not output.
Thus, the voltage vectors V.sub.0 and V.sub.7 are defined as zero
voltage vectors. On the other hand, for voltage vectors V.sub.1 to
V.sub.6, a phase difference between adjacent voltage vectors is 60
degrees. Each of voltage vectors V.sub.1 to V.sub.6 has a fixed
magnitude of 2/3 V.sub.dc. Thus, voltage vectors V.sub.1 to V.sub.6
are defined as effective voltage vectors. The phase command
voltages 2A is modulated to an actual voltage via appropriate
synthesis between the effective voltage vectors and the zero
voltage vectors.
[0057] The offset command voltage calculated by the offset command
voltage calculation unit 111 of FIG. 2 may have quite various
types.
[0058] An offset command voltage in a sinusoidal pulse width
modulation scheme (SPWM) is expressed by Equation 6 below:
.nu..sub.sn*=0 Equation 61
[0059] In a space vector pulse width modulation scheme (SVPWM), an
offset command voltage may be expressed as a following Equation
7:
v sn * = - v max + v min 2 [ Equation 7 ] ##EQU00011##
[0060] where V.sub.max refers to the largest phase command voltage
among the three phase command voltages, and V.sub.min refers to the
smallest phase command voltage among the three phase command
voltages.
[0061] In one example, the offset command voltage of each of
Equation 6 and Equation 7 is based on a continuous pulse width
modulation scheme in which the switching functions of all 3 phases
change over a single carrier wave period.
[0062] A pulse width modulation scheme in which a switching
function of one phase does not change in order to reduce a
switching loss is referred to as a discontinuous pulse width
modulation scheme. A typical discontinuous pulse width modulation
scheme is as follows.
[0063] First, it may be assumed that the phase command voltage is
defined as Equation 8 below, and a phase current is defined as
Equation 9 below:
.nu..sub.xs*=V.sub.m cos .theta. [Equation 8]
i.sub.xs=I.sub.m cos(.theta.-.PHI.) [Equation 9]
[0064] In this connection, a subscript `xs` means a specific phase.
For example, as for an a-phase, xs becomes as; xs becomes bs for a
b-phase; and xs becomes cs for a c-phase. .theta. denotes an AC
electric angle. .PHI. denotes a phase-difference between the
voltage and current. Further, V.sub.m and I.sub.m refer to a peak
value of the phase command voltage and the peak value of the
current, respectively.
[0065] A typical discontinuous pulse width modulation scheme is
60.degree. discontinuous pulse width modulation scheme (DPWM), in
which when a period of a AC frequency is 360 degrees, a switching
discontinuous duration from an angular point corresponding to the
maximum value of the phase command voltage is 60.degree.. An offset
command voltage in the 60.degree. discontinuous pulse width
modulation scheme may be given by a following Equation 10. This
DPWM is a pulse width modulation scheme in which the switching loss
is minimized when the phase-difference .PHI. between the phase
command voltage and phase current is 0.degree..
{ v sn * = V dc 2 - v max ( if , v max + v min .gtoreq. 0 ) v sn *
= - V dc 2 - v min ( if , v max + v min < 0 ) [ Equation 10 ]
##EQU00012##
[0066] FIG. 4 shows an operation of an a-phase based 60-degree
discontinuous pulse width modulation scheme when a phase command
voltage is expressed as a command voltage vector V* in a space
vector system.
[0067] It may be seen from a shaded area of FIG. 4 that when an
a-phase command voltage is positive, and an absolute value thereof
is a maximum value among absolute values of the three phases
command voltages, an a-phase switching function S.sub.a becomes 1
and thus an a-phase switching element is always in an on state for
a certain duration. To the contrary, it may be seen from a shaded
area of FIG. 4 that when an a-phase command voltage is negative,
and an absolute value thereof is a maximum value among absolute
values of the three phases command voltages, the a-phase switching
function S.sub.a becomes 0 and thus the a-phase switching element
is always in an off state for a certain duration.
[0068] This discontinuous pulse width modulation scheme may reduce
the switching loss, but may have a disadvantage that the total
harmonic distortion (THD) of the current increases. The continuous
pulse width modulation scheme has a lower current THD than that of
the discontinuous pulse width modulation scheme. However, the
continuous pulse width modulation scheme has a drawback that the
switching loss increases.
[0069] Further, when, conventionally, the discontinuous pulse width
modulation scheme using an offset command voltage is used, a
discontinuous pulse width modulation duration is always fixed to
120.degree., which is 1/3 of a single period of a fundamental wave.
As a result, when a pulse width modulation index is low and when
the discontinuous pulse width modulation is applied, the current
THD is very large.
[0070] In one example, an adjustment of the discontinuous
modulation duration provides for a degree of freedom for proper
selection between the switching loss and current THD. This reduces
the switching loss in a region of a low pulse width modulation
index compared to the continuous pulse width modulation scheme.
Further, a method of reducing the current THD compared to the
discontinuous pulse width modulation scheme.
[0071] FIG. 5 is an exemplary diagram for illustrating another
implementation of the discontinuous pulse width modulation scheme.
In FIG. 5, reference numerals 5A, 5B, and 5C refer to a, b, and
c-phases command voltages .nu..sub.as*, .nu..sub.bs* and
.nu..sub.cs* respectively. A reference numeral 5D represents a peak
value of each phase command voltage. Each of 5Ds of the 3 phases
command voltages is equal to MI.sup.V.sup.dc.sub.2 when the pulse
width modulation index is defined as MI.
[0072] The pulse width modulation index is defined as a following
Equation 11:
MI = V m V dc / 2 [ Equation 11 ] ##EQU00013##
[0073] A reference numeral 5E in FIG. 5 represents a magnitude of a
voltage at which the discontinuous pulse width modulation begins.
The magnitude 5E of the voltage at which the discontinuous pulse
width modulation begins is defined as
MI V dc 2 cos .pi. 6 . ##EQU00014##
[0074] Thus, when the a-phase command voltage 5A is greater than
the 5E, the a-phase switching function is always 1. When the
a-phase command voltage 5A is smaller than a negative 5E, the
a-phase switching function is always 0. This may be equally applied
to the b-phase command voltage 5B and the c-phase command voltage
5C.
[0075] Thus, the implementation of the 60.degree. discontinuous
pulse width modulation scheme may be redefined as a following
Equation 12:
{ v sn * = V dc 2 - v max ( if , v max > k V dc 2 ) v sn * = - V
dc 2 - v min ( if , v min < - k V dc 2 ) [ Equation 12 ]
##EQU00015##
[0076] where, k is defined as
MI cos .pi. 6 . ##EQU00016##
[0077] FIG. 6 shows an example to illustrate ADPWM (Adjustable
Discontinuous PWM) as another discontinuous pulse width modulation
scheme.
[0078] In FIG. 6, reference numerals 6A, 6B and 6C denote a, b,
c-phases command voltages .nu..sub.as*, .nu..sub.bs* and
.nu..sub.cs* respectively. A reference numeral 6D represents a peak
value of each phase command voltage. Each of 6Ds of the 3 phases
command voltages is equal to MI.sup.V.sup.dc.sub.2 when the pulse
width modulation index is defined as MI. A reference numeral 6E in
FIG. 6 represents a magnitude of a voltage at which the
discontinuous pulse width modulation begins. The magnitude 6E of
the voltage at which the discontinuous pulse width modulation
begins is defined as
MI V d c 2 cos .theta. D . ##EQU00017##
In this connection, .theta..sub.D refers to a discontinuous pulse
width modulation angle representing a length of a discontinuous
pulse width modulation duration. When .theta..sub.D is zero, the
space vector pulse width modulation as a continuous pulse width
modulation scheme is achieved. When .theta..sub.D is 30.degree.,
the 60.degree. discontinuous pulse width modulation scheme as
described above is achieved.
[0079] Further, in FIG. 6, a reference numeral 6F means a duration
during which a corresponding phase switching element does not
perform a switching operation. In FIG. 6, a reference numeral 6G
means a duration during which a corresponding phase switching
element performs a normal switching operation. When the a-phase
command voltage 6A is greater than 6E, then the a-phase switching
function is always 1, so that the a-phase switching element
performs a switching operation for the duration 6F for which the
a-phase switching element does not perform the switching operation.
When the a-phase command voltage 6A is smaller than a negative 6E,
then the a-phase switching function is always 0, so that the
a-phase switching element performs a switching operation for the
duration 6F for which the a-phase switching element does not
perform the switching operation. This may be equally applied to the
b-phase command voltage 6B and the c-phase command voltage 6C.
[0080] Thus, the implementation of the ADPWM may be redefined as
Equation 13 below:
[ Equation 13 ] ##EQU00018## { v sn * = V d c 2 - v max ( if , v
max > k V d c 2 ) v sn * = - V d c 2 - v min ( if , v min < -
k V d c 2 ) v sn * = - v max + v min 2 ( if , v max < k V d c 2
, v min > - k V d c 2 ) ##EQU00018.2##
[0081] where, k is defined as MI cos .theta..sub.D.
[0082] FIG. 7 shows a configuration diagram of an implementation of
the ADPWM.
[0083] For the implementation of the ADPWM, an offset command
voltage calculation unit 711 receives 3 phases command voltages 7A,
a DC stage voltage V.sub.dc and a k value defined in the above
Equation 13 and then calculates an offset command voltage. A pole
command voltage calculation unit 712 adds the offset command
voltage V*.sub.sn to the phase command voltages 7A to calculate
three-phases pole command voltages 7B.
[0084] Although the discontinuous pulse width modulation scheme as
described above may reduce the switching loss, the discontinuous
pulse width modulation scheme has the disadvantage of increasing
the THD of the current. To overcome this disadvantage, the user may
appropriately control a trade-off between the switching loss and
the current THD by adjusting the discontinuous modulation
duration.
[0085] Especially when the pulse width modulation index MI is
small, the discontinuous pulse width modulation scheme may be used
to reduce the switching loss. In this connection, when using the
discontinuous pulse width modulation scheme, the current THD must
deteriorate. However, a conventional method may reduce the
switching loss in a region of a low modulation index MI as compared
to the continuous voltage modulation scheme. Using the conventional
method, the current THD may be reduced compared to the
discontinuous voltage modulation scheme.
[0086] The conventional method as described above has a problem of
having a minimum loss only in a state where the power factor is 1
in which the phase difference between the voltage and the current
is 0.degree..
[0087] In accordance with the present disclosure, the user may
appropriately control the trade-off between the switching loss and
the current THD by adjusting the discontinuous modulation duration.
Further, in accordance with the present disclosure, an
inverter-controlling device may always achieve a minimum loss for a
certain discontinuous modulation duration regardless of the power
factor.
[0088] The inverter-controlling device in accordance with the
present disclosure is applied to a two-level three-phases voltage
type inverter used for the energy storage system (ESS),
photo-voltaic (PV) inverter, and motor drive technology, as shown
in FIG. 1. The inverter-controlling device in accordance with the
present disclosure is based on a triangular wave pulse width
modulation scheme using an offset voltage. Thus, the configuration
of FIG. 2 in which the pole command voltages and the triangular
carrier wave are compared to each other is applied equally to the
present disclosure.
[0089] In the conventional ADPWM, both switching discontinuous
angular durations are present around an angular point corresponding
to a maximum value of each phase command voltage. Each of both
switching discontinuous angular durations is .theta..sub.D. In this
scheme, the switching loss is minimized when the phase-difference
.PHI. between each phase command voltage and each phase current is
zero. That is, both switching discontinuous angular durations
occurs around an angular point corresponding to a maximum value of
each phase current Each of both switching discontinuous angular
durations is .theta..sub.D. Therefore, this scheme has a minimum
loss compared to other discontinuous pulse width modulation
schemes.
[0090] One embodiment of the present disclosure is based on this
scheme. In one embodiment of the present disclosure, a minimal loss
may be achieved using a virtual command voltage in spite of a
non-zero phase-difference between the actual command voltage and
actual output current. That is, regardless of the power factor, the
minimum loss may occur at a certain discontinuous modulation angle
.theta..sub.D. One embodiment of the present disclosure may be
implemented by applying the ADPWM based on the virtual command
voltage such that a phase of the virtual command voltage coincides
with a phase of the current as much as possible.
[0091] FIG. 8 shows an example configuration of converting the
phase command voltage to the pole command voltage in the
inverter-controlling device in accordance with an embodiment of the
present disclosure.
[0092] As shown in FIG. 8, an inverter-controlling device in
accordance with an embodiment of the present disclosure may include
an offset command voltage calculation unit 10 and a pole command
voltage calculation unit 20.
[0093] The inverter-controlling device in accordance with an
embodiment of the present disclosure calculates an offset command
voltage with a minimal loss for the ADPWM. To this end, the offset
command voltage calculation unit 10 according to an embodiment of
the present disclosure uses phase voltages 8A of three phases, a DC
stage voltage V.sub.DC, the k value, a phase-difference .PHI.
between each phase command voltage and each phase inverter output
current to calculate each phase offset command voltage. In this
connection, the k value is defined as MI cos .theta..sub.D, the
pulse width modulation index is denoted as MI, and .theta..sub.D
refers to the discontinuous modulation angle which may control the
discontinuous modulation duration.
[0094] The pole command voltage calculation unit 20 may generate
each pole command voltage 8B by adding each offset command voltage
to each phase command voltage 8A.
[0095] FIG. 9 shows a detailed configuration of the offset command
voltage calculation unit 10 in FIG. 8.
[0096] As shown in FIG. 9, the offset command voltage calculation
unit 10 in accordance with an embodiment of the present disclosure
includes a first coordinate transform unit 11, a rotation transform
unit 12, an angular transform unit 13, a second coordinate
transform unit 14, and an offset command voltage generation unit
15.
[0097] The first coordinate transform unit 11 may transform a, b,
and c-phase variables into stationary reference frame d and q axis
variables and may be expressed as Equation 14 below.
2 3 ( 1 - 1 2 - 1 2 0 3 2 - 3 2 ) [ Equation 14 ] ##EQU00019##
[0098] Therefore, the 3-phase phase command voltages may be
transformed by the first coordinate transform unit 11 into the d
and q-axis command voltages as expressed in Equation 15 below:
( v ds * v qs * ) = 2 3 ( 1 - 1 2 - 1 2 0 3 2 - 3 2 ) ( v as * v bs
* v cs * ) [ Equation 15 ] ##EQU00020##
[0099] The rotation transform unit 12 may rotate the d and q axis
variables by .PHI..sub.V and may be expressed as Equation 16
below:
R ( .theta. ) - 1 = ( cos .theta. - sin .theta. sin .theta. cos
.theta. ) [ Equation 16 ] ##EQU00021##
[0100] Therefore, the command voltages based the d and q axes
passing through the first coordinate transform unit 11 may be
transformed, by the rotation transform unit 12, into rotated d and
q axis command voltages as expressed as Equation 17 below:
( v ds V v qs V ) = ( cos .phi. V - sin .phi. V sin .phi. V cos
.phi. V ) ( v ds * v qs * ) [ Equation 17 ] ##EQU00022##
[0101] The second coordinate transform unit 14 may
coordinate-transform the d and q axis variables to a, b, and
c-phase variables, and may be expressed as Equation 18 below:
( 1 0 - 1 2 3 2 - 1 2 - 3 2 ) [ Equation 18 ] ##EQU00023##
[0102] Thus, the rotated d and q axis command voltages
.nu..sub.ds.sup.V and .nu..sub.qs.sup.V from the rotation transform
unit 12 may be transformed by the second coordinate transform unit
14 into virtual phase command voltages .nu..sub.as.sup.V,
.nu..sub.bs.sup.V and .nu..sub.cs.sup.V as follows:
( v as V v bs V v cs V ) = ( 1 0 - 1 2 3 2 - 1 2 - 3 2 ) ( v ds V v
qs V ) [ Equation 19 ] ##EQU00024##
[0103] In summary, the 3 phases command voltages .nu..sub.as*,
.nu..sub.bs* and .nu..sub.cs* may be transformed, by the first
coordinate transform unit 11, rotation transform unit 12 and second
coordinate transform unit 13, into the virtual 3 phases command
voltages .nu..sub.as.sup.V, .nu..sub.bs.sup.V and .nu..sub.cs.sup.V
as expressed by a following Equation 20:
[ Equation 20 ] ##EQU00025## ( v as V v bs V v cs V ) = 2 3 ( 1 0 -
1 2 3 2 - 1 2 - 3 2 ) ( cos .phi. V - sin .phi. V sin .phi. V cos
.phi. V ) ( 1 - 1 2 - 1 2 0 3 2 - 3 2 ) ( v as * v bs * v cs * )
##EQU00025.2##
[0104] In this connection, the angular transform unit 13 may
receive the phase-difference .PHI. between the command voltage and
the output current to generate the angular information used for the
rotation transformation. This will be described in more detail
later.
[0105] The offset command voltage generation unit 15 may generate
the offset command voltages using the three phases command voltages
8A, the DC stage voltage, the k value, and the virtual three phases
command voltages.
[0106] FIG. 10 is a detailed block diagram of an embodiment of the
offset command voltage generation unit 15 of FIG. 9.
[0107] As shown in FIG. 9, the offset command voltage generation
unit 15 in accordance with one embodiment of the present disclosure
may include a first determination unit 31, a second determination
unit 32, and a third determination unit 33.
[0108] The first determination unit 31 may determine maximum and
minimum values among the three-phases command voltages as
follows:
.nu..sub.max*=max(.nu..sub.as*,.nu..sub.bs*,.nu..sub.cs*)
.nu..sub.min=min(.nu..sub.as*,.nu..sub.bs*,.nu..sub.cs*) [Equation
21]
[0109] The second determination unit 32 may determine maximum and
minimum values among the virtual three-phases command voltages as
follows:
.nu..sub.max.sup.V=max(.nu..sub.as.sup.V,.nu..sub.bs.sup.V,.nu..sub.cs.s-
up.V)
.nu..sub.min.sup.V=min(.nu..sub.as.sup.V,.nu..sub.bs.sup.V,.nu..sub.cs.s-
up.V) [Equation 22]
[0110] The third determination unit 33 may determine the offset
command voltages using the maximum and minimum values among the
three phase command voltages, the DC stage voltage V.sub.dc, the k
value, the maximum and minimum values among the virtual three-phase
phase command voltage using a following Equation 23:
[ Equation 23 ] ##EQU00026## { v sn * = V d c 2 - v max * , ( if ,
v max V > k V d c 2 ) v sn * = - V d c 2 - v min * , ( if , v
min V < - k V d c 2 ) v sn * = - v max * + v min * 2 , ( if , v
max V < k V d c 2 , v min V > - k V d c 2 )
##EQU00026.2##
[0111] Thus, the generation of the offset command voltage in
accordance with an embodiment of the present disclosure may use the
three-phase command voltages.
[0112] FIG. 11 is an example diagram for illustrating a relation
between a phase difference .PHI. between a command voltage and an
output current and a virtual phase-difference .PHI..sub.V as an
angular information used for generation of a virtual phase command
voltage according to one embodiment of the present disclosure. In
FIG. 11, (a) indicates a command voltage space vector V*, a virtual
command voltage space vector V.sup.V, and a current space vector i
when a phase-difference .PHI. between the command voltage and the
output current is
0 .ltoreq. .phi. < .pi. 3 - .theta. D . ##EQU00027##
[0113] As shown, both .theta..sub.D sized discontinuous modulation
durations are present around a current vector i Thus, the phase
difference between the current vector and the virtual command
voltage vector is 0. To this end, the actual phase-difference .PHI.
and a virtual phase-difference .PHI..sub.V used for the rotation
transformation are equal to each other. That is, when
0 .ltoreq. .phi. < .pi. 3 - .theta. D , .phi. V = .phi. .
##EQU00028##
[0114] In FIG. 11, (b) indicates a command voltage space vector V*,
a virtual command voltage space vector V.sup.V, and a current space
vector i when a phase-difference .PHI. between the command voltage
and the output current is
.pi. 3 - .theta. D .ltoreq. .phi. < .pi. 2 - .theta. D .
##EQU00029##
[0115] For the a-phase, a sector 1, sector 6, sector 3, and sector
4 only correspond to the discontinuous pulse width modulation
duration. Therefore, this may disallow the coincidence between the
phases of the virtual vector and the current vector. In order to
minimize the loss in the discontinuous modulation duration, a
difference between the phase of the virtual voltage vector and the
phase of the current vector should be minimized. To this end, since
an angular point in which
.phi. = .pi. 3 - .theta. D , ##EQU00030##
the phase .PHI..sub.V of the virtual command voltage vector V.sup.V
may be fixed to
.pi. 3 - .theta. D . ##EQU00031##
[0116] That is, when the phase-difference .PHI. between the phases
of the command voltage and the output current is
.pi. 3 - .theta. D .ltoreq. .phi. < .pi. 2 - .theta. D , .phi. V
= .pi. 3 - .theta. D . ##EQU00032##
[0117] In FIG. 11, (c) indicates a command voltage space vector V*,
a virtual command voltage space vector V.sup.V, and a current space
vector I when a phase-difference .PHI. between the command voltage
and the output current is
.pi. 2 - .theta. D .ltoreq. .phi. < .pi. 2 . ##EQU00033##
[0118] For the a-phase, a sector 1, sector 6, sector 3, and sector
4 only correspond to the discontinuous pulse width modulation
duration. Therefore, this may disallow the coincidence between the
phases of the virtual vector and the current vector. In order to
minimize the loss in the discontinuous modulation duration, a
difference between the phase of the virtual voltage vector and the
phase of the current vector should be minimized. To this end, the
phase-difference between the virtual command voltage vector V.sup.V
and the current vector is fixed to
.pi. 6 . ##EQU00034##
In this way, the switching loss can be minimized by locating the
discontinuous pulse width modulation duration appropriately into
the sector 1, sector 6, sector 3, and sector 4 based on the current
vector.
[0119] That is, when the phase-difference .PHI. between the command
voltage and the output current is
.pi. 2 - .theta. D .ltoreq. .phi. < .pi. 2 , .phi. V = .phi. -
.pi. 6 . ##EQU00035##
[0120] FIG. 12 is an example diagram to illustrate the operation of
the angular transform unit 13 of FIG. 9. FIG. 12 shows a
relationship between the phase-difference .PHI. between the command
voltage and the output current and the virtual phase-difference
.PHI..sub.V used for the generation of the virtual command
voltage.
[0121] As shown in FIG. 12, when
0 .ltoreq. .phi. < .pi. 3 - .theta. D , .phi. V = .phi. .
##EQU00036##
When
[0122] .pi. 3 - .theta. D .ltoreq. .phi. < .pi. 2 - .theta. D ,
.phi. V = .pi. 3 - .theta. D . ##EQU00037##
When
[0123] .pi. 2 - .theta. D .ltoreq. .phi. < .pi. 2 , .phi. V =
.phi. - .pi. 6 . ##EQU00038##
This may form an odd function.
[0124] FIG. 13 is an example graph for illustrating the switching
loss in the inverter-controlling device in accordance with one
embodiment of the present disclosure. A horizontal axis in FIG. 13
denotes the phase-difference between the command voltage and the
output current. A vertical axis represents the ratio of the
switching loss of the discontinuous pulse width modulation scheme
to the switching loss of the continuous pulse width modulation
scheme. That is, when the switching loss ratio is 1, the same
switching loss between the continuous and discontinuous pulse width
modulation schemes is exhibited. The ratio 0.5 means that the
switching loss of the discontinuous pulse width modulation scheme
is reduced by 50% compared with the continuous pulse width
modulation scheme.
[0125] In FIG. 13, reference numerals 13A and 13B indicate the
switching loss ratio according to the conventional ADPWM and the
switching loss ratio according to one embodiment of the present
disclosure respectively when a discontinuous modulation angle
.theta..sub.D thereof is set to 6.degree.. Reference numerals 14A
and 14B indicate the switching loss ratio according to the
conventional ADPWM and the switching loss ratio according to one
embodiment of the present disclosure respectively when a
discontinuous modulation angle .theta..sub.D thereof is set to
12.degree.. Reference numerals 15A and 15B indicate the switching
loss ratio according to the conventional ADPWM and the switching
loss ratio according to one embodiment of the present disclosure
respectively when a discontinuous modulation angle .theta..sub.D
thereof is set to 18.degree.. Reference numerals 16A and 16B
indicate the switching loss ratio according to the conventional
ADPWM and the switching loss ratio according to one embodiment of
the present disclosure respectively when a discontinuous modulation
angle .theta..sub.D thereof is set to 24.degree.. Reference
numerals 17A and 17B indicate the switching loss ratio according to
the conventional ADPWM and the switching loss ratio according to
one embodiment of the present disclosure respectively when a
discontinuous modulation angle .theta..sub.D thereof is set to
300.
[0126] As shown FIG. 13, the conventional ADPWM exhibits a minimum
loss when the phase difference .PHI. between the command voltage
and the output current is zero at a given discontinuous pulse width
modulation angle. However, the control device in accordance with
the present disclosure exhibits a possible minimum loss at a given
discontinuous pulse width modulation angle regardless of the
phase-difference .PHI..
[0127] Thus, the control device in accordance with the present
disclosure uses the phase-difference between the command voltage
and output current, and the discontinuous modulation angles that
are used to control the discontinuous pulse width modulation
duration. Further, the control device in accordance with the
present disclosure may use the generated virtual command voltage,
thereby to always exhibit the possible minimum loss at a given
discontinuous pulse width modulation duration regardless of the
power factor.
[0128] According to one embodiment of the present disclosure, the
virtual phase command voltage may be generated via the rotational
transformation of the actual phase command voltage. The rotation
angle used for this rotation transformation may be determined using
the phase-difference between the command voltage and the output
current and the discontinuous modulation angle. In this way, the
pulse width modulation may be performed using the virtual phase
command voltage, the actual phase command voltage and the
discontinuous modulation angle. The discontinuous modulation
duration may be adjusted to properly control the trade-off between
the switching loss and current THD. In addition, the present scheme
always result in a minimum loss in a given discontinuous modulation
duration regardless of the power factor.
[0129] It will be apparent to those skilled in the art that various
modifications and variations may be made in the present invention
without departing from the spirit of the present disclosure. The
technical scope of the present disclosure is not limited to the
contents described in the embodiments but should be determined by
the claims and equivalents thereof.
* * * * *