U.S. patent application number 14/046041 was filed with the patent office on 2015-01-01 for system and method for variable frequency clock generation.
This patent application is currently assigned to STMicroelectronics International N.V.. The applicant listed for this patent is STMicroelectronics (CROLLES 2) SAS, STMicroelectronics International N.V.. Invention is credited to Nitin AGARWAL, Kallol CHATTERJEE, Pierre DAUTRICHE, Nitin GUPTA, Junaid YOUSUF.
Application Number | 20150002197 14/046041 |
Document ID | / |
Family ID | 52114990 |
Filed Date | 2015-01-01 |
United States Patent
Application |
20150002197 |
Kind Code |
A1 |
CHATTERJEE; Kallol ; et
al. |
January 1, 2015 |
SYSTEM AND METHOD FOR VARIABLE FREQUENCY CLOCK GENERATION
Abstract
A variable frequency clock generator. In aspects, a clock
generator includes a droop detector circuit configured to monitor a
voltage supply to an integrated circuit. If the supply voltage
falls below a specific threshold, a droop voltage flag may be set
such that a frequency-locked loop is triggered into a droop voltage
mode for handling the voltage droop at the supply voltage. In
response, a current control signal that is input to an oscillator
that generates a system clock signal is reduced by sinking current
away from the current control signal to the oscillator. This
results in an immediate reduction on the system clock frequency.
Such a state remains until the voltage droop has dissipated when
the current path is removed for sinking some of the current.
Inventors: |
CHATTERJEE; Kallol;
(KOLKATA, IN) ; AGARWAL; Nitin; (KANPUR, IN)
; YOUSUF; Junaid; (Srinagar, IN) ; GUPTA;
Nitin; (Kurukshetra, IN) ; DAUTRICHE; Pierre;
(MONTBONNOT, FR) |
|
Applicant: |
Name |
City |
State |
Country |
Type |
STMicroelectronics International N.V.
STMicroelectronics (CROLLES 2) SAS |
Amsterdam
Crolles |
|
NL
FR |
|
|
Assignee: |
STMicroelectronics International
N.V.
Amsterdam
NL
STMicroelectronics (CROLLES 2) SAS
Crolles
FR
|
Family ID: |
52114990 |
Appl. No.: |
14/046041 |
Filed: |
October 4, 2013 |
Current U.S.
Class: |
327/159 ;
327/155; 327/156; 327/174; 327/180 |
Current CPC
Class: |
H03L 7/095 20130101 |
Class at
Publication: |
327/159 ;
327/155; 327/174; 327/156; 327/180 |
International
Class: |
H03L 7/095 20060101
H03L007/095 |
Foreign Application Data
Date |
Code |
Application Number |
Jun 28, 2013 |
IN |
1939/DEL/2013 |
Claims
1. A clock generation circuit, comprising: a detection circuit
configured to detect a change in a voltage supply signal coupled to
the clock generation circuit; and a control circuit coupled to the
detection circuit and configured to alter a control signal for
regulating a current-controlled oscillator in response to detecting
the change.
2. The clock generation circuit of claim 1, wherein the detection
circuit is further configured to detect a voltage droop in the
voltage supply signal beyond a threshold.
3. The clock generation circuit of claim 1, wherein the detection
circuit is further configured to generate a flag indicative of the
change and configured to actuate a switch in the control
circuit.
4. (canceled)
5. The clock generation circuit of claim 1, wherein the
current-controlled oscillator comprises a digital
current-controlled oscillator.
6. The clock generation circuit of claim 1, wherein the control
circuit further comprises a frequency-locked loop having: a digital
current-controlled oscillator; a digital counter coupled to the
digital current-controlled oscillator and configured to count edges
of a clock signal generated by the digital current-controlled
oscillator; and a digital integrator coupled to the digital counter
and configured to generate a digital control word in response to
the digital counter and further configured to alter an output of
the digital current-controlled oscillator in response to the
generated digital control word.
7. The clock generation circuit of claim 1, wherein the oscillator
further comprises: a first digital-to-analog converter configured
to provide a first control current signal to the current-controlled
oscillator; and a second digital-to-analog converter configured to
remove current from the current control signal when engaged.
8. The clock generation circuit of claim 7, wherein the
current-controlled oscillator further comprises a control circuit
having: a first transistor having a first conduction node coupled
to a first supply node, a second conduction node coupled to the
first digital-to-analog converter and a control node coupled to the
second conduction node; a second transistor having a first
conduction node coupled to the first supply node, a second
conduction node coupled to the second digital-to-analog converter
and a control node coupled to the control node of the first
transistor; a third transistor having a first conduction node
coupled to the first supply node, a second conduction node coupled
to the oscillator and a control node coupled to the control node of
the first transistor; a fourth transistor having a first conduction
node coupled to a second supply node, a second conduction node
coupled to the second digital-to-analog converter and a control
node coupled to the second conduction node of the fourth
transistor; a fifth transistor having a first conduction node
coupled to the second supply node, a second conduction node and a
control node coupled to the control node of the fourth transistor;
and a switch controllable by the detection circuit and coupled
between the oscillator and the second conduction node of the fifth
transistor.
9. The clock generation circuit of claim 1, wherein the detection
circuit further comprises: a comparator configured to compare a
supply voltage signal to a threshold signal; a resistor ladder
coupled to the comparator and configured to generate the threshold
signal; and a controller coupled to the resistor ladder and
configured to control the generation of the threshold signal.
10. The clock generation circuit of claim 9, wherein the detection
circuit is further configured to generate a flag if the comparator
determines that the supply voltage signal falls below the threshold
signal, the flag configured to cause the control circuit to alter
the control signal used to regulate the oscillator.
11. A method, comprising: monitoring a supply voltage; generating a
digital control word for generating the clock signal; and in
response to detecting the supply voltage falling below a threshold,
causing a clock signal to be reduced by ramping the digital control
word toward generating a clock signal with a lower frequency.
12. The method of claim 11, wherein the reduction of the clock
signal further comprises reducing the clock signal to half.
13. (canceled)
14. The method of claim 11, further comprising: generating a
control current having a first magnitude for generating the clock
signal prior to the detecting the supply voltage falling below a
threshold; and generating the control current having a second
magnitude that is one half of the first magnitude after the
detecting the supply voltage falling below a threshold.
15. The method of claim 11, further comprising generating a
condition flag in response to the detecting the supply voltage
falling below a threshold.
16. The method of claim 15, further comprising closing a switch in
response to the generation of the condition flag.
17. The method of claim 15, further comprising counting the clock
cycles during the time that the condition flag is set and clearing
the condition flag after a threshold count is reached.
18. The method of claim 15, further comprising clearing the
condition flag in response to detecting the supply voltage rising
above the threshold.
19. The method of claim 18, further comprising generating a digital
control word configured to ramp the clock frequency toward an
initial frequency.
20. The method of claim 19 wherein the ramp comprises a linear
ramp.
21. The method of claim 19 wherein the ramp comprises an
exponential ramp.
22. A method, comprising: generating a clock signal in a frequency
locked loop, the frequency of the clock signal controlled by a
control signal; in response to detecting a supply voltage falling
below a threshold voltage; subtracting current from the control
signal.
23. The method of claim 22, wherein the current subtracted
comprises one half of the current of the control signal prior to
the detecting.
24. The method of claim 22, wherein the current subtracted is
subtracted immediately after the detecting.
25. A system, comprising: a voltage supply node a first electronic
component having a clock generator circuit and coupled to the
voltage supply node, including: a detection circuit configured to
detect a change in voltage at the voltage supply node; and a
control circuit coupled to the detection circuit and configured to
alter a control signal for regulating a current-controlled
oscillator in response to detecting the change; and a second
electronic component coupled to the first electronic component.
26. The system of claim 25, wherein one of the first and second
electronic components comprises a processor.
27. The system of claim 25, wherein one of the first and second
electronic components comprises single integrated circuit die.
28. The system of claim 25, wherein one of the first and second
electronic components comprises multiple integrated circuit
dies.
29. An integrated circuit, comprising: a voltage supply node; a
detection circuit configured to detect a change in voltage at the
voltage supply node; and a control circuit coupled to the detection
circuit and configured to subtract current from a control signal
for regulating a system clock in response to detecting the
change.
30. An integrated circuit, comprising: a voltage supply node a
detection circuit configured to detect a change in voltage at the
voltage supply node; and a control circuit coupled to the detection
circuit and configured to engage a current sink that sinks half of
a current of a control signal for regulating a system clock in
response to detecting the change.
31. An integrated circuit, comprising: a voltage supply node a
detection circuit configured to detect a change in voltage at the
voltage supply node; and a control circuit coupled to the detection
circuit and configured to immediately ramp a system clock signal in
response to detecting the change.
Description
PRIORITY CLAIM
[0001] The instant application claims priority to Indian Patent
Application No. 1939/DEL/2013, filed Jun. 28, 2013, which
application is incorporated herein by reference in its
entirety.
BACKGROUND
[0002] Integrated circuits and processors typically operate with a
specific expected supply voltage. Maintaining a steady voltage
supply assists with assuring that higher operating frequencies of
various logic circuits in the integrated circuit and/or processor
operates correctly with proper timing margins. However, if a lower
voltage supply than required is encountered, this may cause timing
failures, which can be catastrophic to the operation of the
integrated circuit and/or processor.
[0003] The power requirements of a processor can vary drastically.
For example, as part of its operation, code and logic may cause
occasional spikes in processing activity, which may result in a
sudden increase in power needed by the processor (e.g., current
drawn). These significant and sudden changes in drawn power may
cause significant droops (and overshoots) in the supplied voltage,
even though the power supply is providing the rated voltage needed
for the processor to operate at the desired frequency. It is
desirous to mitigate any effects of these voltage droops
BRIEF DESCRIPTION OF THE DRAWINGS
[0004] The foregoing aspects and many of the attendant advantages
of the claims will become more readily appreciated as the same
become better understood by reference to the following detailed
description, when taken in conjunction with the accompanying
drawings, wherein:
[0005] FIG. 1 shows a block diagram of a clock generation circuit
according to an embodiment of the subject matter disclosed
herein.
[0006] FIG. 2 shows a block diagram of a frequency-locked loop
circuit that may be part of the clock generation circuit of FIG. 1
according to an embodiment of the subject matter disclosed
herein.
[0007] FIG. 3 shows a block diagram of a voltage-droop detection
circuit that may be part of the clock generation circuit of FIG. 1
according to an embodiment of the subject matter disclosed
herein.
[0008] FIG. 4 shows a block diagram a system that may include the
clock generation circuit of FIG. 1 according to an embodiment of
the subject matter disclosed herein.
DETAILED DESCRIPTION
[0009] The following discussion is presented to enable a person
skilled in the art to make and use the subject matter disclosed
herein. The general principles described herein may be applied to
embodiments and applications other than those detailed above
without departing from the spirit and scope of the present detailed
description. The present disclosure is not intended to be limited
to the embodiments shown, but is to be accorded the widest scope
consistent with the principles and features disclosed or suggested
herein.
[0010] By way of overview, an embodiment as described herein
provides for a variable frequency clock generator. In aspects, an
embodiment includes a clock generator having a voltage-droop
detector circuit configured to monitor a supply voltage to an
integrated circuit. If the supply voltage falls below a specific
threshold, a voltage-droop flag may be set such that a
frequency-locked loop is triggered into a voltage-droop mode for
handling the voltage droop at the supply voltage. In response, a
current control signal that is input to an oscillator (in the
frequency-locked loop) that generates a system clock signal is
reduced by sinking current away from the current control signal to
the oscillator. This results in an immediate reduction on the
system clock frequency which will alleviate current demands for the
circuit by slowing down the operation of various components. Such a
state remains until the voltage droop has dissipated when the
current path is removed for sinking some of the current control
signal. Further, various biasing functions are provided for biasing
the current control signal back to an initial state after the
voltage droop situation has been cleared. Various biasing functions
may be used depending on the speed in which one desires that the
frequency of the system click signal return to its initial
frequency.
[0011] In conventional solutions to handling voltage droop, some
problematic circuits would employ a multiplexor circuit in the
signal path for the system clock. Thus, in response to detecting a
voltage droop, these conventional systems would adjust the path of
the clock signal through a series of multiplexors, effectively
introducing delay into the clock signal. Thus, by adding unneeded
delay, conventional clock generators attempted to "stretch" the
initial clock signals by dividing down the frequency of the clock
signal via delay elements in the large multiplexor. However, such
large multiplexors are cumbersome and inefficient since additional
circuitry is required that uses additional power. Thus, a solution
that does not use any multiplexor-based frequency adjustment is
desired.
[0012] FIG. 1 shows a block diagram of a clock generation circuit
100 according to an embodiment of the subject matter disclosed
herein. The clock generation circuit 100 may include, generally,
two components for determining if and when the system clock signal
140 may be modified in response to a voltage-droop event. These two
components, as shown in the embodiment of FIG. 1, include a
voltage-droop detection circuit 110 and a frequency-locked loop
circuit 120.
[0013] As will be described in greater detail below, the
voltage-droop detection circuit 110 includes a supply voltage input
signal 130 and a reference voltage input signal 135. The
voltage-droop detection circuit is configured to compare the supply
voltage 130 to the reference voltage 135. If the comparison yields
a large enough deviation (e.g., the supply voltage falls below a
specific threshold with respect to the reference voltage 135), then
the voltage-droop detection circuit generates a voltage-droop flag
115. The voltage-droop detection circuit is described in greater
detail below with respect to FIG. 3.
[0014] Keeping focus on FIG. 1 and this general overview of the
clock generation circuit 100, the voltage-droop flag 115 may be
input to the frequency-locked loop (FLL) circuit 120 as a trigger
for entering or leaving a droop mode of operation. Generally, if
the flag 115 is asserted, the FLL 120 will operate in a droop mode
of operation wherein the frequency of the system clock signal 140
that is generated is reduced. If the flag 115 is de-asserted, the
operating mode of the FLL 120 will return to a normal mode of
operation. In other embodiments, the FLL 120 may be other kinds of
clock generating circuitry, such as a phase-locked loop (PLL). The
transition into and transition from these modes of operation are
discussed in greater detail below with respect to FIG. 2.
[0015] Turning attention to FIG. 2, a block diagram is shown of a
FLL circuit 120 that may be part of the clock generation circuit of
FIG. 1 according to an embodiment of the subject matter disclosed
herein. The FLL circuit 120 of FIG. 2 may typically be used to
generate s system clock signal 140 to be used in circuits coupled
to the clock generator 100 of FIG. 1. Such circuits may be disposed
on the same integrated circuit die as the clock generator or on
other integrated circuit dies or printed circuit boards coupled to
the clock generator 100, such as separate processors and memories
(shown in FIG. 4). Further, these circuits are also typically
coupled to the overall supply voltage (130 of FIG. 1) such that as
these various circuits perform operations, the voltage supplied by
the power supply (not shown) may exhibit droops in voltage due to
increased current demand by these various circuits as briefly
discussed above.
[0016] In the FLL of FIG. 2, an oscillator 210 generates the system
clock signal 140. In this embodiment, the oscillator 210 is a
digitally controlled oscillator (DCO) such that a digital error
signal 221 is used as a feedback signal to continually adjust the
output of the DCO 210 (i.e., the system clock signal 140). The
digital error signal 221 is generated from a digital integrator 220
that receives a feedback signal 232 from a cycle counter 230 which
is coupled to the system clock signal 140 (e.g., the output of the
DCO 210 to provide feedback).
[0017] In operation, the DCO 210 may be synchronized to an external
frequency reference 231 which is used as an input to the digital
counter 230. The frequency of this external reference signal is
typically a low frequency signal that is used as a reset signal to
the digital counter 230. In this manner, the digital counter 230
acts as a frequency divider, counting pulses from a system clock
140 (typically several MHz) and toggling the state of its output
when the count reaches a specific and programmable value. The
frequency of the output of the digital counter 230 can thus be
defined by the number of pulses counted (of the system clock signal
140), and this generates a feedback signal 232 at the desired
frequency to be used as input to the digital integrator 220. Thus,
the digital counter 230 effectively compares the frequency of
system clock signal 140 to a multiple of the frequency of a
lower-frequency reference clock signal 231, and generates a
feedback signal 232 in response to the comparison. For example, the
digital counter 230 may cause the frequency of system clock 140 to
be 2000 times (e.g., 2 GHz) the frequency of the reference clock
(e.g., 1 MHz).
[0018] Further, the digital integrator 220 effectively provides a
low-pass filter for the feedback signal 232 from the digital
counter 230, and provides a digital control word 221 to a current
control circuit 260 for the DCO 210 so as to set and maintain the
frequency of system clock 140 at the desired frequency. In summary,
the DCO 210, digital counter 230, and digital integrator 220 form a
feedback loop that maintains the frequency of system clock 140 at a
programmable multiple of the reference clock 231. The operation of
the current control circuit 260 may be dependent upon the assertion
or de-assertion of the droop voltage flag 115 as discussed further
below.
[0019] Thus, when the droop-voltage flag 115 is de-asserted (e.g.,
the voltage of a supply voltage is maintained within a specific
voltage level), one may say that the operation of the FLL 120 is in
a normal mode. This is opposed to a droop-voltage mode when the
droop-voltage flag 115 is asserted (as discussed next). In normal
mode, the switch 265 is open and a control current signal 270 is
generated through the current control circuit 260 for controlling
the current controlled oscillator 250. This is done so through a
current digital-to-analog converter (DAC) 240, such that the
digital control word 221 is converted into an analog current
signal. Further, a subtractor DAC 245 also receives the digital
control word 221 and converts it into a similar analog current
signal.
[0020] The current control circuit 260 includes an internal voltage
supply rail Vdd. The DAC 240 draws a current I through transistor
M2 from the Vdd rail. For the purposes herein, this current I will
simply be referred to as I and derives from a combination of a
current source coupled to the Vdd rail as adjusted by the digital
control word 221 via the DAC 240. This current I is mirrored on
transistor M3 and M4. The transistor M3 includes a drain terminal
coupled to the subtractor DAC 245 and therefore draws a current
from the drain terminal of approximately one half of the current
through the transistor M2, i.e., I/2. The other half of the current
I is sunk through transistor M5 to ground. During operation, the
current through the subtractor DAC 245 will always remain at I/2.
The purpose of this portion of the circuit is to establish a
current through transistor M5 as approximately one half of the
current I though transistor M2 and M3.
[0021] Still referring to a normal mode of operation, the
current/is also mirrored through transistor M4. Of course, in
normal mode, the droop-voltage flag 115 is not set and the switch
265 is open. Therefore, no current may flow through transistor M6
and the entire current I flows into the current controlled
oscillator 250 as the oscillator control signal 270. Thus, in
normal mode, any currents sunk by the subtractor DAC 245 may
effectively be ignored as not affecting the generation of the
system clock signal 140.
[0022] However, if the supply voltage is determined to have
deviated too far below an expected level (e.g., drooped), then the
voltage-droop flag 115 may be set and close the switch 265. When
this occurs, first, the voltage-droop flag 115 freezes the digital
control word 221 from the digital integrator at its current value;
that is, the voltage-droop flag 115 causes the digital integrator
220 to effectively ignore the error signal 232 from the counter
230.
[0023] Further, with switch 265 closed, an additional current path
is created for the current control signal 270. The current that is
generated as a result of this path now opened up is mirrored from
transistor M5 though transistor M6. This current is I/2. Thus, the
control current signal 270 falls from I to I/2 as soon as the
switch 265 closes. This, in turn, immediately causes the
current-controlled oscillator 250 to begin generating a system
clock signal 140 that is half of the previous frequency.
[0024] Shortly thereafter, the digital integrator 220 changes the
value of the digital control word 221 such that the current
generated by the current DAC 240 is reduced to the difference
current (e.g., I/2). Likewise, the current generated by the
subtractor DAC 245 remains at I/2 and the current sunk through the
current mirror of M5 and M6 begins to fall toward zero current.
Thus, as the current through the current DAC 240 begins to track
lower (e.g., eventually settling on a current I/2), the
current-controlled oscillator 250 continues to receive the same
value of a current control signal 270 (e.g., I/2). That is, the
subtractor DAC 245 serves the purpose of quickly reducing the
frequency of the system clock signal 140 until the digital
integrator 220 has a chance to reduce the current from the current
DAC 240 and the additional current from the current DAC above a
value of I/2 is sunk though the current mirror of M5 and M6 until
reaching equilibrium. The FLL 120 remains in this droop-voltage
mode of operation until the droop voltage flag 115 is
de-asserted.
[0025] Keeping focus on FIG. 2, the droop voltage flag may be
cleared (e.g., de-asserted) in any manner of ways as discussed
below with respect to FIG. 3. When the droop-voltage flag 115 is
de-asserted, the switch 265 once again opens up and creates an open
circuit leg through transistor M6. Further, the digital integrator
220 begins to change the digital control word 221 back toward its
pre-droop mode value (which the digital integrator 220 previously
stored in response to the droop voltage flag 115). The digital
integrator 220 may be configured to cause the digital control word
221 to ramp back to its initial value using a number of possible
methods. In one embodiment, the digital integrator 220 begins
biasing the digital control word 221 back to its initial value at a
programmable rate. The programmable rate may be steady ramp
function (both linearly steady and exponentially steady) or
segmented, and may even be non-monotonic. Therefore, the current
generated by the current DAC 240 ramps back up to I at the same
programmable rate, as does the current sunk by the transistor M5
ramp back up to I/2 (or whatever other fraction of I for which it
is programmed) at the same programmed rate. Likewise, the frequency
of system clock signal 140 eventually also ramps back up its
initial frequency in a controlled manner at the same programmable
rate.
[0026] Additional control parameters may be in place to guard
against situations where the supply voltage droops again before
returning to an initial frequency or in situations where the supply
voltage droops continuously after getting back to an initial
frequency (e.g., chattering). In one embodiment, if the supply
voltage droops again before the frequency of system clock signal
140 ramps back up to F, then the FLL 120 repeats the above
procedure without waiting for system clock signal 140 to ramp back
up to F. That is, the voltage-droop flag 115 is again set, and the
procedure repeats. Thus, the digital integrator 220 is in the midst
of biasing the digital control word 221 back to its pre-droop
value, when the droop-voltage flag 115 is set and the switch is
closed--creating a current path of approximately half of the
current control signal to sink through transistor M6 again.
[0027] In another embodiment, if the FLL 120 may be a droop-voltage
mode for an extended period of time. Thus, additional factors such
as temperature and environmental factors may alter what the best
pre-droop-voltage frequency ought to be. That is, because the FLL
120 is not operating in normal mode for an extended period of time,
other aspects of the clock generator 100 which may take into
account temperature and ambient environment, have been suspended
for some time and temperature and ambient conditions may no longer
match the pre-droop-voltage frequency in which the digital
integrator 220 has stored prior to the voltage-droop flag 115 being
asserted. Thus, the FLL 120 may utilize the droop counter 234
counter to count system clock signal 140 pulses in response to the
voltage-droop flag 115. When the voltage-droop flag 115 remains
asserted and the count of this counter exceeds a programmable
threshold, then, instead of ramping the value of the digital
control word 221 back to its pre-droop-voltage value as described
above, the FLL 120 may close the feedback loop immediately in
response to clearing the voltage-droop flag (i.e., the voltage
droop on the supply voltage is no longer present), so that the FLL
120 can acquire the proper value of the digital control word 221 to
force the frequency of system clock signal back to F without
following the programmed biasing function. Although this may be
slower, it may be more accurate given the time that the FLL 120 was
in voltage-droop mode.
[0028] In another embodiment, if the supply voltage continually
droops before the frequency of system clock signal 140 returns to
F, then the FLL 120 may dynamically increase the time for biasing
the frequency of system clock signal 140 back to F after a reset of
voltage-droop flag 115. That is, it may become apparent that using
an initial biasing function to return the frequency of the system
clock signal 140 back to F may be too fast and actually cause
subsequent droops on the supply voltage as functionality of the
systems is increased due to the rapidly increasing frequency of the
system clock signal 140. As a result, a chattering effect (e.g., a
consistent transition between droop-voltage mode and normal
operation mode) may be affected. Therefore, the FLL 120 may be
configured to recognize a number of transitions in a specific time
period whereby the biasing function is adjusted in response.
[0029] Turning attention to the next figure, FIG. 3 shows a block
diagram of a voltage-droop detection circuit 110 that may be part
of the clock generation circuit 100 of FIG. 1 according to an
embodiment of the subject matter disclosed herein. The droop
voltage flag 115 may be set in response to a high-speed voltage
comparator 325 detecting that the actual supply voltage 130 has
fallen below a specific and programmable trip voltage or reference
voltage 135. A threshold voltage 340 may be programmable using a
resistor ladder 320 that may be controllable via a controller 330.
Thus, the controller 330 may set a specific threshold voltage 340
via the resistor ladder 320. The droop detector 110 may include a
first comparator 325 for receiving the threshold voltage 340 and a
supply voltage 130. Further, the droop voltage detector 110 may
also include comparator 365 for receiving the reference voltage 135
and the threshold voltage 340 that is set from the resistor ladder
320. When compared to the reference voltage 135, the effective trip
voltage may be stored as a digital value via this feedback to the
resistor ladder 320 in a simple manner e.g., via the controller
330. As can be expected, if the supply voltage 130 rises above the
threshold voltage 340, the comparator 325 resets the voltage-droop
flag 115 (e.g., de-asserts it). Likewise, if the threshold voltage
falls below the supply voltage 130, then the voltage-droop flag 115
is set (e.g., asserted).
[0030] The clock generator 100 as described above with respect to
FIGS. 1-3 exhibits a number of advantages over previous clock
generators of the past. As briefly discussed above, conventional
clock generators (not shown in any figure) may often employ a
multiplexor circuit in an effort to reduce clock frequency in
response to a detected voltage droop in the supply voltage.
However, such the embodiments described provide better resolution
at much lower power than a multiplexor. The current DAC 240 of FIG.
2 uses little extra circuitry than what is already present for the
FLL 120. Thus, simply using the current DAC 240 in the additional
ways described above eliminates any need for a cumbersome
multiplexor. Further, the frequency of system clock signal 140 is
biased back toward the initial frequency at its very own frequency
thereby eliminating any frequency-limiting factor as is present
with a multiplexor and eliminating any delays associated with the
elements of the multiplexor itself.
[0031] In yet another advantage, the various ways in which the
clock generator 100 biases the system clock signal 140 frequency
back to its initial frequency does not utilize any manner of phase
switching that is used in a multiplexor-based system. Switching
between phases of a clock signal generates jitter on the system
clock signal 140 that is not desirous. Thus, the biasing functions
do not introduce any phase-switching jitter.
[0032] Further yet, by using a voltage-droop flag 115, the clock
generator 100 of FIG. 1-3 provides an indication of a voltage droop
in an asynchronous manner. That is, the voltage-droop flag 115 is
generated independent of the system clock signal 140. Thus, setting
voltage-droop flag 115 switches in the current mirror (M5-M6) to
the path of the current control signal 270 to the oscillator 250,
and because this switching in of the current mirror (M5-M6) can be
done at any time, it is asynchronous. That is, the setting of
voltage-droop flag 115 does not need to wait for an edge of system
clock signal 140, or an edge of any other clock.
[0033] The clock generator 100 described above with respect to
FIGS. 1-3 may be part of an overall system as well. FIG. 4 shows a
block diagram a system 400 that may include the clock generation
circuit 100 of FIG. 1 according to an embodiment of the subject
matter disclosed herein. The clock generator 100 may be disposed on
a single integrated circuit die 401 as shown, or may be disposed
across more than one integrated circuit die such as a second
integrated circuit die 402 that is shown as coupled to the first
integrated circuit die. The first or second integrated circuit dies
may also include additional circuitry such as circuitry 403 s shown
disposed on integrated circuit 401.
[0034] Further yet, the system 400 may also include a processor 405
and a memory 406 coupled to the clock generator 100. These
additional components may also be disposed on speared integrated
circuit dies on the same integrated circuit die with the clock
generator 100. These additional components may also employ use of
the system clock 140 generated by the clock generator 100 of the
system 400.
[0035] While the subject matter discussed herein is susceptible to
various modifications and alternative constructions, certain
illustrated embodiments thereof are shown in the drawings and have
been described above in detail. It should be understood, however,
that there is no intention to limit the claims to the specific
forms disclosed, but on the contrary, the intention is to cover all
modifications, alternative constructions, and equivalents falling
within the spirit and scope of the claims.
* * * * *