U.S. patent number RE34,410 [Application Number 07/771,905] was granted by the patent office on 1993-10-19 for antenna system for hybrid communication satellite.
This patent grant is currently assigned to Hughes Aircraft Company. Invention is credited to Harold A. Rosen.
United States Patent |
RE34,410 |
Rosen |
October 19, 1993 |
Antenna system for hybrid communication satellite
Abstract
A satellite communications system employs separate subsystems
for providing broadcast and point-to-point two-way communications
using the same assigned frequency band. The broadcast and
point-to-point subsystems employ an integrated satellite antenna
system which uses a common reflector (12). The point-to-point
subsystem achieves increased communication capacity through the
reuse of the assigned frequency band over multiple, contiguous
zones (32, 34, 36, 38) covering the area of the earth to be
serviced. Small aperture terminals in the zones are serviced by a
plurality of high gain downlink fan beams (29) steered in the
east-west direction by frequency address. A special beam-forming
network (98) provides in conjunction with an array antenna (20) the
multiple zone frequency address function. The satellite (10)
employs a filter interconnection matrix (90 ) for connecting earth
terminals in different zones in a manner which permits multiple
reuse of the entire band of assigned frequencies. A single pool of
solid state transmitters allows rain disadvantaged users to be
assigned higher than normal power at minimum cost. The
intermodulation products of the transmitters are geographically
dispersed.
Inventors: |
Rosen; Harold A. (Santa Monica,
CA) |
Assignee: |
Hughes Aircraft Company (Los
Angeles, CA)
|
Family
ID: |
27118532 |
Appl.
No.: |
07/771,905 |
Filed: |
October 4, 1991 |
Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
Issue Date |
|
Reissue of: |
896533 |
Aug 14, 1986 |
04792813 |
Dec 20, 1988 |
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Current U.S.
Class: |
343/781P;
343/756; 343/779; 343/DIG.2 |
Current CPC
Class: |
H01Q
5/45 (20150115); H01Q 21/0025 (20130101) |
Current International
Class: |
H01Q
5/00 (20060101); H01Q 21/00 (20060101); H01Q
019/14 () |
Field of
Search: |
;343/781P,756,779,909,DIG.2 |
References Cited
[Referenced By]
U.S. Patent Documents
Other References
Parekh et al, "Advanced Satcom Communication Antennas" IEEE
International Conference on Communications 1985, vol. 3 of 3, IEEE,
Jun. 1985, pp. 1293-1294..
|
Primary Examiner: Hajec; Donald
Assistant Examiner: Le; Hoanganh
Attorney, Agent or Firm: Lindeen, III; Gordon R. Denson-Low;
Wanda K.
Claims
What is claimed is:
1. An antenna reflector system, comprising:
a first reflector for reflecting radio frequency signals having a
first linear polarization; and
a second reflector for reflecting radio frequency signals having a
second linear polarization .[.different than.]. orthogonal to said
first linear polarization;
said first and second reflectors intersecting each other along a
common axis and being angularly offset relative to each other about
said common axis;
the direction of said first linear polarization being parallel to
said common axis, the direction of said second linear polarization
being perpendicular to said common axis.
2. The antenna reflector system of claim 1, wherein each of said
reflectors is generally parabolic in shape.
3. The antenna reflector system of claim 1, wherein said first
reflector is transmissive of radio frequency signals having said
second polarization and said second reflector is transmissive of
radio frequency signals having said first polarization.
4. An antenna system for earth-orbiting communications satellite,
comprising:
first and second reflectors for respectively reflecting radio
frequency signals of first and second differing polarizations;
a first antenna subsystem including a first transmitter means
oriented for transmitting to said first reflector a first transmit
beam having siad first polarization and a first receiver means
oriented for receiving from said second reflector a first receive
beam having said second polarization, said first transmit beam
being reflected by said first reflector to the earth, said first
receive beam being reflected by said second reflector from the
earth to said first receiver means; and
a second antenna subsystem including a second transmitter means
oriented for transmitting to said second reflector a second
transmit beam having said second polarization and a second receiver
means oriented for receiving from said first reflector a second
receive beam having said first polarization, said second transmit
beam being reflected by said second reflector to the earth, said
second receive beam being reflected by said first reflector from
the earth to said second receiver means.
5. The antenna system of claim 4, wherein said first and second
reflectors intersect each other along a common axis.
6. The antenna system of claim 5, wherein said first and second
reflectors are angularly offset with respect to each other about
said common axis.
7. The antenna system of claim 5, wherein each of said first and
second reflectors is generally parabolic in shape.
8. The antenna system of claim 4, including a first frequency
diplexer for separating the frequencies of said first receive beam
and said second transmit beam, and a second frequency diplexer for
separating the frequencies of said second receive beam and said
first transmit beam.
9. The antenna system of claim 8, wherein:
said first diplexer includes a first frequency selective screen for
passing said first receive beam therethrough and for reflecting
said second transmit beam therefrom, and
said second diplexer includes a second frequency selective screen
for passing said second receive beam therethrough and for
reflecting said first transmit beam therefrom.
10. The antenna system of claim 9, wherein said first receiver
means includes at least one feed horn and said first frequency
selective screen is positioned between said feed horn and said
second reflector.
11. The antenna system of claim 10, wherein said second transmitter
means includes a transmit array for forming said second transmit
beam and said second antenna subsystem further includes means for
enlarging the second transmit beam emanating from said transmit
array.
12. The antenna system of claim 11, wherein said enlarging means
includes a parabolic reflector positioned to reflect to said second
frequency selective screen the second transmit beam emanating from
said transmit array.
13. The antenna system of claim 11, wherein said transmit array,
said first frequency selective screen and said feed horn are
mounted on a common support.
14. The antenna system of claim 9, wherein said first and second
frequency selective screen are disposed in side-by-side
relationship to each other.
15. The antenna system of claim 9, wherein said second receiver
means includes at least one feed horn and said second frequency
selective screen is positioned between said feed horn and said
first reflector.
16. The antenna system of claim 9, wherein said first transmitter
is positioned between said second frequency selective screen and
said first reflector.
17. The antenna system of claim 8, wherein said first diplexer,
said first receiver means and said second transmitter means each
include feed horns diposed on one side of a plane passing through
approximately the centers of said first and second reflectors, and
said second diplexer, and said first transmitter means and said
second receiver means include feed horns disposed on the other side
of said plane.
18. An antenna system for an earth-orbiting communications
satellite, comprising:
a first transmitter and a first receiver forming a first
earth-to-earth communications link, said first transmitter
transmitting a first transmit signal having a first polarization,
said first receiver receiving a first receiver signal having a
second polarization different than said first polarization;
a second transmitter and a second receiver forming a second
earth-to-earth communications link, said second transmitter
transmitting a second transmit signal having said second
polarization, said second receiver receiving a second receive
signal having said first polarization;
first means for separating the frequencies of said first transmit
signal from the frequencies of said second receive signal;
second means for separating the frequencies of said first receive
signal from the frequencies of said second transmit signal; and
means for reflecting each of said first and second transmit and
receive signals.
19. The antenna system of claim 18, wherein said reflecting means
includes a first reflector having said first polarization for
reflecting said first transmit signal and said second receive
signal, and a second reflector having said second polarization for
reflecting said first receive signal and said second transmit
signal.
20. The antenna system of claim 19, wherein said first and second
reflectors intersect each other along a common axis and are
angularly offset from each other about said common axis.
21. The antenna system of claim 18, wherein each of said first and
second means respectively include first and second frequency
selective screen, said first screen being arranged to transmit said
second receive signal therethrough and to reflect said first
transmit signal, said second screen being arranged to transmit said
first receiver signal therethrough and to reflect said second
transmit signal.
22. The antenna system of claim 18, wherein:
said second transmitter includes a transmit array for forming a
transmit beam pattern defining said transmit signal,
said system further includes means for enlarging said transmit beam
pattern, and
said second means includes a frequency selective screen for passing
said first receive signal therethrough and for reflecting said
transmit signal;
said first receiver includes at least one receive horn,
said screen being positioned between said first receive horn and
said reflecting means,
said enlarging means including a reflector positioned to reflect
said transmit beam from said array onto said screen.
23. The antenna system of claim 18, wherein:
said first means includes a frequency selective screen for
transmitting said second receiver signal therethrough and for
reflecting said first transmit signal therefrom, and
said second receiver includes at least one receive horn,
said screen being positioned between said reflecting means and said
second receive horn,
said first transmitter including at least one horn positioned
between said screen and said reflecting means.
Description
TECHNICAL FIELD
The present invention broadly relates to satellite communication
systems especially of the type employing a spin-stabilized
satellite placed in geosynchronous orbit above the earth so as to
form a communication link between many small aperture terminals on
the earth. More particularly, the invention involves an antenna
system for a communication satellite having hybrid communication
capability accommodating both two-way and broadcast communication
systems.
BACKGROUND ART
Communications satellites have in the past typically employed
several antenna subsystems for receiving and transmitting signals
from and to the earth respectively. These antenna subsystems are
often mounted on a "despun" platform of the satellite so as to
maintain a constant antenna orientation relative to the earth. The
antenna subsystems may be either fixed or steerable and may operate
on different polarizations. For example, one known type of antenna
subsystem includes a pair of primary reflectors mounted in aligned
relationship to each other, one behind the other. One of the
reflectors is vertically polarized and is operative to reflect one
of the transmit and receive signals. The other reflector is
horizontally polarized and is operative to reflect the other of the
transmit and receive signals.
Because of space constraints in communication satellites, the
antenna systems for such satellites must be as compact and utilizes
a few components as possible. To partially satisfy this objective,
imaging reflector arrangements have been deviced to form a scanning
beam using a small transmit array. These arrangements achieve the
performance of a large aperture phased array by combining a small
phased array with a large main reflector and an imaging arrangement
of smaller reflectors to form a large image of a small array over
the main reflector. An electronically scannable antenna with a
large aperture is thus formed, using a small array. One important
feature of this imaging arrangement is that the main reflector need
not be fabricated accurately, since small imperfections can be
corrected efficiently by the array.
In order to provide a compact antenna system, so called
quasi-optical diplexers have been employed in the past to separate
coincident radio signals of different frequency bands, e.g. a
transmit signal and a receive signal. A compact imaging arrangement
employing a quasi-optical diplexer of the type discussed above is
disclosed in "Imaging Reflector Arrangements to Form a Scanning
Beam Using a Small Array", C. Dragone and M. J. Gans, The Bell
System Technical Journal, Volume 5, No. 2, Feb. 9, 1979. This
publication discloses a frequency diplexer positioned between a
transmit array and an imaging reflector. The receive array is
positioned on one side of the diplexer, opposite that of the
transmit array. Signals in the transmit band pass from the transmit
array through the diplexer to the imaging reflector. The diplexer
is reflective of signals in the receive band, consequently, a
signal in the receive band which is incident on the diplexer is
reflected onto the receive array.
With the increasing cost of placing a communications satellite in
geosynchronous orbit, it has become increasingly important for the
satellite to handle a maximum number of channels, and if possible,
different types of communications services. The present invention
is directed toward achieving these objectives.
SUMMARY OF THE INVENTION
According to the present invention, an antenna system is provided
for a communications satellite which comprises a first subsystem
suitable for providing two-way, point-to-point communications
service, and a second subsystem for providing broadcast service.
Each of the subsystems include a transmitter and a receiver. Both
subsystems employ a main reflector assembly comprising a pair of
parabolic reflectors which intersect each other along a common axis
and are respectively vertically and horizontally polarized.
The point-to-point transmitter and broadcast receiver of the
subsystems each use a vertically polarized signal and cooperate
with the vertically polarized main reflector. The broadcast
transmitter and point-to-point receiver of the subsystems each
operate with a horizontally polarized signal and cooperate with the
horizontally polarized reflector. The transmitter of the
point-to-point subsystem includes an imaging reflector arrangement
utilizing a small subreflector to form a large image of the small
transmitter array over the main reflector, thereby obtaining the
performance of a large aperture phased array.
A pair of quasi-optical diplexers defined by frequency selective
screens are employed to separate the transmit and receive signals
of each of the subsystems.
It is therefore a primary object of the present invention to
provide an antenna system for a communications satellite which
includes subsystems forming independent communication links with
the areas serviced by the satellite.
A further object of the present invention is to provide an antenna
system as described above which is particularly compact and simple
in construction.
A further object of the invention is to provide an antenna system
as described above which includes a first receiver and transmitter
allowing two-way communication between any of a plurality of ground
stations and a second receiver and transmitter providing a
broadcast service for the area serviced by the satellite.
Another object of the present invention is to provide an antenna
system as described above which utilizes a pair of frequency
selective screens for respectively separating the transmit and
receive signals of each of the subsystems.
A further object of the invention is to provide an antenna system
as described above which includes an electronically scannable
antenna with a large aperture using a small phased array.
Another object of the present invention is to provide an antenna
reflector assembly comprising a pair of reflectors of respectively
different polarizations which intersect each other along a common
axis and form a compact assembly.
These, and further objects and advantages of the invention will be
made clear or will become apparent during the course of the
following description of the invention.
BRIEF DESCRIPTION OF THE DRAWINGS
In the accompanying drawings:
FIG. 1 is a perspective view of a communications satellite, showing
the antenna subsystems;
FIG. 2 is a top plan view of the antenna subsystems shown in FIG.
1;
FIG. 3 is a sectional view taken along the line 3--3 in FIG. 2;
FIG. 4 is a sectional view taken along the line 4--4 in FIG. 2;
FIG. 5 is a view of the United States and depicts multiple,
contiguous receive zones covered by the satellite of the present
invention, the primary areas of coverage being indicated in
crosshatching and the areas of contention being indicated by a
dimpled pattern;
FIG. 6 is a block diagram of the communications electronics for the
communication satellite;
FIG. 7 is a schematic diagram of a coupling network which
interconnects the point-to-point receive feed horns with the inputs
to the communications electronics shown in FIG. 6.
FIG. 8 is a reference table of the interconnect channels employed
to connect the receive and transmit zones for the point-to-point
system;
FIG. 9 is a diagrammatic view of the United States depicting
multiple contiguous transmit zones covered by the satellite and the
geographic distribution of the interconnected channels for each
zone, across the United States;
FIG. 9A is a graph showing the variation in gain of the transmit
antenna beam for each zone in the point-to-point system in relation
to the distance from the center of the beam in the east-west
direction;
FIG. 9B is a graph similar to FIG. 9A but showing the variation in
gain in the north-south direction;
FIG. 10 is a detailed schematic diagram of the filter
interconnection matrix employed in the point-to-point system;
FIG. 11 is a detailed, plan view of the beam-forming network
employed in the point-to-point system;
FIG. 12 is an enlarged, fragmentary view of a portion of the
beam-forming network shown in FIG. 11;
FIG. 13 is a front elevational view of the transmit array for the
point-to-point system, the horizontal slots in each transmit
element not being shown for sake of simplicity;
FIG. 14 is a side view of the transmit element of the array shown
in FIG. 13 and depicting a corporate feed network for the
element;
FIG. 15 is a front, perspective view of one of the transmit
elements employed in the transmit array of FIG. 13;
FIG. 16 is a front view of the receive feed horns for the
point-to-point system; and
FIG. 17 is a diagrammatic view showing the relationship between a
transmitted wave and a portion of the transmit feed array for the
point-to-point system.
DESCRIPTION OF THE PREFERRED EMBODIMENTS
Referring first to FIGS. 1-4, a communications satellite 10 is
depicted which is placed in geosynchronous orbit above the earth's
surface. The satellite's antenna system, which will be described in
more detail below, will typically be mounted on an earth-oriented
platform so that the antenna system maintains a constant
orientation with respect to the earth.
The satellite 10 is of a hybrid communications-type satellite which
provides two different types of communication services in a
particular frequency band, for example, the fixed satellite service
Ku band. One type of communication service, referred to hereinafter
as point-to-point service, provides two-way communications between
very small aperture antenna terminals of relatively narrow band
voice and data signals. Through the use of frequency division
multiple access (FDMA) and reuse of the assigned frequency
spectrum, tens of thousands of such communication channels are
accommodated simultaneously on a single linear polarization. The
other type of communication serivce provided by the satellite 10 is
a broadcast service, and it is carried on the other linear
polarization. The broadcast service is primarily used for one-way
distribution of video and data throughout the geographic territory
served by the satellite 10. As such, the transmit antenna beam
covers the entire geographic territory. For illustrative purposes
throughout this description, it will be assumed that the geographic
area to be serviced by both the point-to-point and broadcast
services will be the United States. Accordingly, the broadcast
service will be referred to hereinafter as CONUS (Continental
United States).
The antenna system of the satellite 10 includes a conventional omni
antenna 13 and two antenna subsystems for respectively servicing
the point-to-point and CONUS systems. The point-to-point antenna
subsystem provides a two-way communication link to interconnect
earth stations for two-way communications. The CONUS antenna system
functions as a transponder to broadcast, over a wide pattern
covering the entire United States, signals received by one or more
particular locations on earth. The point-to-point transmit signal
and the CONUS receive signal are vertically polarized. The CONUS
transmit and point-to-point receive signals are horizontally
polarized. The antenna system includes a large reflector assembly
12 comprising two reflectors 12a, 12b. The two reflectors 12a, 12b
are rotated relative to each other about a common axis and
intersect at their midpoints. The reflector 12a is horizontally
polarized and operates with horizontally polarized signals, while
the reflector 12b is vertically polarized and therefore operates
with vertically polarized signals. Consequently, each of the
reflectors 12a, 12b reflects signals which the other reflector 12a,
12b transmits.
A frequency selective screen 18 is provided which includes two
halves or sections 18a, 18b and is mounted on a support 30 such
that the screen halves 18a, 18b are disposed on opposite sides of a
centerline passing diametrically through the satellite 10, as best
seen in FIG. 2. The frequency selective screen 18 functions as a
diplexer for separating different bands of frequencies and may
comprise an array of discrete, electrically conductive elements
formed of any suitable material, such as copper. Any of various
types of known frequency selective screens may be employed in this
antenna system. However, one suitable frequency selective screen,
exhibiting sharp transition characteristics and capable of
separating two frequency band which are relatively close to each
other, is described in U.S. patent application Ser. No. 896,534,
filed Aug. 14, 1986, and assigned to Hughes Aircraft Company. The
frequency selective screen 18 effectively separates the transmitted
and received signals for both the CONUS and point-to-point
subsystems. It may be appreciated that the two halves 18a, 18b of
the screen 18 are respectively adapted to separate individual
signals which are horizontally and vertically polarized.
The CONUS subsystem, which serves the entire country with a single
beam, has, in this example, eight conventional transponders each
having a high power traveling wave tube amplifier as its
transmitter 82 (see FIG. 6). The CONUS receive antenna uses
vertical polarization, sharing the vertically polarized reflector
12b with the point-to-point transmission system. CONUS receive
signals pass through the frequency selective screen half 18b and
are focused on the receive feed horns 14 located at the focal plane
28 of reflector 12b. The antenna pattern so formed is shaped to
cover CONUS. The CONUS transmit antenna employs horizontal
polarization, and shares reflector 12a with the point-to-point
receive system. Signals radiating from the transmit feeds 24 are
reflected by the horizontally polarized frequency selective screen
18a to reflector 12a whose secondary pattern is shaped to cover
CONUS.
The point-to-point subsystem broadly includes a transmit array 20,
a subreflector 22, and receive feed horns 16. The transmit array
20, which will be described later in more detail, is mounted on the
support 30, immediately beneath the screen 18. The subreflector 22
is mounted forward of the transmit array 20 and slightly below the
screen 18. The signal emanating from the transmit array 20 is
reflected by the subreflector 22 onto one half 18b of the screen
18. The subreflector 22 in conjunction with the main reflector 12
functions to effectively magnify and enlarge the pattern of the
signal emanating from the transmit array 20. The signal reflected
from the subreflector 22 is, in turn, reflected by one half 18b of
the screen 18 onto the large reflector 12b, which in turn reflects
the point-to-point signal to the earth. Through this arrangement,
the performance of a large aperture phase array is achieved. The
receive feed horns 16 are positioned in the focal plane 26 of the
reflector 12a. It consists of four main horns 50, 54, 58, 62 and
three auxiliary horns 52, 56, 60 as shown in FIG. 16.
Referring now also to FIGS. 13-15, the transmit array 20 comprises
a plurality, for example forty, transmit waveguide elements 106
disposed in side-by-side relationship to form an array, as shown in
FIG. 13. Each of the transmit waveguide elements 106 includes a
plurality, for example twenty-six, of horizontal, vertically spaced
slots 108 therein which result in the generation of a vertically
polarized signal. As shown in FIG. 14, the transmit array 20 is fed
with a transmit signal by means of a corporate feed network,
generally indicated by the numeral 110 which excites the array
element in four places 114. The purpose of the corporate feed
network 110 is to provide a broadband match to the transmit
waveguide element 106. Signals input to the waveguide opening 112
excite the array slots 108 so that the slot excitation is designed
to give a flat pattern in the north-south direction.
Attention is now directed to FIG. 5 which depicts a generally
rectangular beam coverage provided by the horizontally polarized
point-to-point receive system. In this particuular example, the
area serviced by the point-to-point system is the continental
United States. The point-to-point receive system comprises four
beams R1, R2, R3, R4 respectively emanating from the four uplink
zones 32, 34, 36, 38 to the satellite, wherein each of the beams
R1-R4 consists of a plurality of individual uplink beams
originating from individual sites in each zone 32, 34, 36, 38 and
carries an individual signal from that site. The uplink beam
signals from the individual sites are arranged into a plurality of
channels for each zone. For example, zone 32 may include a
plurality, e.g. sixteen 27 MHz channels with each of such channels
carrying hundreds of individual beam signals from corresponding
uplink sites in zone 32.
The signal strength for each of the four beam pattern contours,
respectively designated by numerals 32, 34, 36 and 38, are
approximately 3 dB down from peaks of their respective beams. The
antenna beams have been designed to achieve sufficient isolation
between them to make feasible in the cross-hatched regions 39, 41,
43, 45 reuse of the frequency spectrum four times. In the dotted
regions 40, 42, and 44, the isolation is insufficient to
distinguish between signals of the same frequency originating in
adjacent zones. Each signal originating in these regions will
generate two downlink signals, one intended and one extraneous. The
generation of extraneous signals in these areas will be discussed
later in more detail.
It may be readily appreciated from FIG. 5 that the four zones
covered by beams 32, 34, 36, 38 are unequal in width. The East
Coast zone covered by beam 32 extends approximately 1.2 degrees;
the Central zone covered by beam 34 extends approximately 1.2
degrees; the Midwest zone covered by beam pattern 36 extends
approximately 2.0 degrees, and; the West Coast zone covered by beam
pattern 38 extends approximately 2.0 degrees. The width of each of
the four receive zones 32, 34, 36 and 38 is determined by the
number of terminals and thus the population density in the various
regions of the country. Thus, beam pattern 32 is relatively narrow
to accommodate the relatively high population density in the
Eastern part of the United States while beam pattern 36 is
relatively wide due to the relatively low population density in the
Mountain states. Since each zone utilizes the entire frequency
spectrum, zone widths are narrower in regions where the population
density is high, to accommodate the greater demand for channel
usage.
As shown in FIG. 9, the point-to-point transmit system comprises
four beams T1, T2, T3, T4 respectively covering the four transmit
zones 31, 33, 35, 37, wherein each of the beams T1-T4 consists of a
plurality of individual downlink beams destined for the individual
downlink sites in each zone 31, 33, 35, 37 and carries an
individual signal to that site. The downlink beam signals, destined
to be received at the individual downlink sites, are arranged into
a plurality of channels for each zone. For example, zone 31 may
include a plurality, e.g. sixteen 27 MHz channels with each of such
channels carrying hundreds of individual beam signals to
corresponding downlink sites in zone 32.
The use of multiple downlink zones and downlink zones of unequal
widths assist in causing the intermodulation products, generated by
the later-discussed solid state power amplifiers, to be
geographically disperseed in a manner which prevents most of these
products from being received at the ground terminals. The net
effect is that the amplifiers may be operated more efficiently
because the system can tolerate more intermodulation products.
Although the widths of the transmit zones 31, 33, 35, 37 are nearly
the same as those of the receive zones R1, R2, R3, R4, small
differences between the two sets have been found to optimize the
capacity of the system.
The half power beam width of the individual transmit beams 29 is
substantially narrower than that of the transmit zones 31, 33, 35,
37. This results in the desirable high gain, and avoids the zones
of contention 40, 42, 44 characteristic of the receive zone
arrangement. These individual beams 29 must be steered within the
zones in order to maximize the downlink EIRP in the directions of
the individual destination terminals. The transmit point-to-point
frequency addressable narrow beams 29 are generated by an array 20
whose apparent size is magnified by two confocal parabolas
comprising a main reflector 12b and a subreflector 22. The
east-west direction of each beam 29 is determined by the phase
progression of its signal along the array 106 of transmit elements
20 (FIGS. 13 and 15). This phase progression is established by a
later-discussed beam-forming network 98 and is a function of the
signal frequency. Each of the transmit array elements 20 is driven
by a later-discussed solid state power amplifier. The power
delivered to the array elements 106 is not uniform but is instead
tapered with the edge elements being more than 10 dB down. Tapering
of the beams 29 is achieved by adjusting the transmit gain
according to the position of the transmit array elements 20. The
excitation pattern determines the characteristics of the transmit
secondary pattern, shown in FIG. 9A. Referring to FIG. 9, the
closest spacing between transmit zones 31, 33, 35, 37 occurs
between zones 31 and 33 and is approximately 1.2 degrees. This
means that a signal addressed to zone 33 using a particular
frequency would interfere with a signal using the same frequency in
zone 31 with its side lobe 1.2 degrees from its beam center.
However, the individual transmit gains have been adjusted to
provide low side lobe levels, thereby permitting frequency reuse in
adjacent zones. Referring to FIG. 9A, it is seen that the side lobe
level at this angle off beam center is more than 30 dB down, so
that such interference will be negligibly small. The same frequency
used in zones 35 and 37 are further removed in angle, hence the
side lobe interference in those zones is even smaller.
FIG. 9B is an illustration of the transmit beam pattern in the
north-south direction. The twenty six slots 108 in each of the
transmit waveguide elements 106 are excited in a manner which
creates a nearly flat north-south pattern, extending over the
covered range of plus and minus 1.4 degrees from the north-south
boresight direction.
Both the point-to-point and CONUS systems may utilize the same
uplink and downlink frequency bands, with the point-to-point system
using horizontal polarization for its uplink polarization, and the
CONUS system using vertical polarization, as previously mentioned.
For example, both services may, simultaneously, utilize the entire
500 MHz uplink frequency band between 14 and 14.5 GHz, as well as
the entire 500 MHz downlink frequency band between 11.7 and 12.2
GHz. Each of the receive zones 32, 34, 36, 38 and transmit zones
31, 33, 35, 37, employing the point-to-point service utilizes the
entire frequency spectrum (i.e. 500 MHz). Furthermore, this total
frequency spectrum is divided into a plurality of channels, for
example, sixteen channel each having a usable bandwidth of 27 MHz
and a spacing of 30 MHz. In turn, each of the sixteen channels may
accommodate approximately 800 subchannels. Hence, within each zone,
approximately 12,500 (16 channels.times.800 subchannels) 32 kilobit
per second channels may be accommodated, at any given moment. As
will be discussed below, the communication architecture of the
point-to-point system allows any terminal to communicate directly
with any other terminal. Thus, within a single polarization, a
total of 50,000 subchannels may be accommodated nationwide.
Referring now particular to FIGS. 1, 2, 6, 7 and 16, the
point-to-point receive feed array 16 employs seven receive horns
50-62. Horns 50, 54, 58 and 62 respectively receive signals from
zones 32, 34, 36 and 38. Horns 52, 56 and 60 receive signals from
the zones of contention 40, 42 and 44. Using a series of hybrid
couplers or power dividers C.sub.1 -C.sub.9, the signals received
by horns 50-62 are combined into four outputs 64-70. For example, a
signal originating from the area of contention 44 and received by
horn 60 is divided by coupler C.sub.2 and portions of the divided
signal are respectively delivered to couplers C.sub.1 and coupler
C.sub.4 whereby the split signal is combined with the incoming
signals received by horns 58, 62 respectively. Similarly, signals
originating from the area of contention 42 and received by horn 56
are split by coupler C.sub.5. A portion of the split signal is
combined, by coupler C.sub.3, with the signal output of coupler
C.sub.4, while the remaining portion of the split signal is
combined, by coupler C.sub. 7, with the signal received by horn
54.
Attention is now particularly directed to FIG. 6 which depicts, in
block diagram form, the electronics for receiving and transmitting
signals for both the CONUS and point-to-point systems. The
point-to-point receive signals 64-70 (see also FIG. 7) are derived
from the point-to-point receive feed network in FIG. 7, whereas the
CONUS receive signal 72 derives from the CONUS receive feed horns
14, (FIGS. 1 and 3). Both the point-to-point and CONUS receive
signal are input to a switching network 76 which selectively
connects input lines 64.varies.72 with five corresponding
receivers, eight of which receivers are generally indicated at 74.
The receivers 74 are of conventional design, three of which are
provided for redundancy and are not normally used unless a
malfunction in one of receivers is experienced. In the event of a
malfunction, switching network 76 reconnects the appropriate
incoming line 64-72 with a back-up receiver 74. Receivers 74
function to drive the filters in a filter interconnection matrix
90. The outputs of the receivers 74, which are connected with lines
64-70, are coupled by a second switching network 78 through four
receive lines R1-R4 to a filter interconnection matrix 90. As will
be discussed later below, the filter interconnection matrix (FIM)
provides interconnections between the receives zones 32, 34, 36,
38, and the transmit zones 31, 33, 35, 37. Operating in the
above-mentioned 500 MHz assigned frequency spectrum, separated into
sixteen 27 MHz channels, four sets of sixteens filters are
employed. Each set of the sixteen filters utilizes the entire 500
MHz frequency spectrum and each filter has a 27 MHz bandwidth. As
will be discussed later, the filter outputs T1-T4 are arranged in
four groups, each group destined for one of the four transmit zones
31, 33, 35, 37.
The transmit signals T1-T4 are respectively connected, via
switching network 94, to four of six driving amplifiers 92, two of
such amplifiers 92 being provided for back-up in the event of
failure. In the event of the failure of one of the amplifiers 92,
one of the back-up amplifiers 92 will be reconnected to the
corresponding transmit signal T1-T4 by the switching network 94. A
similar switching network 96 couples the ampliified output of the
amplifiers 92 to a beam-forming network 98. As will be discussed
later in more detail, the beam-forming network 98 consists of a
plurality of transmission delay lines connected at equal intervals
along the four delay lines. These intervals and the width of the
delay lines are chosen to provide the desired centerband beam
squint and the beam scan rate with frequency for the corresponding
transmit zones 31, 33, 35, 37 to be serviced. The transmit signals,
coupled from the four delay lines, are summed in the beam-forming
network 98 as shown in FIGS. 11 and 12, to provide inputs to solid
state power amplifiers 100, which may be embedded in the
point-to-point system's transmit array 20. In the illustrated
embodiment discussed below, forty solid state power amplifiers
(SSPAs) 100 are provided. Each of the SSPAs 100 amplifies a
corresponding one of the forty signals formed by the beam-forming
network 98. The SSPAs 100 possess different power capacities to
provide the tapered array excitation previously mentioned. The
output of the SSPA 100 is connected to the input 112 (FIG. 14) at
one of the elements of the transmit array 20.
The receive signal for CONUS on line 72 is connected to an
appropriate receiver 74 by switching networks 76, 78. The output of
the receiver connected with the CONUS signal is delivered to an
input multiplexer 80 which provides for eight channels, as
mentioned above. The purpose of the input multiplexers 80 is to
divide the one low level CONUS signal into subsignals so that the
subsignals can be amplified on an individual basis. The CONUS
receive signals are highly amplified so that the CONUS transmit
signal may be distributed to very small earth terminals. The
outputs of the input multiplexer 80 are connected through a
switching network 84 to eight of twelve high power traveling wave
tube amplifiers (TWTAs) 82, four of which TWTAs 82 are employed for
back-up in the event of failure. The outputs of the eight TWTAs 82
are connected through another switching network 86 to an output
multiplexer 88 which recombines the eight amplified signals to form
one CONUS transmit signal. The output of the multiplexer 88 is
delivered via waveguide to the transmit horns of the CONUS
transmitter 24 (FIGS. 2 and 3).
Attention is now directed to FIG. 10 which depicts the details of
the FIM 90 (FIG. 6). As previously discussed, the FIM 90
effectively interconnects any terminal in any of the receive zones
32, 34, 36, 38 (FIG. 5) with any terminal in any of the transmit
zones 31, 33, 35, 37. The FIM 90 includes four waveguide inputs
120, 122, 124 and 126 for respectively receiving the receive
signals R1, R2, R3 and R4. As previously mentioned, receive signals
R1-R4, which originate from a corresponding receive zones 32, 34,
36, 38 (FIG. 5), each contain the entire assigned frequency
spectrum, (e.g. 500 MHz), and are separated into a plurality of
channels (e.g. sixteen 27 MHz channels). The channels are further
separated into a plurality of subchannels, where each of the
subchannels carries a signal from a corresponding uplink site. The
FIM 90 includes 64 filters, one of which is indicated by the
numeral 102. Each of the filters 102 has a passband corresponding
to one of the channels (e.g. 1403-1430 MHz). The filters 102 are
arranged in four groups, one for each receive zone 32, 34, 36, 38,
with each group including two banks or subgroups of eight filters
per subgroup. One subgroup of filters 102 contains those filters
for the even-numbered channels and the other subgroup in each group
contains eight filters for the odd-numbered channels. Thus, for
example, the filter group for receive signal R1 comprises subgroup
104 of filters 102 for odd channels, and subgroup 106 of filters
102 for even channels. The following table relates the receive
signals and zones to their filter subgroups:
______________________________________ Filter Subgroups Receive
Zone Receive Signal Odd Channels Even Channels
______________________________________ 32 R1 104 106 34 R2 108 110
36 R3 112 114 38 R4 116 118
______________________________________
The filters are grouped in a unique manner such that when the
receive signals R1-R4 are filtered, the filtered outputs are
combined to form the transmit signals. The transmit signals T1-T4
also utilize the entire assigned frequency spectrum, (e.g. 500
MHz). In the illustrated embodiment, each of the transmit signals
T1-T4 possesses sixteen 27 MHz wide channels, and comprises four
channels from each of the four receive zones 32-38 (FIG. 5).
The incoming receive signals R1-R4 are divided into the
corresponding subgroups by respectively associated hybrid couplers
128-134 which effectively divert 50% of the signal power to each
subgroup. Hence, for example, one-half of the R1 signal input at
waveguide 120 is diverted to transmission line 136 which services
the subgroup 104 of filters 102, and the remaining half of the R1
signal is diverted to transmission line 138 which services subgroup
106 of filters 102. In a similar manner, each of the subgroups
104-118 of filters 102 is served by a corresponding distribution
line, similar to lines 136 and 138.
The construction of subgroup 104 will now be described in more
detail, it being understood that the remaining subgroups 106-118
are identical in architecture to subgroup 104. At intervals along
the transmission line 136, there are eight ferrite circulators 140,
one associated with each of the odd-numbered channel filters 102.
The function of the circulators 140 is to connect the transmission
line 136 to each of the odd channel filters 102 in a lossless
manner. Thus, for example, the R1 signal enters the first circular
140a and circulates it counterclockwise whereby the 27 MHz band of
signals corresponding to channel 1 passes through it to circulator
142. All other frequencies are reflected. These reflected signals
propagate via the circulator toward the next filter where the
process is repeated. Through this process, the R1 receive signal is
filtered into sixteen channels by the sixteen filters 104-108
corresponding to the R1 signals. Hence, the R1 signal with
frequencies in the range of channel 1 will pass through the first
ferrite circulator 140a and it will be filtered by filter 1 of
group 104.
The outputs from a filter subgroup 104-108 are selectively coupled
by a second set of ferrite circulators 142 which sums, in a
criss-cross pattern, the outputs from an adjacent group of filters
102. For example, the outputs of channel filters 1, 5, 9, and 13 of
group 104 are summed with the outputs of channel filters 3, 7, 11
and 15 of filter group 112. This sum appears at the output terminal
for T1 144. Referring to FIG. 8, these signals correspond to the
connections between receive zones R1 and R3 and to transmit zone
T1.
Attention is now directed to FIGS. 8 and 9 which depict how the
transmit and receive signals are interconnected by the FIM 90 to
allow two-way communication between any terminals. Specifically,
FIG. 8 provides a table showing how the receive and transmit zones
are connected together by the interconnect channels while FIG. 9
depicts how these interconnect channels are distributed
geographically across the transmit zones 31, 33, 35, 37. In FIG. 8,
the receive signals R1-R4 are read across by rows of interconnect
channels and the transmit signals T1-T4 are read by columns of
interconnect channels. It can be readily appreciated from FIG. 8
that each of the transmit signals T1-T4 is made up of sixteen
channels arranged in four groups respectively, where each group is
associated with one of the receive signals R1-R4. The satellite
communications system of the present invention is intended to be
used in conjunction with a ground station referred to as a
satellite network control center which coordinates communications
between the ground terminals via packet switched signals. The
network control center assigns an uplink user with an uplink
frequency based on the location of the desired downlink, assigning
the available frequency whose downlink longitude is closest to that
of the destination. The frequency addressable downlink transmit
beams 29 are thus addressed by the frequencies of the uplink
signals. This strategy maximizes the gain of the downlink
signal.
As shown in FIG. 9, the continental United States is divided into
four primary zones 31, 33, 35, 37. Zone 31 may be referred to as
the East Coast zone, zone 33 is the Central zone, zone 35 is the
Mountain zone, and zone 37 is the West Coast zone. As previously
mentioned, each of the zones 31, 33, 35, 37 utilizes the entire
assigned frequency spectrum (e.g. 500 MHz). Thus, in the case of
500 MHz assigned frequency band, there exists sixteen 27 MHz
channels plus guard bands in each of the zones 31, 33, 35, 37.
The numbers 1-16 repeated four times above the beams 29 in FIG. 9
indicate the longitude of the beams corresponding to the center
frequencies of the channels so numbered. Because of the frequency
sensitivity of the beams, the longitude span between the lowest and
highest frequency narrow band signal in a channel is approximately
one channel width. Each beam is 0.6 degrees wide between its half
power point, about half the zone width in the East Coast and
Central zones and nearly one-third the zone width in the Mountain
and West Coast zones. The antenna beams 29 overlap each other to
ensure a high signal density; the more that the beams overlap, the
greater channel capacity in a given area. Hence, in the East Coast
zone 31, there is a greater overlap than in the Mountain zone 35
because the signal traffic in the East Coast zone 31 is
considerably greater than that in the Mountain zone 35.
The interconnect scheme described above will now be explained by
way of a typical communication between terminals in different
zones. In this example, it will be assumed that a caller in
Detroit, Mich. wishes to place a call to a terminal in Los Angeles,
Calif. Thus, Detroit, Mich., which is located in the Central zone
34, is the uplink site, and Los Angeles, Calif., which is located
in the West Coast zone 37, is the downlink destination. As shown in
FIG. 9, each geographic location in the continental United States
can be associated with a specific channel in a specific zone. Thus,
Los Angeles is positioned between channels 14 and 15 in transmit
zone 37.
Referring now concurrently to FIGS. 5, 8, and 9 particularly,
receive and transmit zones R1 and T1 lie within the East Coast zone
32 and 32, R2 and T2 lie within the Central zone 34 and 33, R3 and
T3 lie within the Mountain zone 36 and 35, and R4 and T4 lie within
the West Coast zone 38 and 37. Since Detroit lies in the Central or
R2 zone 34, it can be seen that the only channels over which
signals can be transmitted to the West Coast or T4 zone 37 are
channels 1, 5, 9 and 13. This is determined in the table of FIG. 8
by the intersection of row R2 and column T4. Therefore, from
Detroit, the uplink user would uplink on either channel 1, 5, 9 or
13, whichever of these channels is closest to the downlink
destination. Since Los Angeles is located between channels 14 and
15, the network control center would uplink the signal on channel
13 because channel 13 is the closest to channel 14. The downlink
beam width is broad enough to provide high gain at Los Angeles.
Conversely, if the uplink site is in Los Angeles and the downlink
destination is in Detroit, the intersection of row R4 and column T2
in FIG. 8 must be consulted. This intersection reveals that the
signal can be transmitted on channels 1, 5, 9 or 13 depending upon
which channel is closest to the downlink destination. The network
control center would uplink the signal from Los Angeles on channel
9 since channel 9 is closest to channel 11 which, in turn, is
closest to Detroit.
Returning now to FIG. 10, the conversion of a receive signal to a
transmit signal will be described in connection with the example
mentioned above in which the uplink site is in Detroit and the
downlink site is in Los Angeles. The uplink signal transmitted from
Detroit would be transmitted on channel 13 carried by receive
signal R2. Thus, the R2 receive signal is input to transmission
line 122 and a portion of such input signal is diverted by the
hybrid coupler 130 to the input line of subgroup 108 of filters
102. Subgroup 108 includes a bank of eight filters for the odd
channels, including channel 13. Thus, the incoming signal is
filtered through by filter 13 and is output on a line 164 along
with other signals from subgroups 108 and 116. The channel 13
signal present on line 164, is combined by the hybrid coupler 158,
with signals emanating from subgroup 106 and 114, and forms the T4
signal on output line 150. The transmit signal T4 is then
downlinked to Los Angeles.
It is to be understood that the above example is somewhat
simplified inasmuch as the network control center would assign a
more specific channel than a 27 MHz wide band channel, since the 27
MHz wide channel may actually comprise a multiplicity of smaller
channels, for example, 800 subchannels of 32 KHz bandwidth.
Referring now again to FIGS. 5, 8 and 9, in the event that an
uplink signal originates from one of the areas of contention, 40,
42, 44 (FIG. 5), such signal will not only be transmitted to its
desired downlink destination, but a non-neglible signal will be
transmitted to another geographic area. For example, assume that
the uplink signal originates from Chicago, Ill. which is in the
area of contention 42 and that the signal is destined for Los
Angeles, Calif. The area of contention 42 is produced by the
overlap of the beams forming zones 34 and 36. Hence, the uplink
signal can be transmitted as receive signals R2 or R3. The network
control center determines whether the uplink communication is
carried by receive signals R2 or R3. In the present example, since
Chicago is closer to zone 36, the uplink communication is carried
on receive signal R3.
As previously discussed, the downlink destination, Los Angeles, is
located in zone 37 and lies between channels 14 and 15. As shown in
FIG. 8, the intersection of R3 with column T4 yields the possible
channels over which the communication can be routed. Thus, the
Chicago uplink signal will be transmitted over one of channels 2,
6, 10 or 14. Since Los Angeles is closest to channel 14, channel 14
is selected by the network control center as the uplink channel.
Note, however, that an undesired signals is also transmitted from
zone 34 on channel 14. To determine where the undesired signal will
be downlinked, the table of FIG. 8 is consulted. The table of FIG.
8 reveals that uplink signals carried on channel 14 in the R2 zone
34 are downlinked to the T1 transmit zone 31. The desired signal is
transmitted to Los Angeles and the undesired signal (i.e. an
extraneous signal) is transmitted to the East Coast (i.e. zone 31).
The network control center keeps track of these extraneous signals
when making frequency assignments. The effect of these extraneous
signals is to reduce slightly the capacity of the system.
Referring now again to FIG. 6, the beam-forming network 98 receives
the transmit signals T1-T4 and functions to couple all of the
individual communication signals in these transmit signals together
so that a transmit antenna beam for each signal is formed. In the
example discussed above in which the assigned frequency spectrum is
500 MHz, a total of approximately 50,000 overlapping antenna beams
are formed by the beam-forming network 98 when the system is fully
loaded with narrow band signals. Each antenna beam is formed in a
manner so that it can be pointed in a direction which optimizes the
performance of the system. The incremental phase shift between
adjacent elements determines the direction of the antenna beam.
Since the phase shift is determined by the signal frequency, the
system is referred to as frequency addressed.
Attention is now directed to FIGS. 11 and 12 which depict the
details of the beam-forming network 98. The beam-forming network,
generally indicated by the numeral 98 in FIG. 11, is arranged in
the general form of an arc and may be conveniently mounted on the
communication shelf (not shown) of the satellite. The arc shape of
the beam-forming network 98 facilitates an arrangement which
assures that the paths of the signals passing therethrough are of
correct length.
The beam-forming network 98 includes a first set of
circumferentially extending transmission delay lines 168, 170, a
second set of transmission delay lines 172, 174 which are radially
spaced from delay lines 168 and 170, and a plurality of radially
extending waveguide assemblies 176. In the illustrated embodiment,
forty waveguide assemblies 176 are provided, one for each of the
elements 106 of the transmit array 20 (FIG. 13). The waveguide
assemblies 176 intersect each of the delay lines 168-174 and are
equally spaced in angle.
Each of the waveguide assemblies 176 defines a radial line summer
and intersects each of the delay lines 168-174. As shown in FIG.
12, at the points of intersection, between the radial line summers
176 and the transmission delay lines 168-174, a crossguide coupler
180 is provided. The crossguide coupler 180 connects the delay
lines 168-174 with the radial line summers 176. The function of the
crossguide couplers 180 will be discussed later in more detail.
Four delay lines 168-174 are provided respectively for the four
transmit zones T1-T4 (FIG. 9). Hence, transmit signal T1 is
provided to the input of delay line 170, T2 is provided to input of
delay line 168, T3 is provided to the input of delay line 174, and
T4 is provided to the input of delay line 172. As shown in FIG. 12,
the distance between the radial line summers is indicated by the
letter "l" and the width of each of the radial delay lines is
designated by the letter "w". Although the radial line summers 176
are spaced at equal angular intervals along the delay lines
168-174, the distance between them varies from delay line to delay
line due to the fact that the delay lines 168-174 are radially
spaced from each other. Thus, the further from the center of the
arc, which is formed by the radial line summers 176, the greater
the distance between the radial line summers 176, at the point
where they intersect with the delay lines 168-174. In other words,
the spacing "l" between radial line summers 176 for delay line 168
is less than the spacing between adjacent radial line summers 176
than for delay line 174. Typical values for the dimensions "l" and
"w" are as follows:
______________________________________ Delay Line Signal l, inches
w, inches ______________________________________ 168 T2 1.66 0.64
170 T1 1.72 0.66 172 T4 2.45 0.74 174 T3 2.55 0.76
______________________________________
The width of the delay lines 168-174, "w", and the distance "l"
between adjacent radial line summers are chosen to provide the
desired center beam squint and beam scan rate so that the beam
pointing is correct for each channel. This results in the desired
start and stop point for each of the transmit zones T1-T4.
Referring particularly to FIG. 12, the transmit signal T2
propagates down the delay line 168 for a precise distance, at which
point it reaches the first radial line summer 176. A portion of the
T2 signal passes through the crossguide coupler 180, which may, for
example, be a 20 dB coupler, such that one percent of the
transmitted power of transmit signal T2 is diverted down the radial
line summer 176. This diverted energy then propagates down the
waveguide 176 toward a corresponding solid state power amplifier
100 (FIGS. 6 and 11). This process is repeated for signal T1 which
propagates down delay line 170. The portions of signals T1 and T2
which are diverted by the crossguide couplers 180 (i.e. 0.01 T1 and
0.01 T2) are summed together in the radial line summer 176 and the
combined signal 0.01 (T1+T2) propagates radially outwardy toward
the next set of delay lines 172, 174. This same coupling process is
repeated for signals T3 and T4 in delay lines 174 and 172
respectively. That is, 0.01 of signals T3 and T4 are coupled via
crossguide couplers 180 to the radial line summer 176. The
resulting combined signal 0.01 (T1+T2+T3+T4) propagates radially
outwardly to an associated solid state power amplifier 100 where it
is amplified in preparation for transmission.
After encountering the first radial line summer 176, the remaining
0.99 of signals T1-T4 propagate to the second radial line summer
where an additional one percent of the signals is diverted to the
summer 176. This process of diverting one percent of the signals
T1-T4 is repeated for each of the radial line summers 176.
The signals, propagating through the radial line summers 176
towards the SSPAs 100, are a mixture of all four point-to-point
transmit signals T1-T4. However, each of the transmit signals T1-T4
may comprise 12,500 subsignals. Consequently, the forty signals
propagating through the radial line summers 176 may be a mixture of
all 50,000 signals in the case of the embodiment mentioned above
where the assigned frequency spectrum is 500 MHz wide. Therefore,
each of the SSPAs 100 amplifies all 50,000 signals which emanate
from each of the plurality of wave guide assemblies 176.
Since each of the SSPAs 100 amplifies all 50,000 signals which are
destined for all regions of the country, it can be appreciated that
all of the narrow, high gain downlink beams are formed from a
common pool of transmitters, i.e. all of the SSPAs 100. This
arrangement may be thought of as effectively providing a nationwide
pool of power since each of the downlink beams covering the entire
country is produced using all of the SSPAs 100. Consequently, it is
possible to divert a portion of this nationwide pool of power to
accommodate specific, disadvantaged downlink users on an individual
basis without materially reducing the signal power of the other
beams. For example, a downlink user may be "disadvantaged" by rain
in the donwlink destination which attenuates the signal strength of
the beam. Such a rain disadvantaged user may be individually
accommodated by increasing the signal strength of the corresponding
uplink beam. This is accomplished by diverting to the disadvantaged
downlink beam, a small portion of the power from the pool of
nationwide transmitter power (i.e. a fraction of the power supplied
by all of the SSPAs 100). The power of an individual uplink beam is
proportional to that of the corresponding downlink beam.
Consequently, in order to increase the power of the downlink beam
it is merely necessary to increase the power of the uplink
beam.
In practice, the previously mentioned network control center keeps
track of all of those regions of the country in which it is raining
and determines which of the uplink users are placing communications
to downlink destinations in rain affected areas. The network
control center then instructs each of these uplink users, using
packet switched signals, to increase its uplink power for those
signals destined for a rain affected area. The increase in power of
the uplink user's signals results in greater collective
amplification of these signals by the SSPAs 100, to produce
corresponding downlink beams to the rain affected areas, which have
power levels increased sufficiently to compensate for rain
attenuation. Typically, the number of signals destined for rain
affected areas is small relative to the total number of signals
being handled by the total pool of SSPAs 100. Accordingly, other
downlink users not in the rain affected zones do not suffer
substantial signal loss since the small loss that may occur in
their signals is spread out over the many thousand users.
The SSPAs 100 (FIGS. 8 and 11) may be mounted for example, on the
rim of the communication shelf (not shown) of the satellite. The
signals amplified by the SSPAs 100 are fed into the corresponding
elements 106 of the transmit array 20 (FIGS. 13 and 14).
As previously discussed, an incremental phase shift is achieved
between the signals that are coupled in the forty radial line
summers 176. Hence, the beam-forming network 98 permits the antenna
beams emanating from the transmit array 20 (FIGS. 1, 2, and 13) to
be steered by frequency assignment. The incremental phase shift is
related to the time delay between the waveguides 176 as well as
frequency. Attention is now directed to FIG. 17 which is a
diagrammatic view of four of the forty transmit array elements 106
(FIG. 13), showing the wavefront emanating therefrom, wherein "d"
is equal to the spacing between transmit array elements 106. The
resulting antenna beam has an angular tilt of .theta., where
.theta. is defined as the beam scan angle. This means that .theta.
is the angle from normal of the transmit beam center. The
incremental phase shift produced by the delay line arrangement is
.DELTA..PHI.. The relationship between .DELTA..PHI. and .theta. is
given by ##EQU1## where: .lambda.=signal wavelength
.theta.=beam scan angle
d=spacing between array elements.
Hence, the east-west direction of the antenna beam is determined by
the incremental phase shift which is different for the four delay
lines 168-174 of the beam-forming network 98, resulting in the four
transmit zones T1-T4 previously noted.
Having thus described the invention, it is recognized that those
skilled in the art may make various modifications or additions to
the preferred embodiment chosen to illustrate the invention without
departing from the spirit and scope of the present contribution to
the art. Accordingly, it is to be understood that the protection
sought and to be afforded hereby should be deemed to extend to the
subject matter claimed and all equivalents thereof fairly within
the scope of the invention.
* * * * *