U.S. patent number 6,680,659 [Application Number 10/133,062] was granted by the patent office on 2004-01-20 for integrated circuit interconnect system.
This patent grant is currently assigned to FormFactor, Inc.. Invention is credited to Charles A. Miller.
United States Patent |
6,680,659 |
Miller |
January 20, 2004 |
Integrated circuit interconnect system
Abstract
In an interconnect system for providing access to a common I/O
terminal for multiple circuit devices such as drivers, receivers
and electrostatic protection devices implemented on an IC, each
such device is provided with a separate contact pad within the IC.
The contact pads are linked to one another and to the IC I/O
terminal though inductive conductors such as bond wires,
metalization layer traces in the IC, or legs of a forked,
lithographically-defined spring contact formed on the IC. The
conductor inductance isolates the capacitance of the circuit
devices from one another, thereby improving characteristics of the
frequency response of the interconnect system. The inductances of
the conductors and various capacitances of the interconnect system
are also appropriately adjusted to optimize desired interconnect
system frequency response characteristics.
Inventors: |
Miller; Charles A. (Fremont,
CA) |
Assignee: |
FormFactor, Inc. (Livermore,
CA)
|
Family
ID: |
22979465 |
Appl.
No.: |
10/133,062 |
Filed: |
April 26, 2002 |
Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
Issue Date |
|
|
258185 |
Feb 25, 1999 |
6448865 |
|
|
|
Current U.S.
Class: |
333/33; 257/664;
333/247; 333/260 |
Current CPC
Class: |
H01L
23/5227 (20130101); H01L 23/60 (20130101); H01L
24/49 (20130101); H01L 2223/6611 (20130101); H01L
2224/48091 (20130101); H01L 2224/4813 (20130101); H01L
2224/49113 (20130101); H01L 2924/01005 (20130101); H01L
2924/01006 (20130101); H01L 2924/01014 (20130101); H01L
2924/01022 (20130101); H01L 2924/01028 (20130101); H01L
2924/01039 (20130101); H01L 2924/01074 (20130101); H01L
2924/01079 (20130101); H01L 2924/01083 (20130101); H01L
2924/14 (20130101); H01L 2924/19041 (20130101); H01L
2924/19042 (20130101); H01L 2924/19043 (20130101); H01L
2924/30105 (20130101); H01L 2924/30107 (20130101); H01L
2924/3011 (20130101); H01L 2224/48091 (20130101); H01L
2924/00014 (20130101); H01L 24/48 (20130101); H01L
2924/01019 (20130101); H01L 2924/01023 (20130101); H01L
2924/014 (20130101); H01L 2924/00014 (20130101); H01L
2924/00014 (20130101); H01L 2224/45099 (20130101); H01L
2924/00014 (20130101); H01L 2224/05599 (20130101); H01L
2924/30111 (20130101); H01L 2924/30111 (20130101); H01L
2924/00 (20130101); H01L 2924/12042 (20130101); H01L
2924/12042 (20130101); H01L 2924/00 (20130101) |
Current International
Class: |
H01L
23/58 (20060101); H01L 23/52 (20060101); H01L
23/60 (20060101); H01L 23/522 (20060101); H03H
007/01 () |
Field of
Search: |
;333/32,33,247,260
;257/664,773 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Pascal; Robert
Assistant Examiner: Jones; Stephen E.
Attorney, Agent or Firm: Smith-Hill and Bedell
Parent Case Text
CROSS-REFERENCE TO RELATED APPLICATIONS
This application is a continuation of U.S. patent application Ser.
No. 09/258,185 filed Feb. 25, 1999 now U.S. Pat. No. 6,448,865.
The subject matter of the present application is related to that of
U.S. patent application Ser. No. 09/258,184 filed Feb. 25, 1999,
now U.S. Pat. No. 6,218,225.
The subject matter of the present application is also related to
that of U.S. patent application Ser. No. 09/258,186 filed Feb. 25,
1999, now U.S. Pat. No. 6,218,910.
Claims
What is claimed is:
1. A method of manufacturing an interconnect system for conveying
signals between first and second nodes within an integrated circuit
and an external node outside the integrated circuit, the first and
second nodes each comprising capacitive impedance, the method
comprising the steps of: a. providing a first conductive path
comprising inductive impedance extending from the first node to the
external node; b. providing a second conductive path comprising
inductive impedance extending from the second node to the first
node; c. selecting a characteristic of a frequency response of the
interconnect system between the external node and one of the first
and second nodes; d. evaluating a function of the impedances of the
first and second conductive paths and the first and second nodes,
to calculate a magnitude of a capacitance at the external node
which will substantially optimize the frequency response
characteristic selected at step c; and e. adjusting the capacitance
at the external node to approximate the magnitude calculated at
step d.
2. The method in accordance with claim 1 wherein the function
models the interconnect system as a filter formed by interconnected
impedances comprising the impedances of the first and second
conductive paths, the impedances of the first and second nodes, and
the capacitance at the external node.
3. The method in accordance with claim 2 wherein the frequency
response characteristic selected at step c is optimized when the
magnitude of the capacitance at the external node causes the
interconnect system to operate as a Butterworth filter.
4. The method in accordance with claim 2 wherein the frequency
response characteristic selected at step c is optimized when the
magnitude of the capacitance at the external node causes the
interconnect system to operate as a Chebyshev filter.
5. The method in accordance with claim 1 wherein the frequency
characteristic selected at step c comprises a bandwidth of the
interconnect system and is optimized when maximized.
6. The method in accordance with claim 1 wherein the frequency
characteristic selected at step c comprises a combination of
bandwidth and roll-off of the interconnect system.
7. The method in accordance with claim 1 wherein the first
conductive path comprises a first bond wire extending from the
first node to the external node; and wherein the second conductive
path comprises a second bond wire extending from the first node to
the second node.
8. The method in accordance with claim 1 wherein the second
conductive path comprises a spiral inductor formed on the IC.
9. The method in accordance with claim 1 wherein the external node
comprises a trace on a printed circuit board, and wherein the
capacitance at the external node is adjusted at step e by forming a
via in the printed circuit board, the via being connected to the
trace and adding capacitance to the external node such that the
capacitance at the external node approximates the capacitance
magnitude calculated at step d.
10. A method of manufacturing an interconnect system for conveying
a signal between a communication circuit implemented within an
integrated circuit and an external node outside the integrated
circuit, the communication circuit comprising capacitive impedance,
the method comprising the steps of: a. forming an electrostatic
discharge (ESD) protection device comprising capacitive impedance
within the integrated circuit; b. providing a first conductive path
comprising inductive impedance extending from the ESD protection
device to the external node; c. providing a second conductive path
comprising inductive impedance extending from the communication
circuit to the ESD protection device; d. selecting a characteristic
of a frequency response of the interconnect system between the
communication circuit and the external node; e. evaluating a
function of the impedances of the first and second conductive
paths, the ESD protection device and the communication circuit to
calculate a magnitude of a capacitance at the external node which
will substantially optimize the frequency response characteristic
selected at step d; and f. adjusting the capacitance at the
external node to approximate the magnitude calculated at step
e.
11. The method in accordance with claim 10 wherein the function
models the interconnect system as a filter formed by interconnected
impedances comprising the impedances of the first and second
conductive paths, the ESD protection device, the communication
circuit and the capacitance at the external node.
12. The method in accordance with claim 11 wherein the frequency
response characteristic selected at step d is optimized when the
magnitude of the capacitance at the external node causes the
interconnect system to operate as a Butterworth filter.
13. The method in accordance with claim 11 wherein the frequency
response characteristic selected at step d is optimized when the
magnitude of the capacitance at the external node causes the
interconnect system to operate as a Chebyshev filter.
14. The method in accordance with claim 10 wherein the frequency
characteristic selected at step d comprises a bandwidth of the
interconnect system and is optimized when maximized.
15. The method in accordance with claim 10 wherein the frequency
characteristic selected at step d comprises a combination of
bandwidth and roll-off of the interconnect system.
16. The method in accordance with claim 10 wherein the first
conductive path comprises a first bond wire extending from the ESD
protection device to the external node; and wherein the second
conductive path comprises a second bond wire extending from the ESD
protection device to the communication circuit.
17. The method in accordance with claim 10 wherein the second
conductive path comprises a spiral inductor formed on the IC.
18. The method in accordance with claim 10 wherein the external
node comprises a trace on a printed circuit board, and wherein the
capacitance at the external node is adjusted at step f by forming a
via in the printed circuit board, the via being connected to the
trace and adding capacitance to the external node such that a total
capacitance at the external node approximates the magnitude
calculated at step e.
19. A method of manufacturing an interconnect system for conveying
signals between a driver and a receiver implemented within an
integrated circuit and an external node outside the integrated
circuit, the driver having capacitive output impedance and the
receiver having capacitive input impedance, the method comprising
the steps of: a. providing an electrostatic discharge (ESD)
protection device comprising capacitive impedance within the
integrated circuit; b. providing a first conductive path comprising
inductive impedance linking the ESD protection device to the
external node; c. providing a second conductive path comprising
inductive impedance extending from the driver to the ESD protection
device; d. providing a third conductive path extending from the
receiver to the ESD protection device; e. selecting frequency
response characteristics of the interconnect system between the
driver and receiver and the external node; f. evaluating a function
of the impedances of the driver, the receiver, the first and second
conductive paths, and the ESD protection device, to calculate a
magnitude of a capacitance at the external node which will
substantially optimize the frequency response characteristics
selected at step e; and g. adjusting the capacitance at the
external node to approximates the magnitude calculated at step
f.
20. The method in accordance with claim 19 wherein the function
models the interconnect system as a filter formed by interconnected
impedances comprising the impedances of the first and second
conductive paths, the ESD protection device, the communication
circuit and the capacitance at the external node.
21. The method in accordance with claim 20 wherein the frequency
response characteristic selected at step e is optimized when the
magnitude of the capacitance at the external node causes the
interconnect system to operate as a Chebyshev filter.
22. The method in accordance with claim 19 wherein the frequency
response characteristic selected at step e is optimized when the
magnitude of the capacitance at the external node causes the
interconnect system to operate as a Butterworth filter.
23. The method in accordance with claim 19 wherein the frequency
characteristic selected at step e comprises a bandwidth of the
interconnect system and is optimized when maximized.
24. The method in accordance with claim 19 wherein the frequency
characteristic selected at step e comprises a combination of
bandwidth and roll-off of the interconnect system.
25. The method in accordance with claim 19 wherein the first
conductive path comprises a first bond wire; wherein the second
conductive path comprises a second bond wire; and wherein the third
conductive path comprises a third bond wire.
26. The method in accordance with claim 19 wherein the second
conductive path comprises a first spiral inductor formed on the IC;
and wherein the third conductive path comprises a second spiral
inductor formed on the IC.
27. The method in accordance with claim 19 wherein the external
node comprises a trace on a printed circuit board, and wherein the
capacitance at the external node is adjusted at step g by forming a
via in the printed circuit board, the via being connected to the
trace and adding capacitance to the external node such that a total
capacitance at the external node approximate the magnitude
calculated at step f.
Description
BACKGROUND OF THE INVENTION
1. Field of the Invention
The present invention relates in general to a system for
interconnecting multiple devices implemented in an integrated
circuit (IC) to a circuit node external to the IC, and in
particular to a system employing appropriately-sized inductors and
capacitors to isolate and impedance match the IC devices to enhance
interconnect system frequency response.
2. Description of Related Art
In an integrated circuit (IC), each signal transmitter or receiver
device that communicates with a circuit node external to the IC is
typically linked to a bond pad on the surface of the IC's
substrate. In a typical packaged IC a bond wire connects the bond
pad to a conductive leg or pin extending from the package
surrounding the IC. When the IC package is mounted on a printed
circuit board (PCB), the package leg is soldered to a microstrip
PCB trace on the surface of the PCB or to a via connected to a
stripline conductor on another layer of the PCB. When bond pads of
one or more other ICs mounted on the PCB are linked to the PCB
trace in a similar manner, the bond pads, bond wires, package legs,
and the PCB trace form an interconnect system for conveying signals
between devices implemented in two or more ICs. Many ICs also
include electrostatic discharge protection devices (ESDs) also
connected to each bond pad to protect the IC from high voltage
noise spikes.
In high frequency applications a combination of series inductances
and shunt capacitances in the signal path provided by the
interconnect system attenuate and distort signals. The bond wire
and package leg typically contribute most of the series inductance.
The capacitance of any IC driver, receiver and/or ESD device
connected to the bond pad and the capacitance of any device
connected to the PCB trace (such as for example, a via) provide
most of the interconnect system capacitance. The conventional
approach to reducing the amount of signal distortion and
attenuation caused by the interconnect system has been to minimize
the series inductance and shunt capacitance of the interconnect
system. The inductance of bond wires and package legs can be
minimized by keeping them as small as possible. Driver, receiver
and ESD capacitances can be controlled to some extent by
controlling shapes and dimensions of structures within the IC. The
PCB trace impedance can be controlled by appropriately choosing
physical characteristics of the trace such as its width and length,
its spacing from ground planes and dielectric nature of the
insulating material forming the circuit board. Vias, conductors
passing vertically through a circuit board to interconnect PCB
traces on various layers of the PCB, can be a source of capacitance
along the PCB trace. Designers avoid the use of vias in high
frequency applications in order to limit the shunt capacitance of
the interconnect system. When vias are unavoidable, designers
typically structure them so as minimize their capacitance. Although
minimizing the inductance of the bond wire and package leg, the
capacitances of the trace, drivers, receivers and ESD devices can
help increase the bandwidth, flatten frequency response and reduce
the signal distortion, it is not possible to completely eliminate
interconnect system inductance and capacitance. Thus some level of
signal distortion and attenuation is inevitable when signal
frequencies are sufficiently high.
What is needed is a way to substantially improve various
characteristics of frequency response of the interconnect system
beyond that which is attainable by reducing interconnect system
inductances and capacitances to minimum attainable values.
SUMMARY OF THE INVENTION
An interconnect system in accordance with the invention provides a
signal path between multiple devices such as drivers, receivers and
electrostatic protection devices implemented on an integrated
circuits (IC) and a single external circuit node such as a printed
circuit board (PCB) trace.
In accordance with one aspect of the invention, each such device is
connected to a separate contact on the IC. The separate contacts
are interconnected to one another and to the trace by inductive
conductors. The conductor inductance isolates the device
capacitances from one another, thereby improving various
characteristics of the frequency response of the interconnect
system, for example, by increasing bandwidth and decreasing signal
distortion.
In accordance with another aspect of the invention the inductive
conductors are bond wires.
In accordance with a further aspect of the invention, in an
alternative embodiment thereof, the inductive conductors are
separate legs of a forked, lithographically-defined spring
contact.
In accordance with a further aspect of the invention, in an
alternative embodiment thereof, the inductive conductors include
lithographically-defined traces formed on a metalization layer of
the IC die.
In accordance with yet another aspect of the invention, capacitance
is added to the PCB trace, suitably by an appropriately dimensioned
via. The magnitude of the conductor inductances and of the added
trace capacitance are appropriately adjusted to optimize
characteristics of the interconnect system frequency response.
It is accordingly an object of the invention to provide a system
for interconnecting integrated circuits having an improved
frequency response.
The concluding portion of this specification particularly points
out and distinctly claims the subject matter of the present
invention. However those skilled in the art will best understand
both the organization and method of operation of the invention,
together with further advantages and objects thereof, by reading
the remaining portions of the specification in view of the
accompanying drawing(s) wherein like reference characters refer to
like elements.
BRIEF DESCRIPTION OF THE DRAWING(S)
FIG. 1 is a plan view of two integrated circuits (ICs) and a prior
art structure for interconnecting them,
FIG. 2 is an equivalent circuit diagram modeling the electrical
behavior of input/output devices of the ICs of FIG. 1 and the prior
art structure interconnecting them,
FIG. 3 illustrates the frequency response of the equivalent circuit
of FIG. 2,
FIG. 4 is a plan view of two integrated circuits (ICs) and an
interconnect system for interconnecting them in accordance with the
present invention,
FIG. 5 is an equivalent circuit diagram modeling the electrical
behavior of input/output devices of the ICs of FIG. 4 and the
interconnect structure interconnecting them,
FIG. 6 illustrates the frequency response characteristics of the
equivalent circuit of FIG. 5,
FIG. 7 is a plan view of two ICs and an interconnect system for
interconnecting them in accordance with a first alternative
embodiment of the present invention,
FIG. 8 is an equivalent circuit diagram modeling the electrical
behavior of input/output devices of the ICs of FIG. 7 and the
interconnect structure interconnecting them,
FIG. 9 illustrates the frequency response characteristics of the
equivalent circuit of FIG. 8,
FIG. 10 is a plan view of two ICs and an interconnect system for
interconnecting them in accordance with the present invention,
FIG. 11 is an equivalent circuit diagram modeling the electrical
behavior of input/output devices of the ICs of FIG. 10 and the
interconnect structure interconnecting them,
FIG. 12 illustrates the frequency response characteristics of the
equivalent circuit of FIG. 11,
FIG. 13 is a plan view of an integrated circuit and an interconnect
system in accordance with the present invention for interconnecting
multiple devices implemented in the integrated circuit to a printed
circuit board trace,
FIG. 14 is a plan view of an integrated circuit and an interconnect
system in accordance with the present invention for interconnecting
multiple devices implemented in the integrated circuit to a printed
circuit board trace,
FIG. 15 is a plan view of an integrated circuit and an interconnect
system in accordance with an alternative embodiment of the present
invention for interconnecting multiple devices implemented in the
integrated circuit to a printed circuit board trace,
FIG. 16 is a plan view of an integrated circuit and an interconnect
system in accordance with the present invention for interconnecting
multiple devices implemented in the integrated circuit to a printed
circuit board trace, and
FIG. 17 is sectional elevation view of an integrated circuit and an
interconnect system in accordance with the present invention for
interconnecting multiple devices implemented in the integrated
circuit to a printed circuit board trace.
DESCRIPTION OF THE PREFERRED EMBODIMENT(S)
Prior Art Interconnect System
The present invention can be considered as an improvement to a
prior art interconnect system for conveying signals between
integrated circuits mounted on a printed circuit board. FIG. 1 is a
simplified plan view of the prior art interconnect system,
including a printed circuit board (PCB) 10 upon which is mounted a
pair of integrated circuit (IC) devices 12 and 14. IC device 12
includes an IC 16 contained within an IC package 18. A bond pad 20
on the surface of IC 16 acts as an input/output (I/O) terminal for
signals entering or departing IC 16. A typical IC has several
input/output terminals and will therefore include several bond
pads. However for simplicity only one bond terminal (package leg
24) is shown in FIG. 1. A bond wire 22 links bond pad 20 to a
conductive pin or leg 24 extending outward from package 18. Leg 24
is typically soldered onto a microstrip PCB trace 26 on the surface
of PCB 10. When a bond pad 28 on an IC 17 within IC device 14 is
connected to microstrip PCB trace 26 in a similar manner through a
bond wire 27 and a package leg 29, devices connected to bond pads
20 and 28 can communicate with one another via the signal path
formed by bond pads 20 and 28, bond wires 22 and 27, package legs
24 and 29, and PCB trace 26.
In the example of FIG. 1, IC 16 includes a conventional driver
circuit 30 for transmitting an analog or digital signal outward via
bond pad 20 while IC 17 includes a receiver circuit 32 for
receiving an incoming analog or digital signal arriving at bond pad
28. ICs 16 and 17 also include conventional electrostatic discharge
protection devices (ESDs) 34 and 36 connected to bond pads 20 and
28, respectively, for protecting the ICs from high voltage noise
spikes.
FIG. 2 is an equivalent circuit diagram modeling devices within ICs
16 and 17 of FIG. 1 and the various structures interconnecting
them. Driver 30 is modeled as an ideal signal source V.sub.in
transmitting a signal to pad 20 through a resistance R1. The
capacitance to ground at bond pad 20 is modeled as a single
capacitor C1 which includes the sum of the output capacitance of
driver 30 and the input capacitance of ESD 34. Bond wire 22 and
package leg 24 are primarily inductive at higher signal frequencies
and therefore can be modeled as a single inductor L1. Receiver 32
is modeled as an ideal signal receiver V.sub.OUT having input
impedance R2 connected to bond pad 28. The capacitance at bond pad
28 is modeled as a single capacitor C2 that includes the sum of
capacitances of ESD 36 and receiver 32. Bond wire 27 and package
leg 29 are modeled as a single inductor L2. Trace 26 is modeled by
its characteristic impedance Z0. Since no major source of
capacitance outside of ICs 12 and 16 is connected to PCB trace 26,
then assuming trace 26 is designed for low capacitance, the PCB
trace capacitance is assumed to be substantially 0.
The system interconnecting driver V.sub.in and receiver V.sub.out
can substantially attenuate and distort high frequency signals
passing between driver 30 and receiver 32. The conventional
approach to reducing the amount of signal distortion and
attenuation in high frequency applications has been to minimize the
series inductance and shunt capacitances in the path between
V.sub.in and V.sub.out. Following this approach, designers of prior
art interconnect systems have avoided the use of vias on trace 26
and have carefully designed trace 26 to substantially eliminate its
capacitance. Inductances L1 and L2 are typically minimized by
keeping bond wires 20, 27 and package legs 24, 29 as small as
possible. The capacitances C1 and C2 at bond pads 20 and 28 can be
reduced to some extent by controlling various structural
characteristics of IC 16 and IC 17.
Table I below illustrates typical impedance values for L1, L2, C1
and C2 for the prior art interconnect system equivalent circuit of
FIG. 2. The 50 Ohm impedance values for R1, R2 and Z0 are typical
in high frequency applications. The 1 nH and 2 pF capacitance
values are typical of minimum practically obtainable values.
TABLE I ELEMENT IMPEDANCE L1 1 nH L2 1 nH C1 2 pF C2 2 pF Z0 50
Ohms R.sub.1 50 Ohms R.sub.2 50 Ohms
FIG. 3 illustrates the frequency response characteristics of the
prior art interconnect system of FIG. 2 when components are set to
the values indicated in Table I. If we define the upper limit of
the passband as the minimum frequency at which attenuation is -3
dB, then FIG. 3 shows that the prior art interconnect system of
FIGS. 1 and 2 has a 2 GHz bandwidth. Note that since the passband
is not particularly flat between 0 and 2 GHz, the interconnect
system will distort signals because it will attenuate some signal
frequencies in the passband substantially more than others. In many
applications it is desirable that the stopband (in this example,
frequencies above 2 GHz) should fall off quickly so as to
substantially attenuate higher frequency signal noise. However note
that FIG. 3 shows the stopband has several large peaks at various
resonant frequencies. The prior art interconnect system therefore
may fail to sufficiently attenuate noise at those resonant
frequencies.
Optimal frequency response characteristics for an interconnect
system depends on the system's application. For example, when the
interconnect system is to convey an analog signal with little
distortion or noise, it is usually desirable that the passband be
only as wide as needed to pass the highest expected frequency
component of the signal. However the passband should be as flat as
possible to avoid signal distortion, and the stopband should drop
off quickly so as to block high frequency noise. FIG. 3 shows that
the passband of prior art interconnect system of FIGS. 1 and 2 is
not wide enough to accommodate signals above 2 GHz. Also the
passband ripple above about 0.5 GHz may make the interconnect
system unsuitable for signal frequencies above 0.5 GHz when only
low levels of distortion can be tolerated. Finally, since the
frequency response illustrated in FIG. 3 fails to fall off rapidly
in the stop band, the prior art interconnect system may be
unsuitable in any application in which it is important to severely
attenuate high frequency noise.
Improved Interconnect System
FIG. 4 illustrates a PCB 50 implementing an improved interconnect
system in accordance with the present invention, for
interconnecting a driver 40 within an IC 42 to a receiver 44 within
an IC 46. ICs 42 and 46 also include conventional electrostatic
discharge protection devices (ESDs) 48 and 50 for protecting the
ICs from voltage spikes. In accordance with the invention, separate
bond pads 52A, 52B, 54A and 54B are provided for driver 40, ESD 48,
receiver 44 and ESD 50, respectively. Bond pads 52A and 52B are
connected to a package pin or leg 56 through separate bond wires
58A and 58B. Similarly, bond pads 54A and 54B are connected to a
package pin or leg 60 through separate bond wires 62A and 62B.
Package legs 56 and 60 are connected to a trace 64 on the surface
of a printed circuit board (PCB) 66.
FIG. 5 is an equivalent circuit diagram of the interconnect system
of FIG. 4. Driver 40 of FIG. 4 is represented in FIG. 5 as an ideal
source V.sub.in connected to pad 52A through resistance R1.
Receiver 44 of FIG. 4 is represented in FIG. 5 as an ideal receiver
V.sub.out having input resistance R2 connected to pad 54A. Bond
wires 58A, 58B, 62A and 62B are modeled as inductances L1.sub.A,
L1.sub.B, L2.sub.A, and L2.sub.B, respectively. The parameters
K.sub.1 and K.sub.2 are the mutual inductance factors for inductors
L1.sub.A and L1.sub.B and for inductors L2.sub.A and L2.sub.B. The
values of K.sub.1 and K.sub.2 may be adjusted by adjusting the
acute angle and distance between bond wires 58A and 58B or 62A and
62B. The capacitances of driver 40, ESD 48, receiver 44 and ESD 50
are represented in FIG. 5 as capacitors C1.sub.DRV, C1.sub.ESD,
C2.sub.RCV and C2.sub.ESD, respectively. Trace 64 is represented in
FIG. 5 by its characteristic impedance Z0.
The equivalent circuit of FIG. 5 differs from the prior art
equivalent circuit of FIG. 2. In FIG. 2 the driver and ESD
capacitances C1.sub.DRV and C1.sub.ESD appear in parallel and are
represented by a single capacitor C1. In FIG. 5, due to the
separation of bond pads 52A and 52B and the use of separate bond
wires 58A and 58B to connect them to package leg 56, the driver and
ESD capacitances C1.sub.DRV and C1.sub.ESD are isolated from one
another though inductances L1.sub.A and L1.sub.B of bond wires 58A
and 58B. Similarly, the receiver and ESD capacitances C2.sub.RCV
and C2.sub.ESD are isolated from one another though inductances
L2.sub.A and L2.sub.B of bond wires 62A and 62B. As discussed
below, by isolating ESD capacitances C1.sub.ESD and C2.sub.ESD from
the main signal path we improve interconnect system frequency
response.
Table II below compares impedance values of the prior art
interconnect system of FIG. 2 (Table I) with impedance values of
the improved interconnect system of FIG. 5 when selected in
accordance with the present invention.
TABLE II PRIOR ART IMPROVED L1 1 nH L1.sub.A 2.6 nH L1.sub.B 0.6 nH
L2 1 nH L2.sub.A 2.6 nH L2.sub.B 0.6 nH C1 2 pF C1.sub.DRV 0.7 pF
C1.sub.ESD 1.3 pF C2 2 pF C2.sub.RCV 0.7 pF C2.sub.ESD 1.3 pF Z0 50
Ohms Z0 50 Ohms R1 50 Ohms R1 50 Ohms R2 50 Ohms R2 50 Ohms
K.sub.1, K.sub.2 0.9
Note that in the improved interconnect system the sum of
capacitances of C1.sub.DRV and C1.sub.ESD and the sum of
capacitances C2.sub.RCV and C2.sub.ESD are each 2.0 pf, the value
of capacitances C1 and C2 of the prior art interconnect system.
Thus the capacitances of the drivers, receivers and ESD devices are
the same for both prior art and improved interconnect systems in
this example. Values of R1, R2 and Z0 are also the same for prior
art and improved interconnect systems. Note, however, that because
the interconnect system of FIG. 4 uses more and longer bond wires
than the circuit of FIG. 1, the total interconnect system
inductance L1.sub.A +L1.sub.B +L2.sub.A +L2.sub.B (6.4 nH) of the
improved interconnect system of FIG. 4 is much larger then the
total inductance L1+L2 (2 nH) of the prior art interconnect system
of FIG. 1. Since conventional practice holds that frequency
response is improved by reducing interconnect system inductance,
not by increasing it, we might expect that with all other
interconnect system component values being the same, the prior art
interconnect system of FIG. 1 would have a better frequency
response than the "improved" interconnect system of FIG. 4. However
such is not the case.
FIG. 6 illustrates the frequency response of the interconnect
system of FIG. 5 in accordance with the invention. FIG. 6 shows
that the bandwidth of the interconnect system of FIG. 4 is
approximately 6 GHz, substantially larger than the 2 GHz bandwidth
of the prior art system as illustrated in FIG. 3. This improvement
in bandwidth arises because the bond wire inductances L1.sub.B and
L2.sub.B isolate the ESD capacitances C1.sub.ESD and C2.sub.ESD
from the main signal path. Thus when wide bandwidth is desired, it
is beneficial to increase L1.sub.B and L2.sub.B to the extent
possible without affecting the ability of ESDs 48 and 50 to provide
adequate protection from electrostatic noise spikes. Note too that
the passband (0-6 GHz) as seen in FIG. 6 is relatively flatter (has
less ripple) than the passband (0-2 GHz) illustrated in FIG. 3.
This means that the improved interconnect system of FIG. 4 will
pass signals with much less distortion than the prior art
interconnect system of FIG. 1.
Thus it is seen that the frequency response of an interconnect
system is not necessarily degraded when we increase its inductance
above minimum, provided that we appropriately arrange that
inductance in accordance with the present invention so that it
isolates capacitive elements employing the interconnect from each
other.
Alternative Embodiment
FIG. 7 illustrates a PCB 80 implementing an alternative embodiment
of the interconnect system in accordance with the present invention
for interconnecting a driver 70 within an IC 72 to a receiver 74
within an IC 76. ICs 72 and 76 also include conventional ESDs 78
and 80 for protecting the ICs from voltage spikes. Separate bond
pads 82A, 82B, 84A and 84B are provided for driver 70, ESD 78,
receiver 74 and ESD 80, respectively. Bond pad 82A is connected to
bond pad 82B through a bond wire 88A while bond pad 82B is
connected to a package leg 86 though a bond wire 88B. Similarly,
bond pad 84A is connected to bond pad 84B though a bond wire 92A
while bond pad 84B is connected to a package leg 90 through a bond
wire 92B. Package legs 86 and 90 are connected to a trace 94 on the
surface of a printed circuit board (PCB) 96 on which ICs 72 and 76
are mounted.
FIG. 8 is an equivalent circuit diagram of the interconnect system
of FIG. 7. Driver 70 of FIG. 7 is represented in FIG. 8 as an ideal
source V.sub.in connected to pad 82A through the driver's output
resistance R1. Receiver 74 of FIG. 7 is represented in FIG. 8 as an
ideal receiver V.sub.out having input resistance R2 connected to
pad 84A. Bond wires 88A, 88B, 92A and 92B and package legs 86 and
90 of FIG. 7 are modeled in FIG. 8 as inductances L1.sub.A,
L1.sub.B, L2.sub.A, and L2.sub.B, respectively. This embodiment
also shows that improved interconnect system performance is
realized with the constraint that
Since bond wires 88A and 88B are substantially perpendicular, their
mutual inductance is negligibly small. The mutual inductance
between bond wires 92A and 92B is also small. The capacitances of
driver 70, ESD 78, receiver 74 and ESD 80 are represented in FIG. 8
as capacitors C1.sub.DRV, C1.sub.ESD, C2.sub.RCV and C2.sub.ESD,
respectively. Trace 94 is represented in FIG. 8 by its
characteristic impedance Z0.
Table III below lists suitable impedance values of the interconnect
system of FIG. 8.
TABLE III L1.sub.A 1.4 nH L1.sub.B 1.4 nH L2.sub.A 1.4 nH L2.sub.B
1.4 nH C1.sub.DRV 0.7 pF C1.sub.ESD 1.3 pF C2.sub.RCV 0.7 pF
C2.sub.ESD 1.3 pF Z0 50 Ohms R1 50 Ohms R2 50 Ohms
Note that all component values are similar to those used when
determining the frequency response (FIG. 6) of the interconnect
system of FIG. 4 (see Table II, "Improved" column) except for
differences in bond wire inductances L1.sub.A, L1.sub.B, L2.sub.A
and L2.sub.B and lack of mutual inductance K arising from the
difference in bond wire layout.
FIG. 9 illustrates the frequency response (plot A) of the
interconnect system of FIG. 8 wherein the values of various
components are set in accordance with Table III. Plot A of FIG. 9
shows that the bandwidth of the interconnect system of FIG. 7 is
approximately 4 GHz, smaller than the 6 Ghz bandwidth of the
interconnect system of FIG. 4, but still substantially larger than
the 2 GHz bandwidth of the prior art system as illustrated in FIG.
1. The bandwidth of the interconnect system of FIG. 7 is not as
wide as that of the system of FIG. 4 primarily because inductors
L1.sub.B and L.sub.2B are series inductances whereas in the system
of FIG. 7 they are shunt inductances. Note that even though the
total series inductance in the improved system of FIG. 7 (5.02 nH)
substantially larger than the total series inductance (2 nH) in the
prior interconnect system of FIG. 1, the system of FIG. 7 has
approximately twice the bandwidth.
While the bandwidth (4 GHz) of the interconnect system of FIG. 7 is
smaller than the 6 GHz bandwidth of the system of FIG. 4, the
interconnect system of FIG. 4 may be preferable in applications
where the wider bandwidth is not needed because the frequency
response of the system of FIG. 4 has sharper roll off and no major
spikes in the stopband above 4 GHz. This means that the system of
FIG. 7 will do a better job of blocking high frequency noise than
the system of FIG. 4.
Adjusting Inductance
The frequency response of the circuits of FIGS. 4 and 7 can be
further improved by appropriately adjusting the bond wire
inductance, for example, by adjusting their lengths and widths and
by adjusting the angle between adjacent bond wires so as to affect
their mutual inductance. Table IV below compares impedance values
for the interconnect circuit of FIG. 8 used when computing
frequency response plot A of FIG. 9 (Table III) to impedance values
for the circuit of FIG. 8 used when computing another frequency
response plot (Plot B) of FIG. 8.
TABLE IV PLOT A PLOT B L1.sub.A 1.4 nH 1.50 nH L1.sub.B 1.4 nH 0.65
nH L2.sub.A 1.4 nH 1.50 nH L2.sub.B 1.4 nH 0.65 nH C1.sub.DRV 0.7
pF 0.7 pF C1.sub.ESD 1.3 pF 1.3 pF C2.sub.RCV 0.7 pF 0.7 pF
C2.sub.ESD 1.3 pF 1.3 pF Z0 50 Ohms 50 Ohms R1 50 Ohms 50 Ohms R2
50 Ohms 50 Ohms
Note that except for differences in bond wire inductances, the
component values used to compute frequency response B are similar
to the value used when determining frequency response A. Note that
frequency response B has a bandwidth of about 6 GHz instead of 4
GHz. Thus while interconnect system frequency response can be
improved by adding and appropriately arranging inductance to the
interconnect system, frequency response may be further improved by
appropriately sizing that inductance.
Adding and Adjusting Capacitance
As previously mentioned, the conventional approach to reducing the
amount of signal distortion and attenuation caused by the
interconnect system has been to minimize the inductance of the
interconnect system. Since it is not possible to completely
eliminate interconnect system inductance, an unacceptable level of
signal distortion and attenuation is inevitable when signal
frequencies are sufficiently high. However as discussed above,
further improvements in interconnect system frequency response can
be had by actually increasing system inductance and appropriately
arranging it. The same considerations apply to interconnect system
capacitance. Conventional wisdom holds that interconnect system
frequency response is improved by minimizing system capacitance to
its lowest practically attainable level. However while most values
of additional PCB capacitance do degrade the frequency response of
the interconnect system, appropriately adjusted higher values of
PCB capacitance can substantially improve various characteristics
of system frequency response.
FIG. 10 illustrates a PCB 110 implementing another alternative
embodiment of the interconnect system in accordance with the
present invention for interconnecting a driver 100 within an IC 102
to a receiver 104 within an IC 106. ICs 102 and 106 also include
conventional ESDs 108 and 110. Separate bond pads 112A, 112B, 114A
and 114B are provided for driver 100, ESD 108, receiver 104 and ESD
110, respectively. Bond pad 112A is connected to bond pad 112B
through a bond wire 118A while bond pad 112B is connected to a
package leg 116 though a bond wire 122B. Similarly, bond pad 114A
is connected to bond pad 114B though a bond wire 122A while bond
pad 114B is connected to a package leg 120 through a bond wire
122B. Package legs 116 and 120 are connected to a trace 124 on the
surface of a PCB 126 on which ICs 72 and 76 are mounted. The
interconnect system of FIG. 10 is therefore structurally similar to
the interconnect system of FIG. 7 except that in the system of FIG.
10 a pair of vias 128 and 129 of appropriately sized capacitance
are added to trace 124. Via 128 is attached to trace 124 near the
point of attachment between package leg 116 and trace 124 while via
129 is attached to trace 124 near the point of attachment between
package leg 120 and trace 124.
A "via" is a conductive path that passes vertically through PCB 110
and is normally employed to interconnect a trace such as trace 124
with a trace on some other layer of PCB 126. While vias
conveniently distribute signals to various layers of a PCB,
conventional wisdom holds that vias should be avoided in high
frequency applications because their capacitance can degrade
frequency response. Notwithstanding conventional wisdom, vias 128
and 129 are added precisely because the additional capacitance they
provide at trace 124, when appropriately adjusted, improves system
frequency response. The additional PCB capacitance provided by via
128 and 129 could also be obtained by connecting discrete
capacitors or other capacitive elements to trace 124. However most
PCB manufacturers can easily add vias to a PCB and can easily
adjust their capacitance by adjusting their dimensions. Thus vias
128 and 129 are a convenient way to obtain the necessary additional
PCB capacitance needed to improve system frequency response and
have the added benefit of allowing more flexibility in signal
routing. As a side benefit, vias 128 and 129 could be used to route
signals from trace 124 to other PCB layers, but they need not be
used for that purpose.
FIG. 11 is an equivalent circuit diagram of the interconnect system
of FIG. 10. Driver 100 of FIG. 10 is represented in FIG. 11 as an
ideal source V.sub.in connected to pad 112A through the driver's
output resistance R1. Receiver 104 of FIG. 10 is represented in
FIG. 11 as an ideal receiver V.sub.out having input resistance R2
connected to pad 114B. Bond wires 118A, 118B, 122A and 122B and
package legs 116 and 120 of FIG. 10 are modeled in FIG. 11 as
inductances L1.sub.A, L1.sub.B, L2.sub.A, and L2.sub.B,
respectively. The capacitances of driver 100, ESD 108, receiver 104
and ESD 110 are represented in FIG. 11 as capacitors C1.sub.DRV,
C1.sub.ESD, C2.sub.RCV and C2.sub.ESD, respectively. The
capacitance of vias 128 and 129 is represented by capacitors
C1.sub.VIA and C2.sub.VIA, respectively. Trace 124 is represented
in FIG. 11 by its characteristic impedance Z0.
Table V below lists suitable component values for the interconnect
system of FIG. 11.
TABLE V L1.sub.A 1.4 nH L1.sub.B 1.4 nH L2.sub.A 1.4 nH L2.sub.B
1.4 nH C1.sub.DRV 0.7 pF C1.sub.ESD 1.3 pF C1.sub.VIA 0.7 pF
C2.sub.RCV 0.7 pF C2.sub.ESD 1.3 pF C2.sub.VIA 0.7 pF Z0 50 Ohms R1
50 Ohms R2 50 Ohms
FIG. 12 illustrates the frequency response of the interconnect
system of FIG. 8 using the Table V values of various
components.
Comparing these values to the values listed in Table IV we note
that all component values are similar to those used when
determining the frequency response (plot A, FIG. 9) of the
interconnect system of FIG. 7 except for the added via capacitance
C1.sub.VIA and C2.sub.VIA. Comparing plot A of FIG. 9 to FIG. 12 we
see that the added via capacitance increases the bandwidth of the
interconnect system from 4 GHz to approximately 6 GHz,
substantially larger than the 4 GHz bandwidth (plot A, FIG. 9) of
the interconnect system of FIG. 7. Note also that the passband in
FIG. 12 (0-6 GHz) is flatter (has less ripple) than the passband of
plots A or B of FIG. 9, and that the stopband drops off more
quickly. Thus despite the conventional wisdom that adding
capacitance to an interconnect system will degrade its frequency
response, a comparison of FIG. 9 and FIG. 12 shows us that
increasing the capacitance of the PCB trace as illustrated in FIG.
10 will actually allow an interconnect system to pass higher
frequency signals and with less distortion, provided that the
additional PCB capacitance is appropriately sized.
Butterworth and Chebyshev Filters
It should be understood that the "optimal" frequency response of an
interconnect system is application-dependent. For example in some
applications we may want to maximize bandwidth. In other
applications we may be willing, for example, to accept a narrower
bandwidth in exchange for a flatter passband, less attenuation at
lower frequencies, or steeper roll off in the stopband. Since the
frequency response of the interconnect system depends on the
impedance of its component values, the appropriate values to which
the bond wire inductances L1.sub.A, L1.sub.B, L2.sub.A and L2.sub.B
and any added PCB via capacitance C1.sub.VIA and C2.sub.VIA should
adjusted are application dependent.
We can view the equivalent circuit of the interconnect system
illustrated in FIGS. 5, 8 and 11, as a 4-pole or 5-pole filter. By
appropriately adjusting bond wire inductance and/or via
capacitance, the interconnect system can be made to behave like a
well-known, multi-pole "Butterworth" filter which provides a
maximally flat frequency response or like a well-known multi-pole
Chebyshev filter which can optimize a combination of bandwidth and
roll off characteristics. The design of multi-pole Butterworth and
Chebyshev filters, including appropriate choices for component
values so as to optimize various characteristics of a filter's
frequency response, is well-known to those skilled in the art. See
for example, pages 59-68 of the book Introduction to Radio
Frequency Design by W. H. Hayward, published 1982 by Prentice-Hall,
Inc., and incorporated herein by reference.
Multiple Drivers and Receivers
In many ICs more than one signal driver and/or receiver may access
a single IC input/output pin or package leg. In such case, in
accordance with the invention, the various drivers, receivers and
ESD devices are provided with separate bond pads interconnected by
bond wires or other conductors having appropriately sized
inductance.
FIG. 13 illustrates, for example, an IC 140 mounted on a PCB 141.
IC 140 includes a driver 142A, a receiver 142B and an ESD device
142C, all of which access a common package leg 143 connected to a
PCB trace 145 connected to a circuit node external to IC 140, such
as, for example, a terminal of another integrated circuit (not
shown). In accordance with the invention, each circuit device
142A-142C is linked to a separate one of a set of bond pads
144A-144C. A bond wire 146A connects driver bond pad 144A to ESD
bond pad 144B, while a bond wire 146C connects receiver bond pad
144C to ESD bond pad 144B. Bond wire 146B connects bond pad 144B to
package leg 143. When a via 149 is added to trace 145, the
capacitance of via 149 and the inductances of bond wires 146A-146C
may be adjusted to substantially optimize desired characteristics
of the interconnect system frequency response.
FIG. 14 illustrates an alternative version of the interconnect
system of FIG. 13 in which three conductive contacts (bond pads)
152A-152C within an IC 150, each linked to a separate one of
driver, ESD and receiver devices 151A-151C. Bond pads 152A-152C are
each also connected directly to an IC package leg 154 through a
corresponding one of a set of three conductors (bond wires)
153A-153C. Package leg 154 is connected to a trace 155 to form a
conductive path for conveying signals to or from a circuit node
external to IC 150. A via 156 (or other capacitive element) may
also be connected to trace 155, with the inductance of bond wires
152A-152C and the capacitance of via 156 sized to substantially
optimize desired frequency response characteristics of the
interconnect system.
Inductive Isolation By Metalization Layer Traces
FIG. 15 illustrates an alternative embodiment of the invention in
which bond pads 144A and 144C and bond wires 146A and 146B of FIG.
14 are replaced by a pair of lithographically-defined inductive
traces 164A and 166B formed on a metalization layer of IC 140.
Referring to FIG. 15, an ESD device 158B is directly connected to a
bond pad 159. A bond wire 160 connects bond pad 159 to a package
leg 162. A driver 158A implemented on IC 140 is linked to bond pad
159 through inductive trace 164A while a receiver 158C is linked to
bond pad 159 though another inductive trace 164C. The inductance of
metalization layer traces such as traces 164A and 164C can be
accurately adjusted by adjusting their lengths and shapes in a
well-known manner. Such metalization layer traces are often shaped
in the form of spirals and are known as "spiral inductors".
Unpackaged Die Instruments
FIGS. 4, 7, 10, 13, 14 and 15 illustrate the interconnect system in
accordance with the invention when used in connection with packaged
ICs. In some applications, unpackaged IC dies can be directly
connected through the bond wires to external traces. Thus, for
example, in FIG. 4, package leg 56 could be omitted and bond wires
58A and 58B could be directly connected to trace 64.
In FIG. 13, package leg 143 could be omitted and bond wire 146B
could be directly linked to trace 145.
In FIG. 14, leg 154 could be omitted and all bond wires 153A-153C
could be connected directly to trace 155.
Inductive Isolation by Lithographically-Defined Spring Contacts
FIGS. 16 and 17 illustrate an alternative embodiment of the
invention in which the function of bond wires and package legs of
FIG. 4 is carried out by a forked, lithographically-defined spring
contact 170. Spring contact 170 has two legs 172A and 172B, each
providing a separate signal path from an external circuit node such
as a trace 180 on a printed circuit board 168 through a tip 270 to
each device (e.g. driver, receiver or ESD device) implemented in an
IC 200. Contact force between tip 270 and trace 186 can be
maintained by the resilience of the spring contact when IC 200 is
held close to trace 180. Tip 270 may also be soldered to trace 180
when a permanent connection is desired.
In the example of FIGS. 16 and 17 spring contact 170 has two legs
172A and 172B to provide separate signal paths to two separate
circuits within IC 200. However in alternative embodiments of the
invention in which three or more devices must communicate with
trace 180, spring contact 170 may have three or more legs. The
capacitance isolating effect of the separate inductance of each leg
172A and 172B improves interconnect system frequency response in
the same way that the inductance L1A and L1B of bond wires 58A and
58B of FIG. 4 improves frequency response. Since the length and
width of legs 172A and 172B influences their inductance, their
inductance can be independently controlled by independently
adjusting their lengths and widths. In the example of FIG. 4, leg
172A is shorter and wider than leg 172B and therefore has a
different inductance.
One advantage (among others) of the using the forked spring contact
170 is that since legs 172A and 172B are accurately shaped by
lithographic processes, and since their shape and the angle between
them control their inductance and mutual inductance, such
inductance and mutual inductance can be controlled with a high
degree of resolution. Thus desired characteristics of the frequency
response of the interconnect system, such as passband width or
flatness, can be accurately controlled. Though not shown in FIG.
17, a via or other capacitive element may be included in circuit
board 182 in contact with trace 180 at or near its point of contact
with the tip of spring contact 170. With the capacitance of the via
or other capacitive element appropriately adjusted, we can further
improve such interconnect system frequency response
characteristics. The tip 270 of spring contact 170 is also suitable
for directly contacting vias or for contacting circuit nodes other
than PCB traces such as, for example, a bonding pad on another
integrated circuit or the tip of a spring contact of another
IC.
Spring contact 170 is constructed from layers of materials
alternately deposited on the surface of IC 200, with dimensions of
each layer being defined via conventional lithographic processes.
IC 200 includes a silicon substrate 202 and an insulating
passivation layer (e.g., polyimide) 204 disposed on the surface of
substrate 202. Passivation layer 204 includes an opening 206
immediately above a contact pad 208. A conductive layer 210 (e.g.,
titanium-tungsten) is deposited on the surface of passivation layer
204, the sidewalls of opening above contact pad 208 making
electrical contact with contact pad 208. A layer of masking
material (e.g., photoresist) 220 is then deposited onto layer 210
and patterned by conventional photolithographic techniques to
include an opening above contact pad 208 extending through masking
layer 220 to conductive layer 210. Layer 220 also includes a bump
230 forming a base for the spring contact's tip 270. A conductive
seed layer 250 (e.g., gold) is then deposited over masking layer
220 and lithographically etched to form the basic shape of contact
170 as viewed in FIG. 16. A resilient, conductive contact layer 260
(e.g., nickel) is then plated onto seed layer 250. The photoresist
masking layer 220 is then removed with a solvent (e.g., acetone),
and other remaining layers (e.g. part of layer 210) are removed
using suitable techniques. In the completed spring contact 170, tip
270 has freedom to flex vertically when pressed against trace 180.
PCT publication WO 98/52224A1 published Nov. 19, 1998 describes
spring contact fabrication in detail and is incorporated herein by
reference.
Laser Trimming
In high precision applications, the inductance of either leg 172A
or 172B can be adjusted after the IC has been fabricated and tested
by employing a laser beam to trim away a portion of the conductive
material forming the leg. The frequency response of the
interconnect system can be iteratively measured and adjusting using
such laser trimming to adjust the inductance of the spring contract
legs. Laser trimming techniques may also be employed to finely
adjust the inductances of traces 164A and 164C of FIG. 15 as well
as the capacitances of bonding pads and vias.
Thus has been shown and described alternative embodiments of an
interconnect system for providing access to a common I/O terminal
for multiple circuit devices such as drivers, receivers and
electrostatic protection devices implemented on an IC. Each such
device is provided with a separate contact pad within the IC and
the contact pads are linked to one another and to the IC I/O
terminal though inductive conductors such as bond wires or legs of
a lithographically-defined spring contact. The conductor inductance
isolates the capacitance of the circuit devices from one another,
thereby improving characteristics of the frequency response of the
interconnect system. In accordance with the invention, the
inductances of the conductors and various capacitances of the
interconnect system are also appropriately adjusted to optimize
interconnect system frequency response characteristics.
While the forgoing specification has described preferred
embodiment(s) of the present invention, one skilled in the art may
make many modifications to the preferred embodiment without
departing from the invention in its broader aspects. For example,
the interconnect system of the present invention interconnects
circuits formed by discrete components not implemented in ICs. The
appended claims therefore are intended to cover all such
modifications as fall within the true scope and spirit of the
invention.
* * * * *