U.S. patent number 3,881,177 [Application Number 05/450,543] was granted by the patent office on 1975-04-29 for frequency agile-baseband sidelobe canceller.
This patent grant is currently assigned to The United States of America as represented by the Secretary of the Army. Invention is credited to Joseph F. Len, Peter M. Rankin.
United States Patent |
3,881,177 |
Len , et al. |
April 29, 1975 |
Frequency agile-baseband sidelobe canceller
Abstract
Undesirable sidelobe signals are cancelled from the returns of a
main radar y the use of an omni antenna which will receive the
undesired signal. The signals from the main antenna and the omni
antenna are mixed together in a correlator which detects phase and
amplitude difference therebetween. The correlator feeds its output
to a modulator which amplitude modulates a signal from the omni
antenna and feeds it to a signal subtraction circuit which is in
series with the main antenna's output. The correlator and the
modulator are broken down into two parallel units which are
90.degree. out of phase with each other.
Inventors: |
Len; Joseph F. (Skaneateles,
NY), Rankin; Peter M. (Syracuse, NY) |
Assignee: |
The United States of America as
represented by the Secretary of the Army (Washington,
DC)
|
Family
ID: |
23788503 |
Appl.
No.: |
05/450,543 |
Filed: |
March 12, 1974 |
Current U.S.
Class: |
342/16; 455/273;
342/379 |
Current CPC
Class: |
H01Q
3/2629 (20130101); G01S 7/2813 (20130101) |
Current International
Class: |
H01Q
3/26 (20060101); G01S 7/28 (20060101); G01s
007/36 () |
Field of
Search: |
;343/18E,1CL,1LE
;325/367,369,371 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Tubbesing; T. H.
Attorney, Agent or Firm: Neureither; Lawrence A. Beumer;
Joseph H. Sims; Robert C.
Claims
We claim:
1. A system comprising a main signal path containing therein a
desired and an undesired signal; a second signal path containing
therein primarily the undesired signal; cancellation means
connected in the main signal path for substantially cancelling the
undesired signal therein; correlator means connected to said main
signal path and said second signal path so as to measure the
amplitude and phase difference of the undesired signal in each of
these paths; modulator means having inputs connected to outputs of
said correlator means and said second signal path; an output of
said modulator means being connected to said cancellation means so
as to subtract the output signal of the modulator from the signals
contained in said main signal path; said modulator means amplitude
modulating the undesired signal in said second path such that the
signal and its output is of the proper phase and amplitude to
cancel in the cancellation means the undesired signal in said main
signal path; said main signal path is connected to an output
terminal; said cancellation means is connected between the main
signal path and said output terminal; said correlator means and
said modulator means each contain two parallel paths; one path
containing a 90.degree. phase shifting meas therein; said
correlator means contains first and second mixer means each having
first and second inputs and an output; said first and second mixer
means being connected in different ones of the two parallel paths
of the correlator means; one input of the first mixer means is
connected to the main signal path and the other input of the first
mixer means is connected to said second signal path; one input of
the second mixer means is connected through the 90.degree. phase
shifter to the main signal path, and the other input is connected
to said second signal path; said modulator means containing first
and second amplitude modulators in separate ones of the two
parallel paths of the modulator means; said first and second
modulators each having two inputs and an output; the output of the
first mixer means being connected to one input of the first
modulator; the other input of the first modulator being connected
to said second signal path; the output of the second mixer means
being connected to one input of said second modulator; the other
input of the second modulator being connected to said second signal
path; the output of said second modulator being connected through
the 90.degree. phase shifter to the input of said cancellation
means; and the output of said first modulator being connected to
the input of said cancellation means.
2. A system as set forth in claim 1 further comprising third and
fourth mixer means each having first and second inputs and an
output; a local oscillator having an output connected to one input
of each of said third and fourth mixer means; the other input of
said third mixer means being connected to said main signal path;
the other input of said fourth mixer means being connected to said
second signal path; first and second bandpass filters; the output
of said third mixer means being connected through said first
bandpass filter to the input of said first mixer means; and the
output of said fourth mixer means being connected through said
second bandpass filter to an input of said second mixer means.
3. A system as set forth in claim 2 further comprising a plurality
of additional second signal paths each containing undesired signals
which are to be found in said main signal path; and a plurality of
additional correlators and modulators associated with the
additional second signal paths and connected in the manner of said
original second signal path.
4. A system as set forth in claim 3 wherein said main signal path
is supplied by a directional radar antenna; and said plurality of
second signal paths each being fed by one of a plurality of omni
antenna.
Description
BACKGROUND OF THE INVENTION
This invention is related to the field of radar processing. More
particularly the invention is related to the provision for
countering anti-radar devices. U.S. Pat. No. 3,202,990 to P. W.
Howells, patented in Aug. 24, 1965, shows an example of the prior
art in this field. The patent to Howells suffers in many respects
due to its transposing to an intermediate frequency before
cancellation, and a need exist for a device which overcomes the
limitations inherent in the Howells patent.
SUMMARY OF THE INVENTION
The phase and amplitude modulation of the omni directional antenna
signal is performed by the use of two amplitude modulators which
operate in parallel circuits which have a 90.degree. phase shift
between them at the carrier frequency. The difference signal
between the main antenna and that subtracted from it by a
subtraction circuit connected in the main radar antenna's receiving
network is transposed into an intermediate frequency by the use of
mixers, local oscillators, and bandpass filters. The same is done
for the omni antenna received signals. The intermediate frequency
of these two transposed signals are the same, and the bandpass
filters in each channel are the same. These signals are then mixed
together in two parallel baseband balanced mixers. One of the two
parallel mixer circuits has a 90.degree. phase shift at the
intermediate frequency. The outputs of the mixers are low pass
filtered and applied as the control signals for the two amplitude
modulators in the two parallel circuits. The signal received in the
omni directional antenna is distributed to these modulators. One of
the parallel circuits contains a 90.degree. phase shifter. The two
parallel circuits are linearly summed to produce one output for the
overall modulator. This output is fed to the subtraction circuit so
as to provide a cancellation of undesired sidelobes.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a block diagram showing a preferred embodiment of the
invention; and
FIG. 2 is a block diagram of another embodiment of the
invention.
DESCRIPTION OF THE PREFERRED EMBODIMENTS
Sidelobe cancellation is a process by which interfering signals
(such as produced by jammers) received through the sidelobe of an
antenna are eliminated. The present invention uses omni directional
antennas located near the principal antenna which also receives the
undesired interfering signal. Optimum amplitude and phase
modulations are applied to this signal which is then subtracted
from the principal antenna signals. By having the proper phase and
amplitude modulation applied, cancellation of the undesirable
signals is achieved. The modulation values are derived by
correlating the principal antenna output after subtraction of the
modulated omni antenna signals with the direct omni antenna
signals. These values are applied in a feedback loop such that the
cancellation process is continuous and automatic.
The amplitude modulation of the omni directional antenna signals
and the subtraction of the modulated omni directional antenna
signal from the main antenna is performed at the radio carrier
frequency of the received signals. No transposing to an
intermediate frequency by the use of mixers, local oscillators, and
bandpass filters of the received signal before the cancellation
mode is required or used. The phase and amplitude modulation of the
omni directional antenna signal antenna is performed by the use of
two amplitude modulators which operate in two parallel circuits
which have a 90.degree. phase shift between them at the carrier
frequency. These two channels are referred to as the in-phase (I)
and quadrature-phase (Q) channels.
Referring to the diagram of FIG. 1, the signals received in an omni
directional antenna 11 are distributed to the modulator 13 and the
mixer 18. The signal applied to the modulator is distributed to two
parallel circuits each of which contain an amplitude modulator 15
or 16. One circuit contains a 90.degree. phase shifter 14. The two
parallel circuits are linearly summed to produce one output for the
modulator. A summing circuit could be connected to the outputs of
modulator 16 and phase shifter 14.
The output of modulator 13 is subtracted from the directional radar
antenna 10 signals at the subtraction node 12. This is the
cancellation node. The difference between the radar antenna signals
and the modulated omni directional antenna signals is distributed
to mixer 17 and to the sidelobe canceller output port 26. The
output of local oscillator 27 is applied to mixers 17 and 18. The
output signals of the mixers are filtered by the bandpass filters
19 and 20. These filters are identical in center frequency,
bandwidth, and bandpass characteristics.
The outputs of the filters 19 and 20 are mixed together in the
baseband mixers 22 and 23. The center frequency of the signals
passed through filters 19 and 20 is the same; therefore the
difference frequency components are base banded. The mixers are
balanced such that one input signal from one filter cannot by
itself produce a base banded output.
The mixer 23 is in a circuit which contains a 90.degree. phase
shift; therefore the unmodulated omni directional antenna signal
(transposed to an intermediate frequency) is mixed with the main
antenna/modulated omni directional antenna difference signal
(transposed to the same intermediate frequency after it has been
phase shifted 90.degree.). The base banded difference signals
desired from mixers 22 and 23 are low pass filtered by low pass
filters 25 and 24 and applied as control signals for the amplitude
modulators 16 and 15 respectively. Although not shown, linear
amplifiers are employed at various points in the circuit with gains
and dynamic ranges as are required by the specific application.
Since no frequency transposing or bandpass filtering is performed
upon signals before the cancellation mode, channel match errors
associated with mixing and band pass filtering are nonexistent in
this circuit. The bandwidth over which signals are to be cancelled
is not limited by frequency transposing or bandpass filtering
processes. The bandwidth over which cancellation of signals will
occur is only limited by the practical bandwidth of the modulator
13, circuitry of the cancellation node 12 and any linear amplifier
which may be used in the circuits between the antennas and the
cancellation node 12.
Desirable signals which are received in radar antenna 10 to be made
available at output terminal 26 are not required to pass through
any mixers, bandpass filters, or other processes which would alter
their characteristics in addition to that which is to be produced
by the sidelobe canceller process itself. The output signals are
available at the same carrier frequency and have not been required
to pass through any bandpass filter. The center frequency and
bandwidth for which the cancellation process is optimized is
determined by signals which are applied to correlator 28. With the
use of mixers 17 and 18, bandpass filters 19 and 20, and local
oscillator 27, the center frequency and bandwidth of the antenna
signals which are applied to the correlator 28 are selected.
With the use of base band feedback control signals, derived from
the in-phase 22 and quadrature phase 23 mixers, flexibility of
design is possible for the low pass filters 24 and 25. Multiple
pole and zero filter designs are practical and sample and hold
processes for the feedback control signals are possible.
The function of the circuit in FIG. 1 is to subtract from the main
antenna output those signals that have been received by omni
antenna 11 after they have been complex modulated; that is, after
the phase and the amplitude of the omni antenna signals have been
modulated. Modulator 13, therefore, is a complex modulator that
achieves an equivalent phase and amplitude modulation by means of
two amplitude modulators, which operate on the signal and on a
90.degree. phase shifted sample of the signal. The remaining
circuitry in FIG. 1 generates the decreased control signal from
complex modulator 13. Correlator 28 is a complex correlator
measuring the effective magnitude and phase angle of the correlator
between the signals out of bandpass filters 19 and 20. Bandpass
filters 19 and 20 determine the bandwidth of the signals to be
correlated.
Mixers 17 and 18 together with local oscillator 27 allow the
bandpass filtering function and the correlation process to take
place at a carrier frequency independent of the carrier frequency
at which the modulation and subtraction processes take place.
A feedback loop exists because the process of changing the
modulator control signal changes the nature of the signal
subtraction at 12, which changes the correlation of signals 19 and
20, and thus the control signal out of correlator 28. In the given
configuration, the loop feedback drives the modulator so that the
signal in output channel 26 is not correlated with the signal of
bandpass filter 20, which was obtained from omni antenna 11. Thus
the processor in FIG. 1 coherently subtracts signals out of the
radar antenna output, which are correlated with signals received in
omni antenna 11 automatically by means of a rapidly conveying
feedback loop. The loop power gain is proportional to the power
received by the omni antenna; therefore the loop will cancel
jamming signals which have a high average power, while it is
relatively insensitive to target returns which have low average
power. In this way the system is able to discriminate between the
two.
FIG. 2 is a block diagram of a multiple loop cancellation processor
capable of processing and, therefore, cancelling a number of
independent signals received in the radar antenna. The process is,
in effect, a multiple processor of the type defined by FIG. 1, but
which has a multiple dimensional capacity capable of processing as
many different signals as there are cancellation loops. In general,
signals are defined to be different when they are received from
widely separate angles of arrival.
The following example describes the operation of the multiple loop
processor. Assume a queisent state in which no signals are received
in any of the antennas 30-32, the correlators 33 and 34 outputs are
zero, and therefore, the modulators 35 and 36 are off. Allow an
environment consisting of a number of signals arriving from widely
separate angles to suddenly appear at the antenna outputs. Each
correlator will start to generate an output that is representative
of the correlation of the multiple signals received in its antenna
(by way of mixers 39 and 40 and filters 41 and 42) and the multiple
signals received in the radar antenna. Initially the modulators are
off so that the unprocessed radar antenna signal will appear by way
of mixer 37 and filter 38 at one input of each of the correlators.
The initial value of the correlation output applied to the
modulator will result in a relatively small reduction of the radar
antenna waveform. The initial reduction is small because the
initial value of the control voltages for each modulator were
derived independently of the effect of the other modulators on
reducing the waveform. The process is convergent however, and a
relatively large reduction is achieved if the number of independent
loops is equal to or greater than the number of independently
received signals. In the converging process, the output of the
subtraction node is continuously being correlated in each loop with
the signals received in the loop's omni antenna. As long as some
part of the subtraction node 43 output is correlated with a loop's
omni antenna inputs, the loop's modulator is adjusted to subtract
the signals, resulting in a further reduction or cancellation of
the radar antenna signals.
As can be seen from FIG. 2 each omni antenna is connected in a
separate cancellation loop. Each loop consists of the omni antenna,
mixer, bandpass filter, correlator, and a modulator. If further
omni antennas are to be used in the system shown in FIG. 2, further
cancellation loops will be provided with the output of the
modulator in each cancellation loop connected as indicated by
"ECT," and the input to the further correlators would be fed from
the bandpass filter 38 by way of connections indicated as ECT. In
this way a plurality of additional cancellation loops connected in
the same manner as that for the omni antenna 1 can be added to the
system shown in FIG. 2 so as to provide cancellation of other
undesired signals which may be received by radar antenna 30.
* * * * *