U.S. patent number 3,806,663 [Application Number 05/232,470] was granted by the patent office on 1974-04-23 for radio telephone subscriber unit.
This patent grant is currently assigned to Integrated Systems Technology, Inc.. Invention is credited to Hernando Javier Garcia, Benjamin Roger Peek.
United States Patent |
3,806,663 |
Peek , et al. |
April 23, 1974 |
RADIO TELEPHONE SUBSCRIBER UNIT
Abstract
Disclosed is a radio telephone subscriber unit for communicating
with a telephone company base terminal wherein control signals are
transmitted between the base terminal and the subscriber unit for
establishing a radio link-up therebetween. The subscriber unit can
be operated in either an automatic or a manual mode. In the
automatic mode, the control signals are transmitted by turning on
and turning off discrete audio-frequency tones which are modulated
onto radio-frequency carrier signals which are generated and
transmitted by radio-frequency transmitters in the subscriber unit
and at the base terminal. When the telephone call is originated by
the base terminal, the audio-frequency control tones or signalling
tones received and detected by the subscriber unit are converted
into digital signals which are supplied to digital control logic
within the subscriber unit. The control logic determines whether
the coding of the tone-derived digital signals represent the phone
number of the subscriber unit and, when the determination is
affirmative, causes the subscriber unit to transmit certain
acknowledgement and connect signals back to the base terminal for
completing the radio link-up. When the telephone call is originated
by the subscriber unit, the same control logic causes the
subscriber unit to transmit coded tone burst signals to the base
terminal for establishing a radio link-up therewith and for
supplying thereto an indication of the phone number of the
telephone being called. The subscriber unit includes an automatic
channel search mechanism for enabling the subscriber unit to
automatically tune in to an idle one of several base terminal
carrier channels. The subscriber unit is particularly adapted for
use as a self-contained portable battery operated unit and the
subscriber unit includes means for automatically switching a
significant portion of the control logic to a power conserving
standby condition during the voice conversation portion of a
telephone call as well as when a telephone call is not in progress.
This minimizes the power drain on the power supply battery. In the
manual mode, the control logic functions in a somewhat simpler
manner, such control logic then being used only on base terminal
originated calls to decode coded tone burst signals and to activate
a ringing circuit in the subscriber unit when the proper phone
number is received. In both modes, various provisions are made for
minimizing the power drain on the power supply battery.
Inventors: |
Peek; Benjamin Roger (Garland,
TX), Garcia; Hernando Javier (San Francisco, CA) |
Assignee: |
Integrated Systems Technology,
Inc. (Garland, TX)
|
Family
ID: |
22873245 |
Appl.
No.: |
05/232,470 |
Filed: |
March 7, 1972 |
Current U.S.
Class: |
455/572;
455/550.1 |
Current CPC
Class: |
H04W
52/028 (20130101); Y02D 70/00 (20180101); Y02D
30/70 (20200801); H04W 88/02 (20130101) |
Current International
Class: |
H04Q
7/32 (20060101); H04q 007/04 () |
Field of
Search: |
;179/41A ;325/55,492,64
;343/177 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Cooper; William C.
Assistant Examiner: Kundert; Thomas L.
Attorney, Agent or Firm: Kanz; Jack A.
Claims
What is claimed is:
1. A radio telephone subscriber unit for transmitting radio signals
to and receiving radio signals from a radio telephone base
terminal, said subscriber unit including
control logic circuit means for generating control signals for
controlling the operation of the subscriber unit, said control
logic circuit means including circuitry for processing signals
received from said base terminal,
battery operated power supply means for providing operating power
for the subscriber unit, and
power supply control means coupled between the battery operated
power supply means and said processing circuitry of the control
logic circuit means and responsive to a first signal generated by
the control logic circuit means for allowing the flow of operating
power to said processing circuitry to thereby enable said circuitry
to process subsequently received signals and responsive to a second
signal generated by the control logic circuit means for disabling
the flow of operating power to said processing circuitry.
2. A radio telephone subscriber unit for transmitting radio signals
to and receiving radio signals from a radio telephone base
terminal, said subscriber unit including
control logic circuit means including circuitry for generating a
first signal when establishment of a radio link-up between the
subscriber unit and the radio telephone base terminal is initiated
and circuitry for generating a second signal when such radio
link-up is established and following transmission by the subscriber
unit of a certain signal to the base terminal,
battery operated power supply means for providing operating power
for the subscriber unit, and
power supply control means coupled between the battery operated
power supply means and predetermined circuitry of the control logic
circuit means and responsive to said first signal for enabling the
flow of operating power to the predetermined circuitry and
responsive to said second signal for disabling the flow of
operating power to the predetermined circuitry.
3. A radio telephone subscriber unit for transmitting radio signals
to and receiving radio signals from a radio telephone base
terminal, said subscriber unit including
control logic circuit means including circuitry for generating a
first signal when disconnection of a radio link-up between the
subscriber unit and the radio telephone base terminal is initiated
and circuitry for generating a second signal upon completion of
disconnection of the radio link-up,
battery operated power supply means for providing operating power
for the subscriber unit, and
power supply control means coupled between the battery operated
power supply means and predetermined circuitry of the control logic
circuit means and responsive to said first signal for enabling the
flow of operating power to the predetermined circuitry and
responsive to said second signal for disabling the flow of
operating power to the predetermined circuitry.
4. A radio telephone subscriber unit for transmitting radio signals
to and receiving radio signals from a radio telephone base
terminal, said subscriber unit including
control logic circuit means for generating control signals for
controlling the operation of the subscriber unit,
battery operated power supply means for providing operating power
for the subscriber unit, and
power supply control means coupled between the battery operated
power supply means and predetermined circuitry of the control logic
circuit means and responsive to a first signal generated by the
control logic circuit means for enabling the flow of operating
power to the predetermined circuitry and responsive to a second
signal generated by the control logic circuit means for disabling
the flow of operating power to the predetermined circuitry.
said power supply control means including
a power input terminal connected to said battery operated power
supply means,
a power output terminal connected to said predetermined
circuitry,
bistable means responsive to said first signal for generating an
enabling signal and responsive to said second signal for generating
a disabling signal, and
means interconnecting said input terminal and said output terminal
and responsive to said enabling signal for allowing the transfer of
operating power from said input terminal to said output terminal
and responsive to said disabling signal for preventing the transfer
of operating power from said input terminal to said output
terminal.
5. A radio telephone subscriber unit as in claim 4 wherein said
interconnecting means includes a first transistor whose emitter and
collector are connected in series between said power input terminal
and said power output terminal, and a second transistor coupled to
said bistable means and to said first transistor, said second
transistor operative to conduct current in response to said
enabling signal and to inhibit the conduction of current in
response to said disabling signal, and said first transistor
operative to allow the transfer of operating power therethrough
when said second transistor is conducting and to prevent the
transfer of operating power therethrough when said second
transistor is not conducting.
6. A radio telephone subscriber unit for transmitting radio signals
to and receiving radio signals from a radio telephone base
terminal, said subscriber unit including
control logic circuit means for generating control signals for
controlling the operation of the subscriber unit,
battery operated power supply means for providing operating power
for the subscriber unit, and
power supply control means coupled between battery operated power
supply means and predetermined circuitry of the control logic
circuit means and responsive to a first signal generated by the
control logic circuit means for enabling the flow of operating
power to the predetermined circuitry and responsive to a second
signal generated by the control logic circuit means for disabling
the flow of operating power to the predetermined circuitry, said
power supply control means further including circuitry for
generating an inhibit signal in response to said second signal,
and
said control logic circuit means including circuitry responsive to
said inhibit signal for preventing the transmission of radio
signals to the base terminal.
7. A radio telephone subscriber unit for use in a two-way radio
telephone system in which a radio telephone base terminal transmits
an idle tone signal to identify an available radio channel and a
seize tone signal to initiate a telephone call between the base
terminal and a selected subscriber unit, said radio telephone
subscriber comprising
control logic circuit means for generating control signals to
control the operation of said subscriber unit and including
circuitry for generating a first signal in response to the
transmission of a seize tone signal by the base terminal,
battery operated power supply means for supplying operating power
for said subscriber unit, and
power supply control means coupled between said battery operated
power supply means and predetermined portions of said control logic
circuit means and responsive to said first signal for allowing the
flow of operating power to said predetermined portions and
responsive to certain other control signals from said control logic
circuit means for preventing the flow of operating power to said
predetermined portions.
8. A radio telephone subscriber unit for use in a two-way telephone
system in which a radio telephone base terminal transmits an idle
tone signal to identify an available radio channel, a seize tone
signal to initiate a telephone call between the base terminal and a
selected subscriber unit, and a called number signal sequence to
identify the selected subscriber unit, said radio telephone
subscriber unit comprising
control logic circuit means for generating control signals to
control the operation of said subscriber unit and including
circuitry for generating a second signal if any but a particular
called number signal sequence is transmitted by said base
terminal,
battery operated power supply means for supplying operating power
for said subscriber unit, and
power supply control means coupled between said battery operated
power supply means and predetermined portions of said control logic
circuit means and responsive to certain of said control signals for
allowing the flow of operating power to said predetermined portions
and responsive to said second signal for preventing the flow of
operating power to said predetermined portions.
9. A radio telephone subscriber unit for use in a two-way telephone
system in which a radio telephone base terminal transmits an idle
tone signal to identify an available radio channel, a seize tone
signal to initiate a telephone call between the base terminal and a
selected subscriber unit, and a called number signal sequence to
identify the selected subscriber unit, said radio telephone
subscriber unit comprising
control logic circuit means for generating control signals to
control the operation of said subscriber unit and including
circuitry for generating a second signal if more than a certain
predetermined period of time elapses between transmission of
various portions of the called number signal sequence by the base
terminal,
battery operated power supply means for supplying operating power
for said subscriber unit, and
power supply control means coupled between said battery operated
power supply means and predetermined portions of said control logic
circuit means and responsive to certain of said control signals for
allowing the flow of operating power to said predetermined portions
and responsive to said second signal for preventing the flow of
operating power to said predetermined portion.
10. A radio telephone subscriber unit for use in a two-way radio
telephone system in which a radio telephone base terminal transmits
a called number signal sequence to identify a selected subscriber
unit, and a ringing signal sequence to notify the selected
subscriber unit that that unit is being called, said radio
telephone subscriber unit comprising
a hook switch having on-hook and off-hook conditions,
control logic circuit means for generating control signals to
control the operation of said subscriber unit and including
circuitry for generating first and second enabling signals if a
particular called number signal sequence is transmitted by said
base terminal and circuitry responsive to said first enabling
signal for generating a third signal a predetermined period of time
after termination of transmission of a ringing signal sequence if
said hook switch is in the on-hook condition,
battery operated power supply means for supplying operating power
for said subscriber unit, and
power supply control means coupled between said battery operated
power supply means and predetermined portions of said control logic
circuit means and responsive to certain of said control signals for
allowing the flow of operating power to said predetermined portions
and responsive to said third signal for preventing the flow of
operating power to said predetermined portions.
11. A radio telephone subscriber unit as in claim 10 wherein said
control logic circuit means further includes circuitry responsive
to said second enabling signal for generating a fourth signal if
said hook switch is placed in the off-hook condition and wherein
said power supply control means further includes circuitry
responsive to said fourth signal for preventing the flow of
operating power to said predetermined portions.
12. A radio telephone subscriber unit as in claim 11 wherein said
control logic circuit means further includes circuitry responsive
to said fourth signal for generating a third enabling signal and
circuitry responsive to said third enabling signal for generating
said first signal upon said hook switch being placed in the on-hook
condition.
13. A radio telephone subscriber unit as in claim 12 wherein said
control logic circuit means further includes circuitry responsive
to the generation of said first signal in response to said third
enabling signal for generating a disconnect signal sequence of
predetermined duration and circuitry for generating a fifth signal
upon termination of generation of said disconnect signal sequence
and wherein said power supply control means further includes
circuitry responsive to said fifth signal for preventing the flow
of operating power to said predetermined portions.
14. A radio telephone subscriber unit for use in a two-way radio
telephone system in which a radio telephone base terminal transmits
an idle tone signal to identify an available radio channel, a seize
tone signal to initiate a telephone call between the base terminal
and a selected subscriber unit, a called number signal sequence to
identify the selected subscriber unit, and a ringing signal
sequence to notify the selected subscriber unit that that unit is
being called, said radio telephone subscriber unit comprising
a hook switch having on-hook and off-hook conditions,
control logic circuit means for generating a first signal in
response to the hook switch being placed in the off-hook
condition,
battery operated power supply means for supplying operating power
for said subscriber unit, and
power supply control means coupled between said battery operated
power supply means and predetermined portions of said control logic
circuit means and responsive to said first signal for allowing the
flow of operating power to said predetermined portions.
15. A radio telephone subscriber unit as in claim 14 wherein said
control logic circuit means further includes circuitry for
generating a second signal if, after a first predetermined period
of time, the idle tone signal is not being transmitted by the base
terminal or if, after a second predetermined period of time, the
idle tone signal is being transmitted by the base terminal, and
wherein said power supply control means further includes circuitry
responsive to said second signal for preventing the flow of
operating power to said predetermined portions.
16. A radio telephone subscriber unit as in claim 15 wherein said
control logic circuit means further includes circuitry for
generating the second signal if, within a third predetermined
period of time, the seize tone signal is not being transmitted by
the base terminal.
17. A radio telephone subscriber unit as in claim 14 wherein said
subscriber unit further includes means for producing dialed signal
sequences for transmission to the base terminal, each such dialed
signal sequence representing a digit of a called telephone number,
wherein said control logic circuit means further includes circuitry
for producing an identification signal sequence for transmission to
the base terminal, said identification signal sequence for
identifying said subscriber unit, circuitry for generating and
enabling signal after production of the identification signal
sequence, and circuitry responsive to said enabling signal when the
hook switch is in the off-hook condition for generating a third
signal if no dialed signal sequence is produced within a
predetermined period of time after generation of said enabling
signal or if no dialed signal sequence is produced within a
predetermined period of time after the production of each dialed
signal sequence, and wherein said power supply control means
includes circuitry responsive to said third signal for preventing
the flow of operating power to said predetermined portions.
18. A radio telephone subscriber unit as in claim 17 wherein said
control logic circuit means further includes circuitry responsive
to said enabling signal for generating said first signal when said
hook switch is placed in the on-hook condition.
19. A radio telephone subscriber unit as in claim 18 wherein said
control logic circuit means further includes circuitry responsive
to the generation of said first signal when said hook switch is
placed in the on-hook condition for generating a disconnect signal
sequence of predetermined duration and circuitry for generating a
fourth signal upon termination of generation of said disconnect
signal sequence and wherein said power supply control means further
includes circuitry responsive to said fourth signal for preventing
the flow of operating power to said predetermined portions.
20. In a radio telephone system including a radio telephone base
terminal for transmitting called number signal sequences and
ringing signal sequences and at least one radio telephone
subscriber unit, said subscriber unit including control logic means
for producing control signals for controlling the operation of the
subscriber unit, battery operated power supply means for supplying
operating power to the subscriber unit, power supply control means
interconnecting the battery operated power supply means with
certain circuitry of the control logic means, microphone and
earphone circuitry, and a hook switch for enabling transmission of
voice signals to and reception of voice signals from the base
terminal by means of the microphone and earphone circuitry
respectively when the hook switch is in a first position and for
disabling transmission of voice signals to and reception of voice
signals from the base terminal when the hook switch is in a second
position, a method of controlling the flow of operating power to
said certain circuitry comprising the steps of
a. enabling the flow of operating power to said certain circuitry
when the base terminal transmits a seize tone signal,
b. disabling the flow of operating power to said certain circuitry
when any but a particular called number signal sequence is
transmitted by the base terminal,
c. disabling the flow of operating power to said certain circuitry
upon termination of transmission of a ringing signal sequence by
the base terminal if, upon such termination, the hook switch is in
the second position,
d. disabling the flow of operating power to said certain circuitry
a predetermined period of time after the hook switch is placed in
the first position following transmission of a ringing signal
sequence,
e. enabling the flow of operating power to said certain circuitry
upon replacing the hook switch in the second position, and
f. disabling the flow of operating power to said certain circuitry
a predetermined period of time after the replacement of the hook
switch in the second positionn.
21. In a radio telephone system including a radio telephone base
terminal for transmitting called number signal sequences and
ringing signal sequences and at least one radio telephone
subscriber unit, said subscriber unit including control logic means
for producing control signals for controlling the operation of the
subscriber unit, battery operated power supply means for supplying
operating power to the subscriber unit, power supply control means
interconnecting the battery operated power supply means with
certain circuitry of the control logic means, means for producing
dialed signal sequences for transmission to the base terminal,
means for producing an identification signal sequence, microphone
and earphone circuitry, and a hook switch for enabling transmission
of voice signals to and reception of voice signals from the base
terminal by means of the microphone and earphone circuitry
respectively when the hook switch is in a first position and for
disabling transmission of voice signals to and reception of voice
signals from the base terminal when the hook switch is in a second
position, a method of controlling the flow of operating power to
said certain circuitry comprising the steps of
a. enabling the flow of operating power to said certain circuitry
when the hook switch is placed in the first position,
b. disabling the flow of operating power to said certain circuitry
if, after a first predetermined period of time, an idle tone signal
is not being transmitted by the base terminal or if, after a second
predetermined period of time, an idle tone signal is being
transmitted by the base terminal,
c. disabling the flow of operating power to said certain circuitry
if, within a third predetermined period of time, a seize tone
signal is not being transmitted by the base terminal,
d. disabling the flow of operating power to said certain circuitry
when no dialed signal sequence is produced within a predetermined
period of time following production of the identification signal
sequence or when no dialed signal sequence is produced within a
predetermined period of time following production of a previous
dialed signal sequence,
e. enabling the flow of operating power to said certain circuitry
upon replacing the hook switch in the second position, and
f. disabling the flow of operating power to said certain circuitry
a predetermined period of time after the replacement of the hook
switch in the second position.
22. A radio telephone subscriber unit for use in a radio telephone
system in which a radio telephone base terminal identifies a
selected subscriber unit by transmitting a called number signal
sequence representing that subscriber unit's identification number
and then notifies the selected subscriber unit by transmitting an
audio ringing signal sequence, said subscriber unit comprising
a receiver for receiving signals transmitted by the base
terminal,
a speaker for generating audible signals,
an amplifier responsive to audio signals applied thereto for
actuating said speaker in accordance with the audio signals
control logic means responsive to the receipt by the subscriber
unit of a particular called number signal sequence for generating a
control signal, and
means coupled between said receiver and said amplifier and
responsive to said control signal for applying to said amplifier
ringing signal sequences received by said receiver.
23. A radio telephone subscriber unit as in claim 22 wherein said
control logic means further includes circuitry responsive to the
receipt by the subscriber unit of said particular called number
signal sequence for causing said amplifier to increase its gain by
a predetermined amount.
24. A radio telephone subscriber unit for use in a radio telephone
system in which a radio communication channel may be established
and maintained between the subscriber unit and a radio telephone
base terminal so long as a radio signal is transmitted between the
base terminal and subscriber unit within a predetermined interval
of time following establishment of the channel or following any
transmission of a radio signal, said subscriber unit comprising
a transmitter for transmitting radio signals over the radio
communication channel, and
control logic means for monitoring said transmitter to determine
when radio signals are being transmitted and for actuating said
transmitter to transmit a radio signal burst if no signals were
transmitted by the transmitter in a preceding predetermined time
interval.
25. The radio telephone subscriber unit as in claim 24 further
including means for generating modulating signals, and wherein said
transmitter includes
means for generating radio signals,
means for applying the radio signals to the radio communication
channel,
gating means coupled between said radio signal generating means and
said applying means and responsive to the presence of an enabling
signal for allowing passage of signals from said radio signal
generating means to said applying means, and
activating means responsive to the presence of an activating signal
from said control logic means and to the presence of said
modulating signals for producing an enabling signal of duration
substantially equal to the duration of the activating signal or
modulating signal present.
26. The radio telephone subscriber unit as in claim 25 wherein said
control logic means includes
means coupled to said activating means for generating a first
signal whenever said enabling signal is being produced and for
generating a second signal whenever said enabling signal is not
being produced, and
timing means responsive to the generation of said second signal for
producing an activating signal of certain duration after a
predetermined time interval unless said first signal is generated
within that time interval.
27. The radio telephone subscriber unit as in claim 26 wherein said
timing means includes
a capacitor,
means responsive to said second signal for enabling said capacitor
to charge and responsive to said first signal for discharging said
capacitor, and
trigger circuit means for producing said activating signal and
discharging said capacitor when the voltage across said capacitor
reaches a predetermined level.
28. A radio telephone subscriber unit as in claim 24 wherein said
control logic means includes means for producing a first signal
when a particular signal sequence is transmitted by the base
terminal, means for producing a second signal following transmittal
of said particular signal sequence by the subscriber unit, and
means responsive to said first and second signals for activating
said transmitter to transmit said signal burst if no signals are
transmitted by the transmitter within a particular time
interval.
29. A radio telephone subscriber unit as in claim 28 wherein said
transmitter includes
means for generating radio signals,
means for applying the radio signals to a radio communication
channel,
activating means including an output line and responsive to an
activating signal from said control logic means for applying a
gating signal of predetermined duration to said output line,
gating means coupled between radio signal generating means and said
applying means and responsive to the presence of said gating signal
on said output line for enabling signals from said radio signal
generating means to be applied to said applying means, and
wherein said control logic means includes means for generating
control signals for establishing a radio communication channel
between the subscriber unit and the base terminal and means
responsive to various ones of said control signals for applying
gating signals to said output line.
30. A radio telephone subscriber unit for use in a radio telephone
system which includes a radio telephone base terminal which
transmits a plurality of radio signals for establishing a radio
link-up with the subscriber unit, said subscriber unit including
means for receiving the radio signals transmitted by the base
terminal and for generating digital signals representing such radio
signals, said digital signals including combinations of idle tone
signal bursts and seize tone signal bursts, each combination
representing a digit of a subscriber unit identification number,
and a control logic unit for producing a plurality of control
signals to control the operation of the subscriber unit, said
control logic unit including
timing means for producing a plurality of timing signals at
predetermined timing intervals following activation of the timing
means, and
timing control means responsive to certain ones of said digital
signals and said control signals for resetting and activating said
timing means at certain times during the course of establishing the
radio link-up, responsive to certain other of said digital signals
in said control signals for resetting and deactivating said timing
means at certain other times during the course of establishing the
radio link-up, and responsive to each idle tone signal burst and
each seize tone signal burst of a combination for resetting and
activating said timing means.
31. A radio telephone subscriber unit as in claim 30 wherein said
control logic unit further includes means for producing a first
signal when a particular combination of idle and seize tone signal
bursts is generated, and wherein said timing control means further
includes circuitry responsive to said first signal for resetting
and deactivating said timing means.
32. A radio telephone subscriber unit as in claim 30 wherein said
control logic unit further includes means for producing a second
signal after a particular combination of idle and seize tone signal
bursts has been generated, and wherein said timing control means
further includes circuitry responsive to said second signal for
resetting and activating said timing means.
33. A radio telephone subscriber unit as in claim 30 further
including a hook switch having on-hook and off-hook conditions, and
wherein said control logic unit further includes means for
producing a third signal when said hook switch is placed in the
off-hook condition following generation of a particular combination
of idle and seize tone signal bursts, and wherein said timing
control means further includes circuitry responsive to said third
signal for resetting and activating said timing means.
34. A radio telephone subscriber unit as in claim 33 wherein said
control logic unit further includes means for producing a fourth
signal when said hook switch is replaced in the on-hook condition,
and wherein said timing control means further includes circuitry
responsive to said fourth signal for resetting and activating said
timing means.
35. A radio telephone subscriber unit which includes a radio
telephone base terminal which transmits a plurality of radio
signals for establishing a radio link-up with the subscriber unit,
said subscriber unit including
means for receiving the radio signals transmitted by the base
terminal and for generating digital signals representing such radio
signals,
a hook switch having on-hook and off-hook conditions,
a logic unit for producing a first signal when said hook switch is
placed in the off-hook condition,
timing means for producing a plurality of timing signals at
predetermined timing intervals following activation of the timing
means, and
timing control means responsive to said first signal for resetting
and activating said timing means, responsive to a particular timing
signal produced by said timing means following production of said
first signal for resetting and deactivating said timing means, and
responsive to a particular digital signal for thereafter activating
said timing means.
36. A radio telephone subscriber unit as in claim 35 wherein said
control logic unit further includes means for producing a second
signal when said hook switch is replaced in the on-hook condition
and wherein said timing control means further includes circuitry
responsive to said second signal for resetting and activating said
timing means.
37. A radio telephone subscriber unit for use in a radio telephone
system having a radio telephone base terminal which transmits a
called number signal sequence specifying a subscriber unit
identification number, said subscriber unit comprising:
means for receiving said signal sequence,
means for producing a first plurality of digital counts, each of
said counts representing the value of a different one of the digits
of the identification number specified by said signal sequence,
means for successively storing each of said counts,
means for producing a second plurality of digital counts, each
representing the value of a different one of the digits of an
identification number assigned to said subscriber unit,
means for comparing each count stored in said storing means with a
corresponding count produced by said second plurality producing
means,
means responsive to said comparing means for producing a parity
signal each time a pair of compared counts match,
means for clearing said storing means each time a parity signal is
produced in preparation for storing the succeeding count,
means for causing said second plurality producing means to produce
the succeeding count of the second plurality each time a parity
signal is produced,
means for producing a no-parity signal each time a pair of compared
counts fails to match,
means for generating a last-digit signal if all pairs of compared
counts match,
timing means for producing a time-out signal a predetermined period
of time after each parity signal is produced unless a succeeding
digital count is stored in said storing means within said
predetermined period or unless a last-digit signal is generated,
and
means responsive to said no-parity signal or said time-out signal
for deactivating a predetermined portion of the subscriber unit
components.
38. A radio telephone subscriber unit as in claim 37 wherein said
storing means comprises a binary counter and said second plurality
producing means includes circuitry for producing binary counts.
39. A radio telephone subscriber unit as in claim 37 further
including
means for successively generating a pulse signal,
means responsive to said pulse signals for transmitting to the base
terminal radio signals representing said pulse signals,
means for applying each pulse signal to said storing means to
thereby cause said storing means to increase its count by one,
means responsive to said parity signal for temporarily inhibiting
the generation of pulse signals to allow for clearing said storing
means and to allow said second plurality of producing means to
produce a succeeding count of the second plurality of counts, the
resulting radio signals transmitted to the base terminal thereby
representing the identification number assigned to the subscriber
unit.
40. A radio telephone subscriber unit as in claim 39 further
including means for inhibiting further generation of pulse signals
after a predetermined number of counts has been produced by said
second plurality of producing means.
41. A radio telephone subscriber unit for use in a radio telephone
system having a radio telephone base terminal which transmits a
called number signal sequence specifying a subscriber unit
identification number, said subscriber unit comprising:
means for receiving said signal sequence,
means for producing a first plurality of digital counts, each of
said counts representing the value of a different one of the digits
of the identification number specified by said signal sequence,
means for successively storing each of said counts,
means for producing a second plurality of digital counts, each
representing the value of a different one of the digits of an
identification number assigned to said subscriber unit,
means for comparing each count stored in said storing means with a
corresponding count produced by said second plurality producing
means,
means responsive to said comparing means for producing a parity
signal each time a pair of compared counts match,
means for clearing said storing means each time a parity signal is
produced in preparation for storing the succeeding count,
means for causing said second plurality producing means to produce
the succeeding count of the second plurality each time a parity
signal is produced, and
wherein said second plurality producing means comprises
decoder means having a plurality of output lines, each representing
a different digit of the identification number assigned to the
subscriber unit, and responsive to said parity signals for
successively energizing each of said output lines,
decimal-to-binary converter means having a plurality of input
lines, each representing a different of the decimal digits, and
responsive to the energization of an input line for producing a
binary count equivalent to the value of the decimal digit
represented by that input line, and,
means for connecting said output lines to various ones of said
input lines so that as the output lines are successively energized
the converter means is caused to produce a plurality of counts
representing the identification number assigned to the subscriber
unit.
42. A radio telephone subscriber unit as in claim 41 further
including a mode switch having a manual position and an automatic
position and means for generating a first signal when said mode
switch is in the manual position and for generating a second signal
when the mode switch is in the automatic position, and wherein said
decoder means includes means responsive to said first signal for
energizing a different one of a first set of said output lines in
response to said parity signal and means responsive to said second
signal for energizing a different one of a second set of said
output lines in response to said parity signal.
Description
BACKGROUND OF THE INVENTION
This invention relates to a radio telephone subscriber unit for
communicating with a telephone company base terminal to connect the
subscriber unit to the land line telephone system or to another
radio telephone subscriber unit.
Various types of radio telephone systems are either in present day
use or have been proposed for future use. These include mobile
systems for use with land-based vehicles, marine systems for use
with boats and ships and the like and airborne systems for use with
aircraft in flight. These systems are characterized by the fact
that the subscriber units are not normally tied to a fixed
location, but are instead located aboard a motor vehicle or other
craft which is capable of moving from place to place. While this
adds a considerable degree of mobility to the telephone, there
nevertheless remains a substantial area of telephone usage which
has not yet been tapped. For sake of a name, this untapped area
might be called the "portable" telephone area and involves the use
of a compact light-weight cordless portable telephone which can be
readily hand carried about by a person desiring to use same and
which enables the placing and receiving of telephone calls with
practically the same ease as an ordinary wireline connected
telephone, with the geography of use of such portable telephone not
being restricted to any greater extent than is the geography of use
of a vehicular-type radio telephone. In other words, such portable
telephone can be carried to and used any place within any
geographical area for which the telephone companying provides
vehicular or similar type radio telephone service.
It is an object of the invention, therefore, to provide a new and
improved self-contained cordless portable radio telephone
subscriber unit which may be readily hand carried to and used in
different parts of a city, different cities and in rural areas.
In order to make the usage of such portable radio telephone
subscriber units immediately available to the greatest extent
possible, it is desirable for the present that such portable
subscriber units be capable of use with the vehicular-type mobile
telephone services presently provided by the various telephone
companies. At the present time, the Bell System telephone companies
and other telephone companies (hereinafter referred to collectively
as "telephone company") provide two principal forms of mobile
telephone service. One is known as "MTS" (Mobile Telephone Service)
and the other is known as "IMTS" (Improved Mobile Telephone
Service). The older MTS system is a manual system wherein each
mobile telephone subscriber unit is assigned a particular operating
channel (set of transmit and receive frequencies) for receiving
calls and all calls are placed by going through the telephone
company operator at the base terminal. In the newer IMTS system a
number of radio channels are provided which are accessible to each
of the subscriber units. Between calls, the subscriber units
monitor a particular one of these multiple channels, which channel
is designated by the base terminal transmitting an audio-frequency
"idle" tone on such channel. When the existing idle channel goes
into use, the idle tone signal is shifted to another channel and
the idle subscriber units automatically tune to this new idle
channel. In addition, the base terminal equipment and subscriber
units in the newer IMTS system are constructed to enable the
subscriber units to place and receive telephone calls automatically
without having to go through a telephone company operator.
It is another object of the invention, therefore, to provide a new
and improved portable radio telephone subscriber unit which can be
readily used in existing telephone company mobile telephone
systems.
It is a further object of the invention to provide a new and
improved radio telephone subscriber unit capable of providing both
automatic and manual operation with a minimum of additional
circuitry.
Existing mobile radio telephone subscriber units are not readily
adaptable to provide a very satisfactory form of portable
subscriber unit. For one thing, existing mobile telephone
subscriber equipment is usually relatively heavy and relatively
bulky, this being no particular problem in such equipment's normal
use--since such equipment is in a motor vehicle where the space and
the weight carrying capability are usually available. Also,
existing mobile telephone subscriber equipment is normally
constructed to receive its operating power from the electrical
system of the motor vehicle. Thus, since a relatively large amount
of power is readily available, usage requirements are less
strenuous and the rate of power consumption of such equipment is
greater than is desired for the case of a self-contained battery
operated portable telephone subscriber unit.
It is another object of the invention, therefore, to provide a new
and improved radio telephone subscriber unit which is of a more
compact and more lightweight construction than existing mobile
telephone subscriber equipment.
It is a further object of the invention to provide a new and
improved radio telephone subscriber unit having a power consumption
rating which is considerably less than that of existing mobile
telephone subscriber equipment.
It is an additional object of the invention to provide a new and
improved radio telephone subscriber unit having a high degree of
reliability even under fairly adverse operating conditions.
It is a further object to the invention to provide a new and
improved radio telephone subscriber unit which is flexible in
nature and which is readily adaptable to the specific requirements
and different telephone company radio telephone systems.
For a better understanding of the present invention, together with
other and further objects and features thereof, reference is had to
the following description taken in connection with the accompanying
drawings, the scope of the invention being pointed out in the
appended claims.
BRIEF DESCRIPTION OF THE DRAWINGS
Referring to the drawings:
FIG. 1 shows in a block diagram fashion the general features of a
portable radio telephone subscriber unit constructed in accordance
with the present invention;
FIG. 2 is a timing diagram used in explaining the operation of the
FIG. 1 subscriber unit for the case of automatic mode base terminal
to subscriber unit (incoming) telephone calls;
FIG. 3 is a timing diagram used in explaining the operation of the
subscriber unit for the case of automatic mode subscriber unit to
base terminal (outgoing) telephone calls;
FIG. 4 is a more detailed block diagram of an FM transmitter used
in the FIG. 1 subscriber unit;
FIGS. 5A and 5B (with FIG. 5A positioned above FIG. 5B) show a more
detailed block diagram of a control logic unit and a demand power
supply unit used in the subscriber unit of FIG. 1;
FIG. 6 shows in greater detail the construction of the idle tone
timer, the off-hook detector and the on-hook detector portions of
the FIG. 5 control logic;
FIG. 7 shows in greater detail the construction of the demand power
supply, the reset logic and the controlled reset logic portions of
the FIG. 5 control logic;
FIG. 8 shows in greater detail the construction of the master timer
portion of the FIG. 5 control logic;
FIG. 9 shows in greater detail the construction of the tone input
logic portion of the FIG. 5 control logic;
FIG. 10 shows in greater detail the construction of the digit
decoder-encoder portion of the FIG. 5 control logic;
FIG. 11 shows in greater detail the construction of the
acknowledgement memory, the disconnect memory, the connect memory,
the guide output, the disconnect output, the connect output, the
carrier only output, the output control and the mode control
portions of the FIG. 5 control logic;
FIG. 12 shows in greater detail the construction of the transmitter
turn-on logic and the channel hold generator portions of the FIG. 5
control logic;
FIG. 13 shows in greater detail the construction of the ringing
logic and the no-answer logic portions of the FIG. 5 control
logic;
FIG. 14 shows in greater detail the construction of the call base
gating logic portion of the FIG. 5 control logic;
FIG. 15 shows in greater detail the construction of the call vase
identification logic portion of the FIG. 5 control logic;
FIG. 16 shows in greater detail the construction of the call base
dialing logic portion of the FIG. 5 control logic;
FIG. 17 shows in greater detail the construction of the timer reset
and power down logic portion of the FIG. 5 control logic;
FIG. 18 shows in greater detail the construction of the channel
search oscillator, the CSO lock, the earphone mute circuit and the
speaker mute circuit portions of the FIG. 5 control logic;
FIG. 19 shows in greater detail the construction of a
radio-frequency signal generator used in the FM transmitter of FIG.
2; and
FIG. 20 shows in greater detail the construction of a VOX circuit
used in the FM transmitter of FIG. 2.
DESCRIPTION OF FIG. 1 RADIO TELEPHONE SUBSCRIBER UNIT
Referring to FIG. 1, there is shown a general block diagram of a
radio telephone subscriber unit constructed in accordance with the
present invention. For sake of an example, the FIG. 1 subscriber
unit will be described for the case where it is constructed for use
with the IMTS (automatic) and the MTS (manual) mobile telephone
services presently provided by the telephone company. As such,
reference will occasionally be made to the particular operating
frequencies and particular signal specifications presently in use,
it being clearly understood that such references are by way of
example only and that the invention is not limited to use with such
specific frequencies and signal specifications.
Each base terminal in the existing telephone company IMTS
(automatic dial) mobile telephone system employs one or more or 11
different radio channels, each channel being comprised of a pair of
carrier frequencies, one for the base terminal transmitter and the
other for the mobile unit or subscriber unit transmitter. The base
terminal transmitter carrier frequencies for the eleven different
channels are spaced 30 kilohertz apart with the lowest carrier
frequency being at 152.51 megahertz and the highest carrier
frequency being at 152.81 megahertz. The mobile unit transmitter
carrier frequencies are also spaced 30 kilohertz apart with the
lowest mobile unit transmitter carrier frequency being at 157.77
megahertz and the highest mobile unit transmitter carrier frequency
being at 158.07 megahertz. The base terminal and the mobile unit
transmitter frequencies are paired in numerical order to form the
individual channels, the lowest channel being formed by the lowest
base terminal frequency and the lowest mobile unit frequency, etc.
Both the base terminal and the mobile unit or subscriber unit
employ frequency modulation (FM) type transmitters.
At any given instant, the base terminal designates only a single
one of the eleven different channels as being available for
communication purposes. This is accomplished by modulating a
particular audio-frequency tone onto the radio-frequency carrier
for the desired available channel, such tone being referred to as
"idle" tone. The various subscriber units which are on active
standby (in condition to receive a call) but which are not
presently involved in a telephone call automatically tune to this
idle channel and "listen" to detect the transmission of their
telephone number by the base terminal. The telephone number of a
particular subscriber unit is transmitted by alternately modulating
in a coded manner the base terminal carrier with the idle tone
audio frequency and a second audio frequency called a "seize" tone
frequency. The presently used idle tone audio frequency is 2000
hertz and the presently used seize tone audio frequency is 1,800
hertz.
When the current idle channel becomes occupied, that is, becomes
engaged in making a telephone call, then the steady idle tone is
shifted to another channel and the turned on subscriber units which
are not in use automatically tune themselves to this new idle
channel. This process shifting the idle tone from channel to
channel continues until all assigned channels for a given base
terminal are in use, after which no more phone calls can be placed
through that base terminal until such time as one of the assigned
channels again becomes idle. When all assigned channels are in use,
the "standby" subscriber units which are not in use simply continue
searching through the channels in a sequential manner until one of
the channels becomes idle at which time the subscriber units tune
themselves to a new idle channel.
When the phone call is originated by the subscriber or mobile unit,
such unit initially transmits a coded pattern of particular
audio-frequency tones to establish the connection with the base
terminal and to remove from an idle condition the particular base
terminal channel being used. A set of three specific
audio-frequency tones are employed by each subscriber unit for
purposes of signalling the base terminal. These are commonly
referred to as a "guard" tone, a "connect" tone and a "disconnect"
tone, the presently used frequencies being 2150, 1633 and 1336
hertz, respectively. These tones are transmitted as frequency
modulation of the subscriber unit radio-frequency carrier for the
particular channel being used at the moment and are employed for
signalling purposes during the making of both incoming and outgoing
phone calls.
The telephone company MTS (manual) system is somewhat simpler in
nature. Each mobile unit is assigned a particular channel which it
always uses for the receiving of a phone call, unless the telephone
company is specifically advised that a different channel is to be
used. When the call is originated by the base terminal, the base
terminal operator turns on the base terminal transmitter for the
channel assigned to the particular mobile unit in question and then
dials out the mobile unit phone number in a manual manner. The
mobile unit phone number is transmitted by alternately modulating
the base terminal radio-frequency carrier with two different audio
tones in a coded pattern. A decoder circuit in the mobile unit
recognizes its phone number and activates a ringing circuit in the
mobile unit. The base terminal then transmits a ringing signal
comprised of one of the two audio tones used for signalling
purposes. The mobile unit user then answers the phone and carries
on the conversation. When the phone call is originated by the
mobile unit, the operation is entirely manual. The mobile unit user
manually selects a free channel and causes the generation of the
channel's carrier signal. The base terminal recognizes that the
mobile unit is on the air by detecting the transmission of its
carrier signal. Thereafter, the phone call is completed by way of
voice conversation between the base terminal and mobile unit
operators.
In the MTS system, the mobile unit does not transmit any signalling
tones during the course of either an incoming call or outgoing
call. The only audio-frequency signalling tones employed are those
transmitted by the base terminal for purposes of activating the
ringing circuit in a particular mobile unit. For sake of
convenience only, the two manual mode base terminal signalling
tones may sometimes be referred to herein as "idle" and "seize"
tones. It is to be clearly understood, however, that this is
strictly a misnomer because the telephone company does not employ
an "idle" tone to mark an idle channel in the MTS system. In fact,
the base terminal transmitter is off the air when the channel
serviced by same is not in use. At the present time, the two tone
signalling audio frequencies employed in the MTS system are 1,500
and 600 hertz.
BASE TERMINAL TO MOBILE (INCOMING) CALL -- IMTS MODE
Considering now the subscriber unit of FIG. 1 and considering first
the case of automatic mode (IMTS) incoming call (a call being
received by the subscriber unit), the radio-frequency signal
transmitted by the base terminal is received by an antenna 102 of
the subscriber unit and supplied by way of a duplexer 106 to a
frequency modulation (FM) radio receiver 110. FM receiver 110
demodulates or separates out the audio-frequency signals carried by
the base terminal carrier signal and supplies such audio-frequency
signals to a tone detector 114 and a muting circuit 118. Muting
circuit 118 is a gated amplifier circuit and serves to control the
passage of audio signals from the FM receiver 110 to an amplifier
146 and loud speaker 150 and to the earphone or earpiece portion of
a telephone handset 122. In the present embodiment, telephone
handset 122 is of the known type wherein the dialing mechanism as
well as the earpiece and the microphone or mouthpiece are mounted
in a unitary hand-held structure.
Tone detector 114 includes tuned amplifier and detector cricuits
for producing output signals indicative of the presence and absence
of the idle and seize tones when in the automatic mode or the
presence and absence of the low and high frequency signalling tones
when in the manual mode. Thus, if the audio-frequency signal
applied to the tone detector 114 is either idle tone or the lower
frequency manual mode tone, the tone detector applies a signal to a
control logic unit 126 via lead IL and if the audio-frequency
signal is either seize tone or the higher frequency manual mode
tone, the tone detector applies a signal to the control logic unit
via lead SL. The tone detector 114 might illustratively comprise
the tone detector circuit disclosed in copending patent application
Ser. No. 185,518, filed Oct. 1, 1971.
Radio frequency signals transmitted by the subscriber unit to the
base terminal are generated by the FM transmitter 130 in response
either to voice modulating signals from the microphone of the
telephone handset 122 or tone modulating signals from a tone
generator 134 operating under the control of the control logic unit
126. The FM transmitter generated signals are applied by way of the
duplexer 106 to the antenna 102 for transmission to the base
terminal. Whenever the transmitter 130 is transmitting, current is
applied to a light-emitting diode 162 causing the diode to emit
light to notify the subscriber user that transmission is taking
place.
Now assume that the subscriber unit has just been turned on so that
power is being supplied by a battery operated power supply 138 to a
demand power supply 142 and to the other circuitry of the
subscriber unit excluding certain circuitry of the control logic
unit 126 which obtains its power via the demand power supply 142.
Power supply 138 includes one or more light-weight batteries which
represent the primary power source for the subscriber unit. Power
supply 138 also includes various voltage regulator circuits for
taking the terminal voltage of the battery pack (+A) and reducing
it down to a series of lesser direct-current voltage levels (+B, +C
and -D), which voltages are regulated to minimize changes in such
levels as the battery terminal voltage falls off with use of the
subscriber unit. By way of example only, the +A may be +13 volts,
+B may be +10 volts, +C may be +5 volts and -D may be -6 volts. If
the battery terminal voltage falls below some minimum level,
current is applied to a light-emitting diode 154 causing the diode
to emit light and thereby warn the subscriber unit user that the
power supply is low. An exemplary battery operated power supply
which could be utilized in the present invention is disclosed in
copending patent application Ser. No. 175,305, filed Aug. 26,
1971.
Upon turning on the subscriber unit, the unit commences to search
over the channels in a sequential manner until idle tone is
detected on one of the channels. Searching over the channels is
carried out under the control of the control logic unit 126 which
successively applies channel search pulses to the FM transmitter
130 via the "search" lead to cause the transmitter to successively
change its internally produced carrier frequency and also the
frequency of the local oscillator signal applied to the FM receiver
110. The local oscillator signal and the signal received from the
base terminal are heterodyned by a mixer in the FM receiver 110 to
produce an output signal whose frequency equals the difference
between the frequency of the local oscillator signal and the
frequency of the received signal. When the idle tone is detected at
the output of the receiver 110 by the tone detector 114, the
detector applies a signal via the IL lead to the control unit 126.
In response thereto, the control logic unit 126 ceases applying
channel search pulses to the transmitter 130 via the "search" lead
so that transmitter maintains the local oscillator signal at the
then-current frequency which designates the channel on which the
idle tone was received. The FM transmitter 130 is now "locked" to
the channel over which the idle tone was received. The other units
would which are turned on similarly lock onto this channel.
To establish a "connection" with a particular subscriber unit, the
base terminal removes the idle tone and transmits a seize tone of
duration of from 0.25 to 1.4 seconds. Replacement of the idle tone
by the seize tone is graphically illustrated in FIG. 2 which is a
timing diagram showing the sequence of signals transmitted between
the base terminal and a subscriber unit for a base terminal to
subscriber unit (incoming) call. The seize tone is detected by the
tone detector 114 which applies a signal via the SL lead to the
control logic 126 causing the control logic to turn on the demand
power supply 142. Power is now supplied by way of the demand power
supply to that circuitry in the control logic unit 126 not
otherwise powered directly by the battery operated power supply
138.
After a short period of seize tone, the base terminal transmits the
phone number of the subscriber unit being called. The phone number
is designated by interrupting the seize tone with groups of idle
tone bursts, the number of idle tone bursts in each group
representing the digit value of one of the digits of the phone
number. The duration of the idle tone burst and of the seize tone
between the idle tone bursts is 50 milliseconds. The duration of
seize tone between each group of idle tone bursts is approximately
300 milliseconds and is provided to specify the end of each digit
of the phone number. Transmission of the subscriber unit phone
number is represented by interval B in FIG. 2, only a portion of
which is shown for convenience of illustration. FIG. 2 also shows
that the demand power supply is turned on at the beginning of
interval B.
After each group of idle tone pulses is received and the control
logic unit 126 is signalled accordingly, the control logic unit
compares the digit represented by the group with a corresponding
"stored" digit to determine if the digits match. If a mismatch
occurs for any pair of compared digits, the control logic unit 126
resets its logic circuitry, turns off the demand power supply 142,
and commences supplying pulses via the "search" lead to the FM
transmitter 130 to cause the subscriber unit to resume searching
for the idle channel. If all pairs of compared digits match, the
control logic unit 126 signals a tone generator 134 via the GX lead
causing the tone generator to generate a guard tone (2150 hertz)
which is applied to the FM transmitter 130 to modulate the
transmitter carrier frequency. At the same time, the control logic
126 produces a transmit signal on lead XMIT which enables the
transmitter 130 to supply the guard tone modulated carrier signal
by way of the duplexer 106 to the antenna 102 for transmission to
the base terminal. This guard tone, which continues for 750
milliseconds, serves as an acknowledgement signal indicating to the
base terminal that the transmitted phone number was received and
that the called subscriber unit is available (see interval C of
FIG. 2). An illustrative tone generator which could be utilized for
the tone generator 134 is the circuit disclosed in copending patent
application Ser. No. 185,745, filed Oct. 1, 1971 and now U.S. Pat.
No. 3,763,322.
At the same time the guard tone is transmitted to the base
terminal, the control logic unit 126 signals an amplifier 146 via a
"ring gate" lead causing the amplifier to increase its gain; the
control logic unit 126 also signals the muting circuit 118 enabling
it to pass audio signals received from the FM receiver 110 to the
amplifier 146 and the telephone handset 122.
Upon termination of transmission of the guard tone by the
subscriber unit, the base terminal commences to transmit a ringing
signal comprising alternate pulses of idle tone and seize tone of
25 milliseconds each. Such pulses are transmitted for a period of 3
to 4 seconds followed by about 3 seconds of seize tone alone,
which, in turn, is followed by alternate pulses idle and seize
tone, etc. The alternate idle and seize tone signals are applied by
the FM receiver 110 to the amplifier 146 via the muting circuit
118. The amplifier 146 amplifies the signals and applies them to a
loudspeaker 150 which produces audible sound vibrations to alert
the subscriber unit user that his unit is being called. The ringing
signal sequence is represented by interval D of FIG. 2. Utilizing
the audio amplifier 146 and the loudspeaker 150 to provide the
audible indication to the subscriber unit user dispenses with the
need for a conventional and more expensive ringing circuit.
If the call remains unanswered for about 45 seconds (during which
time the ringing signals are being transmitted to the subscriber
unit), the base terminal terminates transmission of the ringing
signals after which the control logic unit 126 turns off the demand
power supply 142 and causes the subscriber unit to commence
searching for an idle channel.
Upon hearing the audible ringing sound, the subscriber unit user
removes the handset 122 from its cradle or switch hook causing a
signal to be applied via the "hook" lead to the control logic unit
126. In response thereto, the control logic unit applies a connect
tone signal to the tone generator 134 via lead CX causing the tone
generator to generate 400 milliseconds of connect tone (1633
hertz). The control logic unit also applies a transmit signal via
lead XMIT to the transmitter 130 enabling it to transmit connect
tone to the base terminal (see interval E of FIG. 2). Upon receipt
of the connect tone, the base terminal removes the ringing signals
from the channel and the conversation may commence. Following
termination of transmission of the connect tone, the control logic
unit 126 turns off the demand power supply 142 as indicated in FIG.
2.
During the course of the conversation, the control logic unit 126
monitors the transmitter (by means of the XMIT lead) to determine
if transmissions are being made thereby, i.e., to determine if
carrier frequency is being transmitted. If no carrier signal
transmissions are made for a period of about 10 seconds, the
control logic unit signals the FM transmitter 130 via lead XMIT
causing the transmitter to generate a short burst of carrier
frequency at this time and at ten second intervals thereafter until
the subscriber unit user causes carrier frequency to be
transmitted--either by speaking into the microphone of the
telephone handset 122 or by manual operation of a push-to-talk
switch on the handset (see interval F of FIG. 2). These bursts of
carrier frequency ("channel hold" signals) notify the base terminal
that the connection is to be maintained. If no provision were made
for transmitting some such signal, the base terminal would
disconnect the subscriber unit after about a 12 second lull in
subscriber unit transmission. Transmitting bursts of carrier
frequency rather than a continuous carrier signal conserves the
power supply of the subscriber unit.
While in conversation, voice modulated radio signals are received
from the base terminal by the antenna 102 and applied via the
duplexer 106 to the receiver 110 which demodulates the signals and
applies the resulting audio signal via the muting circuit 118 to
the earphone inside the telephone handset 122. Voice transmission
from the subscriber unit to the base terminal is carried out when
the mouthpiece or microphone inside the telephone handset 122 picks
up audible signals from the subscriber unit user and applies a
resulting audio signal via the "voice" lead to the FM transmitter
130. This audio signal actuates the transmitter 130 to generate a
voice modulated signal which is transmitted to the base terminal.
As indicated earlier, provision is also made for actuating the
transmitter 130 by depressing a push-to-talk switch located in the
telephone handset 122. Depressing the push-to-talk switch results
in a signal being applied via the "talk switch" lead to the control
logic unit 126 which then actuates the transmitter 130 via the XMIT
lead.
When the conversation is concluded, the subscriber unit user
replaces the telephone handset 122 on the switch hook causing a
signal to be applied via the "hook" lead to the control logic unit
126. In response thereto, the control logic unit 126 alternately
applies signals via the DX and the GX leads to the tone generator
134 causing the tone generator to generate a 750 millisecond
disconnect signal sequence consisting of alternate 25 milliseconds
bursts of disconnect tone and guard tone together with the carrier
frequency. This is illustrated as interval G of FIG. 2. The
disconnect signal sequence is transmitted to the base terminal to
inform the base terminal that the call is concluded and that the
channel is free for further use. Upon termination of transmission
of the disconnect signal sequence, the control logic unit 126 turns
off the demand power supply 142 and initiates channel searching as
previously described.
MOBILE-TO-BASE STATION (OUTGOING) CALL -- IMTS MODE
FIG. 1 will now be described for a call initiated by the subscriber
unit (outgoing call) for the IMTS mode of operation. FIG. 3 which
is a timing diagram graphically illustrating the signals
transmitted between the base terminal and a subscriber unit for a
subscriber unit initiated call, will be utilized in conjunction
with the FIG. 1 description.
Assuming that the FM transmitter 130 of the subscriber unit has
"locked" onto an idle channel, the tone detector 114 detects the
idle tone and energizes a lamp 158 to indicate to the subscriber
unit user that an idle channel is available. To originate a call,
the user removes the telephone handset 122 from the switch hook
causing a signal to be applied via the "hook" lead to the control
logic unit 126 in turn causing the control logic unit to turn on
the demand power supply 142. (Note that if the telephone handset
122 is removed from the switch hook before the unit has "locked"
onto an idle channel, the channel searching is stopped and the
demand power supply 142 is not turned on.) The control logic unit
126 also signals the tone generator 134 and the FM transmitter 130
to transmit 350 milliseconds of guard tone (see interval K of FIG.
3). If, after the transmission of 350 milliseconds of guard tone,
the control logic unit 126 determines that the idle tone is still
present on the channel to which the subscriber unit is locked, the
control logic unit signals the tone generator 134 and the FM
transmitter 130 to transmit 50 milliseconds of connect tone
(interval L of FIG. 3). If, after transmission of the connect tone,
the control logic unit 126 determines that the idle tone has been
removed from the channel to which the subscriber unit is locked,
the control logic unit signals the tone generator 134 and the FM
transmitter 130 to again transmit guard tone (interval M of FIG.
3).
If, after the transmission of the 350 milliseconds of guard tone,
the control logic unit 126 determines that the idle tone is not
being received, or if, after transmission of the 50 milliseconds of
connect tone, the control logic unit determines that the idle tone
is being received, then the demand power supply 142 is turned off,
the control logic unit circuitry is reset, and the subscriber unit
commences searching for an idle channel. Failure to detect the idle
tone following the 350 milliseconds of guard tone indicates that
the channel to which the subscriber unit was locked has been seized
by another subscriber unit. Detecting the idle tone following the
50 milliseconds of connect tone indicates that the base terminal
has not responded to the subscriber unit's "dial request." In
either case, the subscriber unit simply starts over again to search
for an idle channel.
During the transmission of the second period of guard tone, the
subscriber unit "waits" for the arrival of a burst of seize tone
from the base terminal. This seize tone burst indicates too the
subscriber unit that the base terminal is ready to receive the
subscriber unit's identification number, i.e., phone number.
Following the arrival of the seize tone and approximately 190
milliseconds after the termination thereof, the subscriber unit
commences transmitting its identification number under the control
of the control logic unit 126 (interval N of FIG. 3). Each digit or
numeral of the identification number consists of a number of 25
milliseconds bursts of connect tone corresponding in number to the
numeral represented. Alternately interspersed between the connect
tone bursts are unmodulated carrier frequency and guard tone. Thus,
referring to interval N of FIG. 3, the first digit of the
identification number there illustrated (the number 3) consists of
carrier modulated by connect tone, unmodulated carrier frequency,
carrier modulated by connect tone, carrier modulated by guard tone,
and carrier modulated by connect tone. For convenience of
illustration, only a portion of the identification interval N is
shown.
Between the digits of the identification number, the unmodulated
carrier frequency or carrier modulated by guard tone is transmitted
for 190 milliseconds. Thus, again referring to interval N of FIG.
3, after the first digit of the identification number, unmodulated
carrier frequency is transmitted and after the second digit (which
is also the numeral 3), carrier modulated by guard tone is
transmitted, etc. Following transmission of the last digit of the
identification number, the control logic unit 126 applies a signal
to the muting circuit 118 enabling the muting circuit to pass audio
signals from the FM receiver 110 to the earphone of the telephone
handset 122; the subscriber unit then simply waits for receipt of
dial tone from the base station (see interval O of FIG. 3). After
receipt of the dial tone, the subscriber unit user may commence to
dial the number he desires to call.
Dialing is accomplished utilizing a dialing mechanism located on
the telephone handset 122. When the dial is "cocked" (prior to
releasing), the control logic 126, in response to a signal from the
telephone handset 122, signals the tone generator 134 to generate
guard tone. Upon release of the dial mechanism and in response to a
sequence of signals from the telephone handset 122 resulting from
alternately opening and closing a set of contacts, the control
logic unit 126 causes the tone generator to generate a sequence of
alternate connect and guard tone bursts, with the number of connect
tone bursts corresponding to the value of the digit being dialed.
Following the last connect tone burst of a digit, a guard tone
pulse is transmitted and then both the carrier frequency and guard
tone are interrupted until the dial mechanism is again cocked at
which time the guard tone and carrier frequency are again
generated. The process is then repeated as described above
(interval P of FIG. 3). If approximately 10 seconds elapses between
the dialing of digits, the control logic unit 126 turns off the
demand power supply 142 and, upon the telephone handset 122 being
placed on the switch hook, commences the disconnect operation as
previously described for the case of an incoming call (interval G
of FIG. 2).
Upon completion of dialing, the control logic unit 126 turns off
the demand power supply (as indicated in FIG. 3) and the subscriber
unit user listens for either the audible ringing signal (indicating
that the called number is not busy) or the buy signal (indicating
that the called number is busy). If the called party answers, the
conversation may commence in the normal manner. As indicated
earlier for an incoming call, during the course of the conversation
when no voice transmissions are being made by the subscriber unit,
the control logic unit 126 causes the transmitter 130 to transmit
repetitive bursts of unmodulated carrier frequency to "hold" the
channel. This is shown in interval Q of FIG. 3.
At the conclusion of the conversation, the subscriber unit user
places the telephone handset 122 on the switch hook causing the
control logic unit 126 to turn on the demand power supply 142 and
to signal the tone generator 134 and FM transmitter 130 to transmit
the disconnect signal sequence in the same manner as described
earlier for the case of an incoming call (for the outgoing call,
see interval R of FIG. 3). Following transmission of the disconnect
signal sequence, the control logic unit 126 turns off the demand
power supply 142 and the subscriber unit commences searching for an
idle channel. It should be noted that the disconnect signal
sequence is also transmitted to the base terminal following the
replacement of the telephone handset 122 on the switch hook upon
encountering a busy line.
If the called party hangs up before the subscriber unit user, the
base terminal will "take down" the connection, but the subscriber
unit will remain locked onto the channel until the user places the
telephone handset on the switch hook--after which the disconnect
signal sequence will be transmitted as previously described.
As is apparent from the description of the FIG. 1 subscriber unit,
one of the significant features of the disclosed embodiment is the
operation and control of the demand power supply 142. To briefly
summarize, the demand power supply prevents the application of
power from the battery operated power supply 138 to a large portion
of the circuitry of the control logic unit 126, placing such
circuitry on a "standby" basis, when no call is in progress and
also during the conversation interval of a call. The drain on the
battery operated power supply 138 is thus minimized. That portion
of the circuitry of the control logic unit 126 which receives its
power from the demand power supply 142 is noted in the more
detailed drawings FIGS. 6-18. Specifically, the demand power supply
illustratively supplies power to all circuitry of the control logic
unit except those components connected to one of the battery
operated power supply terminals +A, +B, +C or -D and those
components designated by an asterisk in FIGS. 6-18.
MTS MODE
As previously indicated, when operating in the MTS (manual) mode,
the subscriber unit does not transmit any signalling tones to the
base terminal for either an incoming or an outgoing call. Also, no
automatic channel searching takes place and the muting circuit 118
is always enabled or turned on to pass audio signals to the
telephone handset. For an incoming call, the base terminal
tramsmits the subscriber unit number over a particular channel
assigned to that subscriber unit. Upon receipt of the appropriate
number by the subscriber unit, the control logic unit 126 activates
the amplifier 146 (to increase its gain) and enables the muting
circuit 118 to pass signals from the FM receiver 110 to the
amplifier 146 just as in the IMTS mode. No acknowledgement signal
sequence, however, is transmitted to the base terminal. Rather, the
base terminal after transmitting the subscriber unit number,
commences to transmit a ringing signal. The ringing signal is
applied by the receiver 110 by way of the muting circuit 118 to the
amplifier 146 which actuates the speaker 150 to notify the
subscriber unit user of the incoming call. The subscriber unit user
may then remove the telephone handset 122 from the switch hook and
commence the conversation. At the conclusion of the conversation,
the subscriber unit user replaces the telephone handset 122 on the
switch hook after which the control logic unit 126 resets its logic
circuitry in preparation for another call.
For an outgoing call in the MTS mode, the subscriber unit user
manually searches for a channel by operating appropriate buttons or
switches in the F.M. transmitter 130 designating the different
channels. Operating a particular switch causes the FM transmitter
to generate the local oscillator signal designating the channel
corresponding to the particular switch. When the user locates a
channel which is not being used (determined simply by listening to
hear if the channel is clear) the user operates the push-to-talk
switch on the telephone handset 122 causing a signal to be applied
via the "talk switch" lead to the control logic unit 126. The
control logic unit 126 then signals the transmitter 130 to cause
the transmission of a carrier signal (designating the selected
channel) for the period during which the push-to-talk switch is
operated. The carrier signal notifies the base terminal that the
subscriber unit user desires to place a call on the selected
channel. The base terminal operator then connects to the designated
channel and orally receives the call request information from the
subscriber unit user. The connection is then established by the
base terminal operator and the conversation commences. Again, no
signalling tones are transmitted from the subscriber unit user to
the base terminal.
DESCRIPTION OF FIG. 4 FM TRANSMITTER
FIG. 4 shows the FM transmitter 130 of FIG. 1 in greater detail.
The transmitter includes a radio frequency signal generator 402
which is capable of generating the various channel carrier
frequencies used in the radio telephone system. As will become more
clear when describing the radio frequency signal generator 402 in
greater detail in conjunction with FIG. 19, the signal generator
includes a stepping circuit mechanism which is driven by the
channel search pulses supplied to lead CSO ("search") to select a
particular one of the carrier frequencies. The signal generated by
the signal generator 402 is applied to a phase modulator 410 and a
frequency multiplier 406. The frequency of the signals applied to
the frequency multiplier 406 is increased by a factor of 18 and the
resulting signals are applied to the FM receiver 110 (FIG. 1) for
use as the local oscillator signal for tuning the receiver to the
respective channels. When it is determined that the subscriber unit
is tuned to an idle channel, the control logic unit 126 ceases
applying channel search pulses to the radio frequency signal
generator 402 and the signal generator remains "locked" to the
signal specifying the idle channel, i.e., the signal generator
continues to generate the carrier signal which determines the idle
channel.
The signal applied by the radio frequency signal generator 402 to
the phase modulator 410 is modulated in accordance with tone
signals received from the tone generator 134 (FIG. 1) via the
"tone" lead or voice signals received from the microphone 412 of
the telephone handset 122 (FIG. 1) via the "voice" lead. (The "mike
mute" lead is provided to "mute" the microphone 412 when the lead
is grounded.) The tone signals or voice signals are applied to an
audio amplifier 426 which amplifies the signals and applies them to
an amplitude limiter 430 and a voice operated transmitter (VOX)
circuit 434 (shown in greater detail in FIG. 20). The amplitude
limiter 430 clips the peaks of the signal received from the audio
amplifier 426 and applies the resultant signals to a driver and
roll-off filter circuit 438. The driver and roll-off filter circuit
438 reduces the high frequency components of the signals to a
relatively low amplitude and applies the resultant modulating
signals to the phase modulator 410. The phase modulator 410 then
"phase modulates" the signals received from the radio frequency
generator 402 in accordance with the signals from the driver and
roll-off filter circuit 438 and applies the modulated signals to a
gated amplifier 418. Depending on the condition of a gate lead
input 442, the gated amplifier 418 either does nothing with the
modulated signals or amplifiers and applies them to a frequency
multiplier 422. If signals are applied to the frequency multiplier
422, the multiplier increases the frequency of the signals by a
factor of 18 and applies the resultant signals to a power amplifier
450. The power amplifier 450 increases the power of the signals and
applies them to the duplexer 106 (FIG. 1) to be transmitted to the
base station. While supplying the signal to the duplexer, the power
amplifier 450 also applies current to the light-emitting diode 162
causing the diode to emit light and thereby indicate that
transmission is taking place.
The gated amplifier 418 is actuated to amplify the signals received
from the phase modulator 410 and to apply the resultant amplified
signals to the frequency multiplier 422 in response to a signal
received from the VOX circuit 434 or received over lead XMIT from
the control logic unit. The VOX circuit 434 applies a signal to the
gated amplifier 418 in response either to an amplified tone or
voice signal from the audio amplifier 426 (provided a switch 446 is
in the "VOX ON" position) or a "channel hold" signal from the
control logic unit (independent of the condition of switch 446). If
a "channel hold" signal is received, the VOX circuit 434 actuates
the gated amplifier and an unmodulated carrier signal is applied to
the frequency multiplier 422, whereas if an amplified tone or voice
signal received, the VOX circuit 434 actuates the gated amplifier
and a modulated carrier signal is applied to the multiplier 422.
Whenever a tone signal is generated and applied to the audio
amplifier 426, the control logic unit 126 also applies a signal via
the XMIT lead to actuate the gated amplifier 418 and thereby ensure
transmission of the tone signal in case the switch 446 has been
placed in the "VOX OFF" position (in which case the VOX circuit 434
would not enable the gated amplifier 418). As has already been
noted, the output signal of the VOX circuit 434 is also, in effect,
fed back to the control logic unit 126 by way of the XMIT lead to
provide an indication of when the VOX circuit 434 is enabling the
gated amplifier 418, and thus of when transmission is taking
place.
DESCRIPTION OF FIG. 5 CONTROL LOGIC UNIT
Composite FIG. 5 shows the control logic unit 126 in "block
diagram" detail together with the demand power supply 142. The
component units of the control logic unit and also the demand power
supply are shown in greater detail in the figures indicated.
Operation of the control logic unit and demand power supply will be
described first for an incoming call in the IMTS mode, then for an
outgoing call in the IMTS mode and finally for the MTS mode
generally. Note that many of the leads interconnecting the various
units of FIG. 5 are identified by letters or numerals some of which
have a bar thereabove and others of which do not. Those leads
identified with letters or numerals having the bar are normally at
the binary one or "high" level condition (e.g., +5 volts) and
application of a signal thereto will be taken to mean that the
binary zero or "low" level condition (e.g., zero volts) is produced
thereon. Such signals may be of relatively short duration, in which
case they may be referred to as pulses, or of relatively long
duration, in which case they may be referred to simply as signals.
Those leads identified by letters or numerals without the bar are
normally at the binary zero level and application of a signal
thereto will be taken to mean that a binary one condition is
produced thereon. Although the functions of many of the leads will
be discussed when describing FIG. 5, the functions of other of the
leads which are not essential to an understanding of the overall
operation of the FIG. 5 circuitry will be discussed when describing
the other FIGS. of the drawings.
INCOMING CALL -- IMTS MODE
Assume that the subscriber unit of which the FIG. 5 circuitry is a
part has not yet "locked" onto an idle channel and that a mode
selector switch 578 is in the open or "automatic" position to
enable the subscriber unit to operate in the automatic mode. In
such case, no idle tone is being received from the base terminal
and lead IL (left side of FIG. 5) from the tone detector 114 will
be "low" making lead IL "high" (by operation of an inverter circuit
502). When lead IL is high as well as leads CSL (from a channel
search oscillator [C.S.O.] lock circuit 512) and MA (from a mode
control circuit 560) being high, leads HK2 (from an off-hook
detector circuit 548) and XON (from a transmitter turn-on logic
circuit 540) being low, and either lead SL (from the tone detector
114) or PUF (from the demand power supply 142) being low, a channel
search oscillator 520 applies a succession of positive-going
channel search pulses via lead CSO to the transmitter 130 (FIG. 1)
causing the transmitter to successively change the frequency of the
local oscillator signal applied to the receiver 110. In other
words, the subscriber unit is caused to search for an idle channel.
For information purposes, lead SL is low when no seize tone is
being received by the subscriber unit, lead HK2 is low when the
telephone handset 122 is on the switch hook, lead MA is high when
the subscriber unit is operating in the IMTS mode, lead XON is low
when the subscriber unit is not transmitting, and lead PUF is low
when the demand power supply 142 is turned off. When an idle
channel is found, i.e., the idle tone is detected, the tone
detector 114 (FIG. 1) applies a high signal to lead IL and thus
causes the IL lead to be brought low which, in turn, causes the
channel search oscillator 520 to cease applying channel search
pulses to lead CSO.
With each positive-going pulse applied to lead CSO, the channel
search oscillator 520 applies a negative-going pulse to lead CSO.
These pulses on lead CSO are applied to the demand power supply 142
to prevent it from being turned on (e.g., by spurious signals)
while the channel search pulses are being generated on lead
CSO.
The high signal on lead IL also causes an idle tone timer 534 to
commence timing for an interval of 120 milliseconds. If, before the
termination of this interval, lead IL is brought low indicating
that the idle tone is no longer being received and thus that a true
base terminal idle channel has not been found, the idle tone timer
534 simply resets and the subscriber unit commences searching for
the next idle channel. If lead IL remains high for this interval,
the idle tone timer 534 arms itself to apply a low pulse to lead PU
upon the subsequent receipt of a low signal over either of the
leads SL or HK2. If a low signal is subsequently received over lead
SL indicating that seize tone has been detected on the idle
channel, the idle tone timer 534 applies a low pulse to lead PU
thereby turning on ("powering up") the demand power supply 142.
When the demand power supply is turned on, it causes a reset logic
circuit 538 to apply a low pulse to lead RS and a high pulse to
lead RS and causes a controlled reset logic circuit 544 to apply a
low pulse to lead CRS. These pulses on leads RS, RS and CRS cause
various component units of the FIG. 5 control logic unit to be
reset as will become clear upon examination of the drawings of the
individual component units to which such leads are connected. The
demand power supply 142 also at this time causes the reset logic
circuit 538 to apply a short low signal to lead RSX and this, in
turn, causes an output control circuit 558 to apply a similarly
short low signal via lead OC to a guard output circuit 524, a
disconnect output circuit 526, a connect output circuit 528, and a
carrier only output circuit 530. The low signal on lead OC inhibits
the named circuits from enabling any transmission of tone signals
from the subscriber unit to the base terminal while the demand
power supply is being "powered up." Noise, for example, might
otherwise cause such transmission.) Finally, the demand power
supply 142 applies a high signal to lead PUF which, in conjunction
with a high signal on the SL lead, prevents the channel search
oscillator 520 from generating pulses on the CSO lead. The high
signal on lead PUF also enables the output control circuit 558 to
apply a high signal to its output lead OC following termination of
low signal on lead RSX and providing the mode selector switch is in
the "AUTO" position. This high signal on lead OC enables the output
circuits 524, 526, 528 and 530 to operate. Thus, before the demand
power supply is turned on, these output circuits are inhibited from
operating. The above actions take place each time the demand power
supply is turned on. The remaining output lines of the demand power
supply 142 are for control purposes for indicating the status of
the power supply as will be discussed later when describing FIG.
7.
In response to the low pulse on lead RS, a timer reset and power
down logic circuit 536 applies a high signal to lead TR (timer
reset) thereby resetting a master timer 546 and at the same time
inhibiting operation of the timer. In further response to the low
pulse on lead RS, the timer reset and power down logic 536 arms
itself to apply a low signal to lead PDA if, after a predetermined
interval, an idle tone has not been received by the subscriber
unit. The low signal on lead PDA turns off the demand power supply
142 and causes the controlled reset logic 544 to apply a low pulse
to lead CRS, which in turn causes the reset logic 538 to apply a
low pulse to lead RS. The subscriber unit then commences searching
for an idle channel.
As the name implies, the timer reset and power down logic circuit
536 controls the operation of the timer 546 and generates "power
down" signals on leads PDA and PD which are used to turn off the
demand power supply 142 upon the occurrence of certain events
during the course of a telephone call.
Assuming that idle tone (representing the beginning of the called
telephone number) is received following receipt of the seize tone,
the IL lead is made low causing the timer reset and power down
logic 536 to bring the TR lead low enabling the master timer 546 to
commence operating. The master timer 546 produces output signals at
various points in time indicated by the output leads thereof. Thus,
the signal level on lead 25 is changed every 25 milliseconds
following the commencement of operation of the master timer, the
signal on lead 50 is changed every 50 milliseconds following
commencement of operation, etc. Pulses are produced on leads CL and
350P every 25 and 350 milliseconds respectively following
commencement of operation. These timing signals and pulses are used
to control the operation of various ones of the other logic
circuits. As will become apparent in the course of describing FIG.
5, the master timer 546 is automatically reset and started upon
receipt of certain signals from the base terminal and upon the
occurrence of certain operations in the control logic unit. Such
automatic and periodic resetting and restarting eliminates the need
for continually resynchronizing the master timer.
Receipt of the initial idle tone burst (following the seize tone)
and of each subsequent idle tone burst causes a tone input logic
circuit 570 to apply a low pulse via lead ILP to a digit decoder
encoder 510. The tone input logic 570 was prevented from applying
such a pulse to the digit decoder-encoder 510 previously because
the demand power supply 142 was not yet turned on and therefore
power was not being applied to the tone input logic. The pulses
received by the digit decoder-encoder 510 correspond to the idle
tone bursts received and therefore represent the called subscriber
unit number. Each transition from either idle tone to seize tone or
from seize tone to idle tone during receipt of the signals
representing the called subscriber unit number, causes the tone
input logic 570 to apply a low pulse via lead TP to the timer reset
and power down logic 536. This pulse causes the timer reset and
power down logic 536 to reset and restart the master timer 546.
The pulses applied via the ILP lead to the digit decoder-encoder
510 are counted by the encoder-decoder. After counting a group of
such pulses (representing a digit of the called number), the 300
millisecond interdigit seize tone is transmitted by the base
terminal. The transition from the last idle tone burst of the group
to the seize tone causes the resetting and restarting of the master
timer 546; and after the elapse of 175 milliseconds, the master
timer applies a signal via lead 175 to the digit decoder-encoder
510. In response thereto, the decoder-encoder compares the count
(of pulses from the tone input logic circuit 570) with a
corresponding count "stored" in the encoder-decoder. The
decoder-encoder 510 is, in effect, comparing a digit of the called
number with a corresponding digit of the subscriber unit's phone or
identification number to determine if the digits match and thus,
ultimately, if the called number corresponds to the subscriber
unit's number. If the digits compared do not match, the digit
decoder-encoder 510 will, upon the subsequent receipt of a signal
from the master timer 546 over lead 200, apply a "no parity pulse"
to lead NPP. This pulse causes the timer reset and power down logic
536 to apply a low pulse via lead PDA to the demand power supply
142 and the controlled reset logic 544 which as already discussed,
turns off the demand power supply and causes the subscriber unit to
commence searching for the next idle channel.
If the digits compared by the digit decoder-encoder 510 match, upon
the subsequent receipt of a signal from the master timer 546 via
lead 200, a pulse counter (located in the digit decoder-encoder)
which counts the pulses received from the tone input logic circuit
570 is reset and the digit decoder-encoder 510 prepares to compare
the next digit of the subscriber unit number with the next digit
received from the base station. At this same time, a "parity pulse"
is applied to lead PP causing the timer reset and power down logic
536 to apply a high signal via lead TR to the master timer 546
thereby resetting and inhibiting the timer from operating. The
pulse on lead PP also arms the timer reset and power down logic 536
to apply a low signal to lead PDA if, after a certain predetermined
period of time, the next group of idle tone pulses is not received
from the base station (assuming that the previous group was not the
last group to be received). The low signal on lead PDA would turn
off the demand power supply 142 and reset the subscriber unit as
already discussed. If the next group of idle tone bursts arrives
before the termination of this predetermined period, the tone input
logic circuit 570 applies a corresponding sequence of low pulses
via the ILP Lead to the digit decoder-encoder 510 and in response
thereto the decoder-encoder applies a high pulse via lead PR to the
timer reset and power down logic 536. As a result, the timer reset
and power down logic 536 is prevented from applying a low signal to
lead PDA, for which it was earlier armed, and is also caused to
reset and restart the master timer 546. The control logic unit of
FIG. 5 then continues processing the group of idle tone bursts then
being received as previously described.
The digit decoder-encoder 510 maintains a count of the number of
groups of pulses received from the tone input logic circuit 570,
i.e., the number of received phone number digits, and, after
receipt of the last digit of a number, the digit decoder-encoder
places a high condition on lead LDS which resets and restarts the
master timer 546. Then, upon receipt of a clock pulse from the
master timer 546 via lead CL, the digit decoder-encoder 510 applies
a low pulse to lead LDP, a high pulse to lead LDP, and brings lead
LD low. The low pulse on lead LDP causes the timer reset and power
down logic 536 to generate a high pulse on lead TR to the master
timer 546 resetting the master timer after which the master timer
commences operating (when lead TR again goes low). The low pulse on
lead LDP also "loads" a ringing logic circuit 508, i.e., sets a
"ringing" flip-flop therein, causing the ringing logic circuit to
apply a high signal to the "ring gate" lead, a low signal to lead
RFF, and a high signal to lead RFF. The high signal on the "ring
gate" lead, as mentioned earlier in connection with FIG. 1, causes
the amplifier 146 (FIG. 1) to increase its gain and thereby amplify
the ringing signals to be received from the base terminal. The low
signal on lead RFF causes a speaker mute circuit 516 to apply a
signal to the muting circuit 118 (FIG. 1) via the "speaker mute"
lead to enable the muting circuit to pass signals from the receiver
110 to the amplifier 146 of FIG. 1. Other functions of the speaker
mute circuit 516 will be discussed in conjunction with FIG. 18. The
high signal on lead RFF arms a no-answer logic circuit 506 to
respond to certain conditions as will be described later. The high
signal on lead RFF also arms an off-hook detector circuit 548 to
generate a low signal on its output lead HKP when a hook switch 550
is placed in the "off hook" position as will be discussed
later.
As indicated earlier, after receipt of the last digit of the called
number, the digit decoder-encoder 510 applies a high pulse to lead
LDP. This causes the C.S.O. lock circuit 512 to apply a low signal
vai lead CSL to the channel search oscillator 520 thereby
preventing the channel search oscillator from operating during the
remainder of the call. The C.S.O. lock circuit 512 also in response
to the high pulse on lead LDP, applies a high signal to an earphone
mute circuit 518 causing the circuit to apply a signal via the "ear
mute" lead to the muting circuit 118 enabling the muting circuit to
pass signals from the receiver 110 to the earphone of telephone
handset 122 of FIG. 1. Before describing the final operation
resulting from the momentary high pulse on lead LDP, the operations
resulting from the low signal on lead LD will be mentioned.
The low signal on lead LD is applied to the tone input logic
circuit 570 to prevent the circuit from applying any signals to its
output leads. The low signal on lead LD also prevents certain
circuitry in the timer reset and power down logic 536 from
interferring with the operation of the master timer 546.
The final operation initiated by the high pulse on lead LDP is to
"load" an acknowledge memory circuit 514. This causes the
acknowledge memory 514 to apply low signals to leads AK and ACK,
the latter of which causes the guard output circuit 524 to apply a
low signal via lead GX to the tone generator 134 and to a
transmitter turn-on logic circuit 540. The transmitter turn-on
logic 540 then applies a signal via the XMIT lead to the FM
transmitter 130 (FIG. 1) enabling or "turning on" the transmitter
to transmit. Simultaneously therewith, the tone generator 134 is
caused to generate the guard tone. Guard tone is thus transmitted
to the base terminal to acknowledge reception of the transmitted
subscriber unit number. The low signal applied to lead AK disables
the off-hook detector 548 from responding to an off-hook indication
from the hook switch 550 (hook switch in "off hook" position). This
enables the completion of the acknowledge signalling interval
without disruption from the hook switch 550.
Seven hundred and fifty milliseconds after the acknowledge memory
514 is loaded, the master timer 546 applies a signal via lead 750
to the acknowledge memory causing it to bring leads AK and ACK high
again and thereby causing the termination of transmission of the
guard tone. Upon termination of transmission of the guard tone, the
base terminal commences to transmit the ringing signal sequence to
the subscriber unit.
Recall that the no-answer logic circuit 506 was armed by a signal
received over lead RFF. If leads IL and SL are both high for a
predetermined period of time, indicating that the alternate idle
and seize tone sequence of the ringing signal is no longer being
received from the base terminal, and if lead HK2 remains high
indicating that the telephone handset has not been taken off the
switch hook (i.e., the subscriber unit user has not answered the
call), the no-answer logic circuit 506 applies a low signal to lead
NA turning off the demand power supply 142 and causing a general
resetting of the FIG. 5 control logic.
If the subscriber unit user removes the telephone handset from the
switch hook in response to the ringing signal, the hook switch 550
is placed in the "off hook" position in response to which the
off-hook detector circuit 548 (having been armed by the high signal
on lead RFF) applies a low pulse to the timer reset and power down
logic 536 via lead HKP causing it to reset and restart the master
timer. The off-hook detector circuit 548 also applies a low signal
to a connect memory circuit 532 via lead HKP thereby "loading" the
memory circuit and causing it to apply a low signal to lead CON.
Lead CFF is also brought low at this time simply to ensure that
lead DSCX is maintained low so that the disconnect sequence is not
inadvertently commenced. The low signal on CON causes the connect
output circuit 528 to signal the tone generator 134 and the
transmitter turn-on logic 540 to transmit connect tone to the base
terminal. 400 milliseconds after the commencement of the generation
of the connect tone, the master timer 546 signals the connect
memory 532 via lead 400 to bring the lead CON high again thereby
causing termination of transmission of the connect tone. The
connect memory 532, also in response to the signal received via
lead 400, applies a low "connect trailing edge" signal to lead CTE
turning off the demand power supply 142 and "loading" the
disconnect memory 522. Turning off the demand power supply results
in a low signal being applied to lead RS to reset, among other
things, the ringing flip-flop of the ringing logic circuit 508.
"Loading" the disconnect memory 522 causes lead DSC to be made high
and lead DSC to be made low. The high condition on lead DSC arms an
on-hook detector circuit 552 to bring PU low when the telephone
handset is placed on the switch hook following the conversation.
The high condition on lead DSC also enables a channel hold
generator 542 to generate channel hold signals a certain period
after XON goes high indicating no transmission from the subscriber
is occurring. These channel hold signals cause bursts of carrier
frequency to be transmitted to the base terminal so that the base
terminal will not take down the connection. The high condition on
lead DSC also arms the on-hook detector 552 for purposes to be
mentioned later. The low condition on DSC prevents the controlled
reset logic 544 from generating a low signal on lead CRS. "Loading"
the disconnect memory 522 further causes a low signal to be applied
to lead LDS.CL and this signal prepares the digit decoder-encoder
510 to maintain LD low when the demand power supply 142 is turned
on again. This is necessary since, when the demand power supply is
turned on again after completion of the conversation and
replacement of the telephone handset on hook, the lead LD would
otherwise be made high in response to the digit decoder-encoder 510
receiving the momentary low signal via RS lead. Maintaining LD low
prevents the tone input logic circuit 570 from applying signals to
its output leads.
Removal of the telephone handset from the switch hook also causes
the off-hook detector 548 to apply a low signal to lead HK3 a
predetermined period of time after removal of the handset and to
apply a high signal to lead HK2. The low signal on lead HK3 enables
a transmitter turn on logic circuit 540 to generate a low signal on
lead XMIT if a push-to-talk switch 582 is depressed (closed to
ground). The push-to-talk switch 582, which was discussed earlier,
is located on the telephone handset for convenience. The high
signal on lead HK2 disables operation of the channel search
oscillator 520 as indicated earlier. Of course, at this stage of an
incoming call the channel search oscillator 520 is already
disabled. The feature of disabling the channel search oscillator
520 when the telephone handset is taken off hook is primarily
employed to prevent initiation of an outgoing call before an idle
channel has been located.
At the completion of the conversation, the subscriber unit user
places the handset on the switch hook causing the hook switch 550
to be placed in the "on hook" position. The off-hook detector
circuit 548 detects this condition and signals the on-hook detector
circuit 552 which, since the DSC lead is high (recall that the DSC
lead was made high when the disconnect memory 522 was loaded),
signals the demand power supply 142 via the PU lead thus turning on
the demand power supply. The demand power supply 142 then applies a
high signal to lead PUF causing the output control circuit 558 to
enable operation of the output circuits 524, 526, 528 and 530. The
demand power supply 142 also signals the reset logic circuit 538
causing it to apply a low pulse to lead RS. The controlled reset
logic circuit 544 which normally generates a low pulse on CRS when
the demand power supply 142 is turned on is prevented from doing so
by the low signal on lead DSC. Thus, the disconnect memory 522 is
not reset at this time. The low signal on lead RS causes the
resetting and inhibiting of the master timer 546 and causes the
disconnect memory 522 to bring lead DSCX high. The high signal on
lead DSCX causes the timer reset and power down logic 536 to start
the master timer 546 operating. The low signal on lead RS, in
conjunction with power being supplied to the logic circuitry of the
disconnect memory 522 by the demand power supply 142, also enables
the disconnect memory 522 to commence to alternately signal the
disconnect output 526 and the guard output 524 in response to
signals received from the master timer 546 via lead 25. This causes
generation of the disconnect signal sequence which consists of
alternate disconnect and guard tones each of duration 25
milliseconds. The disconnect signal sequence continues for a period
of 750 milliseconds after which the disconnect memory 522 in
response to a signal from the master timer 546 via lead 750
generates a high signal on the DSC lead and a low "disconnect
unload" pulse on the DUL lead, the latter causing the demand power
supply 142 to turn off and causing the controlled reset logic
circuit 544 to generate a low pulse on CRS and the reset logic
circuit 538 to generate a low signal on lead RS and a high pulse on
lead RS. The low signal on lead CRS resets the C.S.O. lock circuit
512 causing it to place a high condition on lead CSL and thus
allowing the channel search oscillator 520 to commence generating
channel search pulses on lead CSO so that the subscriber unit
commences searching for an idle channel.
A novel feature of the present embodiment is the provision for
resetting and restarting the master timer 546 during the initial
contact signalling interval (interval B of FIG. 2) of an incoming
call. The master timer is reset and restarted upon receipt by the
subscriber unit of an idle tone or seize tone burst from the base
terminal. Upon receipt of an idle tone or seize tone burst, signals
are applied to leads IL and SL respectively causing the tone input
logic 570 to produce relatively narrow pulses corresponding to the
leading edges of the idle tone and seize tone bursts. These "edge"
pulses are combined to produce a composite pulse train on lead TP
which is supplied to the timer reset and power down logic 536 to
cause same to supply a corresponding train of timer reset pulses
via lead TR to the master timer 546. This resets and restarts the
master timer 546 at the leading edge of each idle tone and seize
tone burst appearing at the output of the receiver 110. This
provision enables the utilization of a master timer 546 which is
less complex and more economical than would otherwise be required.
It also enables the control logic to tolerate variations in the
time durations of the idle tone and seize tone bursts.
OUTGOING CALL -- IMTS MODE
Assume that an idle channel has been located by the subscriber unit
and that the idle tone timer 534 has timed for the presence of idle
tone for the required 120 milliseconds and has thus "armed" the PU
lead. The idle tone timer 534 will also have applied an enabling
signal (high) by way of lead 535 to the off-hook detector circuit
548 enabling the off-hook detector to generate a low signal on lead
HKO when the telephone handset 122 of FIG. 1 is taken off the
switch hook. When the telephone handset is taken off the switch
hook to place a call, the hook switch 550 is placed in the "off
hook" position and the off-hook detector 548 is signalled
accordingly. In response thereto, the off-hook detector circuit 548
applies a low signal via lead HK2 to the idle tone timer 534
causing the idle tone timer to bring lead PU low thereby turning on
the demand power supply 142 and causing the demand power supply to
signal the reset logic 538 and the controlled reset logic 544 to
generate low signals on leads RS and CRS respectively for resetting
the FIG. 5 circuitry.
Also, in response to the hook switch 550 being placed in the "off
hook" position, the off-hook detector 548 applies a low signal to a
call base gating logic circuit 554 via lead HKO setting a pair of
flip-flops therein and thereby causing a high signal to be applied
to a "call base" or CB lead and a "dial request" or DR lead and a
low signal to be applied to lead CB. The low signal on lead CB and
the high signal on lead CB will persist until the completion of the
outgoing call if everything progresses in the normal manner. For an
incoming call, these signals are not generated since the low signal
on lead HKO is not produced for an incoming call because at the
time the handset is taken off hook no enabling signal will be
present on lead 535. The low signal on lead HKO also arms the call
base gating logic 554 to generate signals on output leads G, C and
IDR.
Placing the high condition on lead CB arms a call base dialing
logic circuit 562 to respond to a signal on lead LDS and dialing
pulses from a handset dial mechanism 574. The high signals on leads
CB and DR also cooperate to arm the timer reset and power down
logic 536 to respond to a signal on lead 425. The high signal on
lead DR further arms the logic 536 to respond to other clock
signals from the master timer 546. Lead DR remains high during
intervals K, L and M of an outgoing call (FIG. 3). Bringing lead CB
low inhibits the tone input logic circuit 570 from generating
output signals, arms the disconnect memory 522 to respond to a
signal on lead LDP from the digit decoder-encoder 510, inhibits the
acknowledge memory 514 from responding to such signal on lead LDP,
and causes the digit decoder-encoder 510 to inhibit for the present
the application of signals to lead NPP. The low signal on lead CB
also causes the timer reset and power down logic 536 to start the
master timer 546 operating. Upon arming the call base gating logic
554, a low signal is immediately generated on lead G and applied to
the guard output circuit 524. In response thereto, the guard output
circuit causes the tone generator and transmitter to generate and
transmit guard tone to the base terminal. The guard output circuit
524 also signals the transmitter turn-on logic 540 causing it to
mute the microphone of the telephone handset. The guard tone is
transmitted by the subscriber unit for 350 milliseconds after which
time the timer reset and power down logic 536 responds to a pulse
received via lead 350P from the master timer 546 (having been armed
by the high signal on lead DR) by "examining" lead IL to determine
if an idle tone is being received by the subscriber unit. If it is,
the timer reset and power down logic 536 does not apply a low
signal to lead PDA. If an idle tone is not being received, the
timer reset and power down logic 536 does apply a low signal to
lead PDA turning off the demand power supply and resetting the FIG.
5 control logic circuitry. Absence of the idle tone at this time
would indicate that another subscriber unit has "captured" the idle
channel for its own use.
After the 350 milliseconds of guard tone, the call base gating
logic 554 in response to a low signal on lead 350 and a high signal
on lead 350 from the master timer 546 brings lead G high and lead C
low respectively. This causes the guard output circuit 524 to
signal the tone generator to cease generating guard tone and causes
the connect output circuit 528 to signal the tone generator and the
transmitter turn-on logic 540 to cause the generation and
transmission of the connect tone. The microphone of the telephone
handset also continues to be muted by the transmitter turn-on logic
540. The connect tone is transmitted for a period of 50
milliseconds, i.e., the time during which the low signal is applied
to lead 350 and the high signal is applied to lead 350, after which
the guard tone is again transmitted.
Twenty-five milliseconds after the commencement of generation of
the guard tone again, a signal is applied by the master timer 546
to the timer reset and power down logic 536 via the lead 425
causing the timer reset and power down logic to "examine" the IL
lead to determine if the idle tone has been removed from the
channel. If the idle tone has not been removed, the timer reset and
power down logic 536 applies a low signal to lead PDA turning off
the demand power supply and causing the control logic unit
circuitry to reset. This result indicates that the subscruber unit
was unsuccessful in "capturing" the idle channel since the base
terminal did not remove the idle tone from the channel. If the idle
tone has been removed, then the timer reset and power down logic
536 takes no action to apply a signal to the lead PDA. The signal
applied to lead 425 also causes the timer reset and power down
logic 536 to bring lead TR high resetting and inhibiting the
operation of the master timer 546 and to arm a timer in the logic
536. If the base terminal does not send the seize tone within a
certain period of time, this timer causes a signal to be applied to
lead PDA turning off the demand power supply 142. If the seize tone
is received from the base terminal, the low signal applied to lead
SL inhibits the timer from causing the application of the signal to
lead PDA. Also, upon receipt of the seize tone, a high signal is
applied to lead SL causing a flip-flop in the call base gating
logic 554 to be set. In response thereto, the call base gating
logic brings lead IDR low causing the timer reset and power down
logic to maintain the master timer 546 in the reset and "inhibit"
condition until the seize tone is removed from the channel. After
the seize tone is removed from the channel (by the base terminal),
the timer reset and power down logic 536 allows the master timer
546 to commence operation. 175 milliseconds thereafter, the master
timer 546 applies a signal via lead 175 to the call base gating
logic 554 causing it to generate an "identification enable" signal
(low) on lead IDE to thus enable the call base ID logic 556. Lead
IDE remains low during interval N of an outgoing call (FIG. 3).
Enablement of the call base ID logic 556 will cause the logic to
alternately generate, in response to pulses received via lead CL, a
connect signal, a carrier only signal, a connect signal, a guard
signal, a connect signal, a carrier only signal, etc. over the
respective designated output leads. These signals serve to energize
the guard output circuit 524, the connect output circuit 528, and
the carrier only output circuit 530 to cause the generation of the
subscriber unit identification signal sequence such as illustrated
in interval N of FIG. 3. Upon the generation of each connect signal
by the call base ID logic 556, a low signal is applied to lead CP
and thus to the digit decoder-encoder 510 causing the digit
decoder-encoder to maintain a count of the number of connect
signals generated. The digit decoder-encoder 510 compares this
count (each time it is increased) with a "stored" count
representing a corresponding indentification digit of the
subscriber unit number. When the number of connect signals
generated corresponds to the numerical value of the corresponding
digit of the identification number, the digit decoder-encoder 510
applies a high "parity flip-flop" signal to lead PFF preventing
further input of pulses via lead CL to the call base ID logic 556
and thus preventing further generation of output signals on the
"connect" lead for a period of 175 milliseconds. After the 175
milliseconds period, a signal is applied via lead 175 to the digit
decoder-encoder 510 causing it to remove the high signal from lead
PFF thereby allowing the call base ID logic 556 to again receive
pulses ove the CL lead. The call base ID logic 556 then commences
to cause the generation of the next digit of the identification
number of the subscriber unit. The above-described operation is
then repeated.
After the last digit of the identification number has been
transmitted to the base terminal the digit decoder-encoder 510
generates a "last digit" signal on lead LD (low signal) to cause
the call base gating logic 544 to bring lead IDE high. This
disables the call base ID logic 556. At this same time, the digit
decoder-encoder 510 applies a signal via lead LDP to the disconnect
memory 522 thereby "loading" the memory. The operations resulting
from "loading" the disconnect memory were discussed earlier for an
incoming call and will not be discussed again here.
At the same time the disconnect memory is "loaded," the digit
decoder-encoder 510 brings lead LDS high and this enables the call
base dialing logic 562 to generate an output in response to signals
received from a handset dial mechanism 574. The subscriber unit
user then listens for dial tone from the base terminal and upon
receipt of same he may commence to dial the called number of the
handset dial mechanism 574. "Cocking" the dial mechanism 574 causes
closure of the switch labeled "cock" causing the call base dialing
logic 562 to apply a low signal to lead G, in turn, causing the
generation of guard tone. When the dial mechanism 574 is released,
the switch labeled "digit" alternately opens and closes causing the
call base dialing logic 562 to periodically interrupt the low
signal on lead G with a low pulse on lead C. The number times the
"digit" switch is opened corresponds to the numerical value of the
digit being dialed. The alternate low signals on leads G and C, in
turn, cause the generation and transmission to the base terminal of
alternate guard and connect tones representing the called number as
illustrated in interval P of FIG. 3. As each digit of the called
number is transmitted, the transmitter turn-on logic 540 applies a
low signal via lead TX to the timer reset and power down logic 536
resetting a so-called "dialing out timer" located therein. This
dialing out timer is controlled by lead DSC (which was made high
upon "loading" the disconnect memory 522) and lead HK2 from the
off-hook detector 548, as well as by lead TX. When HK2 is low
(telephone handset off hook) and lead DSC is high, the dialing out
timer is "activated" to time during any period in which lead TX is
high, i.e., when no tone signals are being transmitted to the base
terminal so that leads GX (from the guard output circuit 524), DX
(from the disconnect output circuit 526), CX (from the connect
output circuit 528), and COX (from the carrier only output circuit
530) are high. If the dialing out timer times for approximately 10
seconds after the transmission of a digit of the called number,
e.g., such as the last digit of the called number, the timer reset
and power down logic 536 causes a signal to be applied to lead PD
turning off the demand power supply 142. A low signal would also be
generated on lead PD if dialing were never commenced.
If the called party answers, the conversation may commence. Channel
hold signals are generated by the channel hold generator 542 during
the course of the conversation under the same circumstances as for
an incoming call.
When conversation is concluded and the subscriber unit user places
the telephone handset on the switch hook, the disconnect operation
as previously described for an incoming call is carried out.
MTS MODE
For operation in the MTS mode, the mode switch 578 is placed in the
closed or "manual" position. This causes a mode control circuit 560
to apply a high signal to lead MA and a low signal to lead MA. The
high condition on lead MA causes the tone input logic circuit 570
to generate a low pulse on lead ILP and lead TP for each low signal
received over either the lead IL or the SL. Thus, for each
transition from a seize tone to an idle tone or from an idle tone
to a seize tone, a low pulse is generated on leads ILP and TP. The
digit decoder-encoder 510 counts the pulses recived via the ILP
lead, and thus counts the transitions from seize tone to idle tone
and vice-versa, which is necessary in the MTS mode since each
transition, during the interval in which a subscriber unit number
is being received, represents one bit of a digit of the number.
(Recall that in the IMTS mode only transitions from seize to idle
tones represented a bit.) The digit decoder--encoder 510 compares
each group of counts representing a digit of the received number
with a corresponding digit of the subscriber unit's phone number.
If, after comparison of all digits, the received number matches the
subscriber unit phone number, then the digit decoder-encoder 510
immediately energizes the ringing logic circuit 508 to, in turn,
enable ringing signals received from the base terminal to actuate
the speaker 150 of the subscriber unit (See FIG. 1).
Each low pulse applied to lead TP causes the timer reset and power
down logic 536 to reset and restart the master timer 546.
The high signal on lead MA, in addition to being supplied to the
tone input logic circuit 570, is also applied to the digit
decoder-encoder 510 causing the decoder-encoder to change modes of
operation so that the received called number digits will be
compared with the appropriate "stored" digits of the subscriber
unit number. In the MTS mode of operation, the called numbers
consists of only five digits rather than seven digits as in the
IMTS mode. Thus, when operating in the IMTS mode, the digits
received will be compared with certain digits of the "stored"
subscriber unit number whereas, when operating in the MTS mode, the
digits received will be compared with certain other digits of the
"stored" subscriber unit number. This will be explained in greater
detail when describing the FIG. 10 digit decoder-encoder.
The low signal on lead MA is applied to the channel search
oscillator 520 to prevent the oscillator from generating "channel
search" pulses. Channel searching in the MTS mode is carried out
manually, as already mentioned, and when an idle channel is found,
the push-to-talk switch 582 is depressed to cause the transmission
of carrier frequency to the base terminal to notify the base
terminal that the subscriber unit user wishes to make a call.
The low signal on lead MA is also applied to the speaker mute
circuit 516 enabling it to generate a high signal on the "speaker
mute" lead to "unmute" the speaker provided the subscruber unit is
not transmitting (TX and XMIT high) and the "speaker off switch"
515 is in the "ON" position. The low signal on lead MA is further
applied to the earphone mute circuit 518 causing it to generate
enabling signals to "unmute" the earphone of the telephone handset
122.
Finally, the mode control circuit 560 also signals the output
control circuit 558 to apply a signal via lead OC to the guard
output circuit 524, the disconnect output circuit 526, the connect
output circuit 528 and the carrier only output circuit 530 to
prevent such circuitry from enabling the generation of any tones
during the operation of the subscriber unit in the MTS mode.
For a base terminal to subscriber unit call in the manual mode, the
demand power supply is turned on and off in much the same manner as
for the automatic mode although a number of circuits in the
subscriber unit are disabled as indicated above. However, for a
subscriber unit to base terminal call in manual mode, the demand
power supply is never turned on. This is because no idle tone
signal (or equivalent) is received by the idle tone timer and hence
the idle tone timer never produces a power up signal on lead PU to
turn on the demand power supply.
DESCRIPTION OF FIG. 6 -- IDLE TONE TIMER, OFF HOOK DETECTOR,
ON-HOOK DETECTOR AND HOOK SWITCH
As noted earlier, the demand power supply 142 illustratively
supplies power to all components of FIG. 6 (and FIGS. 7-18) except
those connected directly to one of the terminals +A, +B, +C and -D
and those designated by an asterisk. The FIG. 6 circuitry will not
be described.
The principal function of the idle tone timer 534 of FIG. 6 is to
turn on the demand power supply in preparation for an incoming or
outgoing call. The idle tone timer generates a low signal on lead
PU to turn on the demand power supply upon receipt of either a
seize tone signal (SL) or an off-hook signal (HK2) following a
period of 120 milliseconds of reception of idle tone.
Included in the idle tone timer are a number of NAND gates 602, 604
and 608, and a 120 milliseconds timing circuit 610 which includes a
transistor 616, a capacitor 620 and a NAND Schmitt trigger 612. The
timing circuit 610 is "off" when the output of the NAND gate 602 is
high. When this condition exists, a diode 603 is forward biased and
current flows from a power supply source +C through a resistor 605,
the diode 603 and diodes 607 and 609 to ground. The voltage drop
across diodes 607 and 609 turns on the transistor 616 which then
provides a path to ground to maintain the capacitor 620 in a
substantially discharged condition. The resulting low voltage level
across the capacitor 620 causes the NAND Schmitt trigger 612 to
produce a high output signal which is converted to a low signal by
an inverter 624. The low output of the inverter 624 causes the NAND
gate 608 to maintain lead PU high.
The idle tone timer generates a low signal on output lead PU in the
following manner. When leads IL and HK2 are both high (indicating
respectively that the idle tone) is being received and that the
telephone handset is on hook), the output of NAND gate 602 is low
reverse biasing the diode 603 preventing the flow of current
therethrough. This reduces the voltage at the base of the
transistor 616 thereby placing the transistor in a non-conducting
condition. With the transistor 616 in the non-conducting condition,
the capacitor 620 commences to charge via a resistor 615 from the
positive voltage source +C, If the high condition on leads IL and
HK2 continue for 120 milliseconds, the capacitor 620 reaches a
voltage sufficient to trigger the NAND Schmitt trigger 612 causing
it to generate a low output signal. The low signal is inverted by
the inverter 624 to a high signal and applied to NAND gate 608.
(Note that lead RS1 is high at this time.) Then, if the other input
lead to NAND gate 608 becomes high thereafter, a low signal will be
applied to lead PU. The other input lead to NAND gate 608 will be
made high if either input to NAND gate 604 is made low, i.e., if
either SL is made low (indicating that seize tone is being received
by the subscriber unit) or HK2 is made low (indicating that the
telephone handset has been taken off-hook). Of course, if either
lead IL or HK2 are made low before the end of the 120 millisecond
interval, then the transistor 616 will be caused to conduct and
discharge the capacitor 620 so that the NANA Schmitt trigger is not
triggered and no low signal is applied to lead PU.
The function of the off-hook detector circuit 548, as the name
implies, is to determine when the telephone handset has been
removed from its cradle or taken "off hook." As indicated above,
when the telephone handset is taken off hook so that hook switch
550 is placed in the "off hook" position, lead HK2 is made low.
With the hook switch 550 in the "off hook" position, a capacitor
632 of the off-hook detector 548 commences to charge via a resistor
634 from a positive voltage source +C. When the voltage across the
capacitor 632 reaches a certain level, and if lead AK from the
acknowledge memory 514 is high, a NAND Schmitt trigger 636 is
triggered bringing lead HK2 low. When lead HK2 is brought low, lead
HK2 is made high by operation of an inverter 638. A high output
from the inverter 638 together with a high output from inverter 624
of the idle tone timer 534 causes a NAND gate 640 to bring its
output low. This causes a capacitor 641 to discharge so that lead
HK0 is eventially brought low.
A further action of bringing lead HK2 low is to cause lead HK3 to
be brought low about one second thereafter. That is, when lead HK2
is brought low, the output of inverter 638 is high causing an
inverter 642 to produce a low output which, in turn, causes the
output of an inverter 644 to be made high and this latter output
commences to charge a capacitor 645. In the meantime, the high
output of inverter 638 is applied to input 654 of a NAND gate 652.
The high output of inverter 638 is also applied to an inverter 655
which inverts the high level to a low level. This low level is
delayed, however, in being applied to input 656 of the NAND gate
652 by a delay circuit including a resistor 658 and a capacitor
660. During the delay, NAND gate 652, since both of its inputs are
high, applies a low signal to NAND gate 648 causing it to apply a
high signal to lead HK3. After the delay, the low signal on input
656 of NAND gate 652 causes NAND gate 652 to apply a high signal to
NAND gate 648 which, together with a high signal on the other input
of NAND gate 648 (capacitor 645 having charged), causes NAND gate
648 to bring lead HK3 low.
Finally, in a manner which is obvious in view of the above
discussion and from an examination of FIG. 6, a momentary low pulse
is generated on lead HKP when lead HK2 is brought low.
The on-hook detector 552, whose function is apparent from its name,
applies a momentary low signal to lead PU in response to lead HK2
going high, lead HK2 going low and lead DSC being high. (Recall
that lead HK2 is high and lead HK2 low when the telephone handset
122 is on hook.) When the lead HK2 input to NAND gate 664 goes
high, the other input to the NAND gate 664 remains high momentarily
due to the delay of the low signal on lead HK2 by the resistor 668
and capacitor 666. NAND gate 664 thus applies a low signal pulse to
an inverter 670 which generates a high signal pulse which, in
conjunction with a high signal on lead DSC, causes a NAND gate 672
to bring lead PU momentarily low.
The functions of the various output signals generated by the idle
tone timer 534, off-hook detector 548 and on-hook detector 552 were
discussed earlier in conjunction with FIG. 5 and will not be
further discussed here.
DESCRIPTION OF FIG. 7 -- DEMAND POWER SUPPLY, RESET LOGIC AND
CONTROLLED RESET LOGIC
Referring to FIG. 7, power is supplied to the demand power supply
142 from the battery operated power supply 138 (FIG. 1) by way of
the lead labeled "power in." The demand power supply, in turn,
supplies power to various component units of the control logic unit
126 by way of the lead labeled "power out." Control of the
application or transfer of power from the "power in" lead to the
"power out" lead is effected by way of input leads NA, PU, PD, CTE,
CSO, PDA and DUL. The demand power supply 142, together with the
reset logic 538 and controlled reset logic 544 of FIG. 7, will now
be described assuming that the battery operated power supply 138
has just been turned on to supply power to the control logic unit
126 and demand power supply 142 and that all input leads to the
demand power supply 142 are placed in their normally high
condition. Note that the reset logic 538 and controlled reset logic
544 receive their operating power directly from the battery
operated power supply 142.
When power is initially applied to the "power in" lead, a capacitor
722 is in the "discharge" condition so that the voltage level at
one input to a NAND Schmitt trigger 708 is low causing the output
thereof to be high and thus the output of an inverter 710 to be
low. With the output of inverter 710 low, the output of a NAND gate
714 is high to reverse bias a diode 716. Current applied to the
"power in" lead thus flows via a diode 718 to the base of a
transistor 702 creating a voltage which turns on the transistor.
Turning on transistor 702 lowers the voltage level at the base of a
transistor 704 turning on the transistor and thereby enabling the
application of power from the "power in" lead to the "power out"
lead. The low output of inverter 710 is also applied to a NAND gate
732 of the controlled reset logic 544 causing the NAND gate to
apply a high signal to an inverter 734 so that the inverter brings
output lead CRS low. Bringing lead CRS low causes lead RS to be
brought low and lead RS to be made high by operation of NAND gate
746 and inverter 748.
Following the initial application of power to the "power in" lead,
a capacitor 722 of the demand power supply commences to charge and
when it reaches a certain predetermined level (and since lead NA is
high), NAND Schmitt trigger 708 is triggered to apply a low signal
to the inverter 710. The inverter 710 thus generates a high signal
which, together with the high output on lead Q2 of a flip-flop 712
(which was reset by the previous low output from the inverter 710),
causes NAND gate 714 to apply a low signal to the diode 716. The
diode 716 is thus forward biased to divert current from diode 718,
reverse biasing diode 718 and causing the transistor 702 to turn
off and thus transistor 704 to turn off. The transfer of power from
the "power in" lead to the "power out" lead is thus inhibited,
i.e., the demand power supply 142 is turned off. In brief summary,
when power is initially supplied to the "power in" lead, the demand
power supply is momentarily turned on and leads CRS and RS are
brought low and lead RS is brought high to generally reset the
control logic unit 126 as discussed earlier.
An additional result of turning on the battery operated power
supply 142 is that the output of a NAND Schmitt trigger 742 of
reset logic 538 is made high (since a capacitor 721 of the demand
power supply 142 is in the "discharge" condition) causing an
inverter 744 to generate a low output signal. This brings lead RSX
low and, by operation of an inverter 747, lead RSl high. The high
condition on lead RSl enables the subsequent generation of a low
signal on PU by the idle tone timer 534 and a low signal on lead
HK0 by the off-hook detector 548 (FIG. 5).
Now assume that power is being supplied to the "power in" lead of
the demand power supply 142 but that the demand power supply is
turned off. Under these conditions, the capacitor 722 is charged so
that the NAND Schmitt 708 produces a low output causing the
inverter 710 to produce a high output. Also, the flip-flop 712 is
in the reset condition so that output lead Q2 thereof is high and
thus the output of NAND gate 714 is low. To turn on the demand
power supply 142, a low signal is supplied to lead PU setting the
flip-flop 712 and thus causing a high signal to be generated on
output Q1 of the flip-flop. This brings one of the inputs to the
lower NAND gate of the flip-flop 712 high which, together with the
other two inputs being high, causes the output lead Q2 of the
flip-flop 712 to be brought low. NAND gate 714 thus generates a
high output which, as previously discussed, causes the transistor
704 to conduct, i.e., causes the demand power supply 142 to turn
on.
Setting the flip-flop 712 also causes a high signal to be applied
to lead PUF which enables the output control circuit 558 (FIG. 5)
to operate and which arms the channel search oscillator 520 (FIG.
5) to cease generating search pulses when a high signal is received
via the SL input thereto. A further result of setting the flip-flop
712 and of causing the NAND gate 714 to generate a high signal is
that an inverter 724 is caused to produce a low signal which
reverse biases a diode 726 to turn off a transistor 706. With the
transistor 706 turned off, a high signal is applied to the lead PUN
enabling the no-answer logic circuit 506 (FIG. 5) to operate.
When the demand power supply 142 is first turned on by applying a
low signal to PU, leads RS and RSl are maintained high and leads RS
and RSX are maintained low by operation of the NAND Schmitt trigger
742, the inverter 744, the NAND gate 746, and the inverters 747 and
748. Also, if input lead DSC to the controlled reset logic 544 is
high, then, since the output of the NAND Schmitt trigger 742 is
initially high, NAND gate 730 applies a low signal to NAND gate 732
which, in turn, applies a high signal to the inverter 734 causing
it to maintain lead CRS low. After turning on the demand power
supply 142, the capacitor 721 commences to charge and when it
reaches a certain voltage level, the NAND Schmitt trigger 742 is
triggered since the PU lead will now be high (after the momentary
low signal to turn on the demand power supply) causing a low signal
to be applied to the inverter 744 and the NAND gate 730. As is
evident, this results in leads RS, RSX and CRS being made high and
leads RS and RSi being made low. The low signal on lead RSl
inhibits the idle tone timer 534 and the off-hook detector 548 from
generating low signals on leads PU and HKO respectively. The
inadvertent generation of such low signals might otherwise disrupt
the operation of the control logic unit 126.
The demand power supply 142 is turned off when low signals are
applied to any one of the input leads PD, CTE, CSO, PDA, or DUL.
With any of these leads made low, a NAND gate 752 generates a high
signal which is applied to one input of a NAND gate 754. The other
input to the NAND gate 754 is also high if lead PU is high and if
the demand power supply 142 has been on a sufficient period so that
the capacitor 721 has reached a voltage sufficient to trigger the
NAND Schmitt trigger 742 so that lead RSX is high. With both inputs
to NAND gate 754 high, the output thereof is low and this resets
the flip-flop 712 causing the output Q2 of the flip-flop to be made
high. Since both inputs to the NAND gate 714 are high, the output
thereof is low and as a result (as already described) the demand
power supply 142 is turned off.
The demand power supply 142 is also turned off when lead NA from
the no answer logic 506 goes low (when the subscriber unit user
fails to answer a call). Specifically, the low signal on lead NA
causes the NAND Schmitt trigger 708 to produce a high output which,
in turn, causes the inverter to produce a low output. The low
output from the inverter resets the flip-flop 712 and also causes a
low signal to be produced on lead RS as already discussed. The low
signal on lead RS causes the no answer logic 506 to bring lead NA
high again resulting in the output of the inverter 710 again being
brought high. Since the output Q2 of the flip-flop 712 is high
(having been reset) and the output of the inverter 710 is high,
NAND gate 714 produces a low output which, as already discussed,
turns off the demand power supply.
When the demand power supply 142 is turned off, leads V and VI are
brought low to "lock" certain logic circuitry of the control logic
unit 126 in its then present condition. That is, when the flip-flop
712 is reset, output lead Q1 thereof is brought low causing a NAND
gate 758 to produce a high signal. This high signal causes
inverters 762 and 764 to produce low conditions on leads VI and V
respectively. Leads V and VI and also brought low when either lead
RSX is low or the output of the inverter 710 is low.
DESCRIPTION OF FIG. 8 -- MASTER TIMER
The master timer of FIG. 8 operates to generate signals or pulses
at various time intervals to control the operation of other
circuits of the control logic unit. The intervals at which the
pulses or signals are generated are indicated by the numerals
identifying these various output leads, except for lead CL on which
a pulse is generated every 25 milliseconds while the master timer
is operating.
The master timer of FIG. 8 includes a timer 802 which is enabled
when input lead TR is made low so that the output of an inverter
812 to a NAND gate 814 is high. The output input to the NAND gate
814 is also normally high causing the output of the NAND gate to be
made low forward biasing a diode 816 and thereby diverting the
voltage of a positive voltage source +B away from the base of a
transistor 818. This turns the transistor off causing a capacitor
817 to commence charging via a resistor 815 from a positive voltage
source +B. When the voltage across the capacitor 817 exceeds the
level of the voltage at the input 821 of a differential amplifier
820 (i.e., when the voltage level on lead 819 of the differential
amplifier 820 exceeds the voltage on lead 821 thereof) the
left-most transistor of the differential amplifier 820 turns on
bringing the output lead 822 of the differential amplifier low and
turning on a transistor 826. With transistor 826 turned on,
positive voltage is applied via the transistor 826 and resistor 839
to the base of a transistor 830 turning on the transistor and
thereby bringing lead CL low. Turning on the transistor 826 also
enables a positive voltage to be applied via resistor 837 and a
diode 833 to the base of the transistor 818 turning on the
transistor so that the capacitor 817 commences to discharge.
Bringing lead CL low causes NAND gate 814 to produce a high output
signal which back biases the diode 816 to enable application of
voltage from the voltage source +B to the base of the transistor
818. This further increases the conductivity of the transistor to
accelerate the discharge of the capacitor 817. With the transistor
830 turned on, a diode 828 is forward biased to allow a capacitor
827 to charge (one side through the base of the transistor 826 and
the other side through the diode 828 and the transistor 830). The
capacitor 827 is chosen so that it will charge very rapidly to turn
off transistor 826 which, in turn, turns off transistor 830 causing
lead CL to be brought high after being low only a very short time.
Backtracking momentarily, the high signal produced by NAND gate 814
in response to the low condition on lead CL is applied to one input
of a NAND gate 832 and to an inverter 823. Since the resulting low
signal produced by the inverter 823 is "delayed" from being applied
to the other input of the NAND gate 832 by a delay circuit
comprised of resistor 825 and capacitor 829, NAND gate 832 produces
a low output signal which causes NAND gate 814 to maintain its high
output for a short while after lead CL is brought high again. The
purpose of this is to ensure that the transistor 818 remains on
long enough to completely discharge the capacitor 817. When the low
output from the inverter 823 "reaches" the NAND gate 832, NAND gate
832 produces a high output signal which, together with the high
condition now on lead CL causes NAND gate 184 to generate a low
output forward biasing the diode 816 and turning off the transistor
818. This enables the capacitor 817 to commence charging again. The
above-described cycle is then repeated to successively generate low
pulses on lead CL. Lead PFF and the circuitry of the timer 802 to
which it is connects (including two diodes and a transistor 834) is
provided to increase the rate at which the timer 802 generates
clock pulses on lead CL. This is done only during the interdigit
periods in the identification interval O of FIG. 3 to meet
telephone company requirements. Thus, when a high signal is applied
to lead PFF, back biasing a diode 835, voltage is applied from a
voltage source +C via a resistor 836 and a diode 838 to the base of
the transistor 834 turning on the transistor. This lowers the
voltage level at the input 821 of the differential amplifier 820 so
that the differential amplifier generates a low signal on lead 822
at a sooner point in time after the capacitor 817 commences to
charge. A pulse on lead CL is thus generated at a point sooner in
time than it otherwise would be
Each pulse generated by the timer 802 is applied to the counter 804
which maintains a count of the pulses and generates output signals
when the count reaches certain values which are identified on the
output leads of the counter 804. Thus, a low signal is produced on
lead 100 after four pulses have been counted (each pulse
representing a 25 millisecond interval), a low signal is produced
on lead 200 after eight pulses have been counted, etc. The
circuitry of the counter 804 for maintaining the count is
well-known and the operation thereof is apparent from an
examination of FIG. 8.
The master timer of FIG. 8 and specifically the counter 804 is
reset each time lead TR is made high. Thus, when lead TR is made
high, an inverter 842 of the counter 804 applies a low signal to a
NAND gate 844 and to flip-flops 846 and 848 resetting the
flip-flops. The low signal applied to NAND gate 844 causes the NAND
gate to apply a high signal to a binary counter 850 for resetting
the counter. A low signal on lead RS also causes resetting of the
binary counter 815 by causing the NAND gate 844 to apply a high
signal to the binary counter 850.
The gating logic 806 of the master timer is provided to generate
output signals from various combinations of signals received from
the counter 804. The signals generated and the time at which such
signals are generated is indicated by the designations of the
output leads of the gating logic 806. The circuitry for generating
such output signals is standard circuitry and its operation is
apparent. Lead LD is provided to inhibit the generation of signals
on leads 175 and 200 whenever LD is made low.
DESCRIPTION OF FIG. 9 -- TONE INPUT LOGIC
The tone input logic circuit of FIG. 9 provides for applying pulses
to the timer reset and power down logic 536 (see FIG. 5) and to the
digit decoder-encoder 510 in response to idle and seize tones being
received by the subscriber unit. The tone input logic includes a
leading edge detector 902 which generates a low output pulse each
time lead IL is made low. Similarly, a leading edge detector 904
generates a low output pulse each time lead SL is made low. If
leads CB and LD are both high, each time either of the detectors
902 or 904 generate a low output pulse, a low pulse is produced on
lead TP which is connected to the timer reset and power down logic
536. A low pulse is also generated on lead ILP under these
conditions if, in addition, lead MA is high. Lead MA is high, of
course, when operating in the MTS mode and each transition from
idle tone to seize tone or from seize tone to idle tone is
considered a count or bit of the digits of a called number. When
lead MA is low, low pulses are generated on lead ILP in response to
low pulses from the detector 902 only. Thus, when in the IMTS mode,
transitions only from seize tone to idle tone are considered counts
or bits of the digits of a called number. Producing a low signal on
either leads CB or LD inhibits the generation of low pulses on
output leads TP and ILP.
DESCRIPTION OF FIG. 10 -- DIGIT DECODER-ENCODER
One of the principal functions of the digit decoder-encoder of FIG.
10 is to compare received called number digits with the digits of
the "stored" subscriber unit ID or phone number and to generate
output signals indicating the results of such comparison. The
decoder-encoder provides for making the proper comparisons when
operating in either the IMTS mode or the MTS mode. As previously
indicated, seven digits are utilized in the subscriber unit number
in the IMTS system whereas only five digits are utilized in the MTS
system. Specifically, each subscriber unit is assigned a telephone
company area code (three digits), office code (three digits) and
station code (four digits). In an IMTS system, the area code plus
station code is used to identify the subscriber units whereas in an
MTS system, the last digit of the office code plus the station code
is used to identify the subscriber units. In order for the
subscriber unit of the present invention to be utilized with either
an IMTS system or an MTS system, provision is made in the digit
decoder-encoder of FIG. 10 so that either seven digits (if in the
IMTS mode) or five digits (if in the MTS mode) of the "stored"
subscriber unit ID number may be compared with a phone number
transmitted from a base terminal. This provision will be explained
later.
Assume that the base terminal is transmitting a called number to
the subscriber unit of which the digit decoder-encoder of FIG. 10
is a part. Low pulses representing the received digits are applied
to lead ILP and thus to a NAND gate 1002 in response to which the
NAND gate 1002 applies a high pulse to a binary counter 1004. The
binary counter 1004 counts the pulses representing each received
digit and applies the binary-coded-decimal equivalent of the count
to a binary comparator 1008. At the beginning of the comparison
process, a binary counter 1020 applies a first set of signals to an
automatic mode decoder 1014 and a manual mode decoder 1018. If lead
MA is low, indicating that the subscriber unit is operating in the
IMTS mode, the automatic mode decoder 1014 is enabled to operate.
Alternatively, if lead MA is high, indicating the subscriber unit
is operating in the MTS mode, an inverter 1016 supplies a low
signal to enable the manual mode decoder 1018. The enabled decoder
(1014 or 1018) responds to the first set of signals from the binary
counter 1020 by applying a signal to one of its output leads
indicating that the first digit of the "stored" ID number is to be
compared with the first digit of the transmitted number. Thus, if
the automatic mode decoder 1014 is enabled, a signal is applied to
output lead 1 which corresponds to the first digit of the area code
of the ID number. If the manual mode decoder 1018 is enabled, it
applies a signal to its output lead 4 corresponding to the last
digit of the office code of the ID number. This output signal from
one of the decoders 1014 or 1018 is applied to a patch board
1012.
The patch board 1012 is utilized to "code" the subscriber unit ID
number. That is, certain inputs of a decimal-to-binary converter
1010 are interconnected with certain outputs of the automatic mode
decoder 1014 and the manual mode decoder 1018. A signal applied to
one of the input leads of the decimal-to-binary converter 1010
causes the converter to generate the BCD equivalent of the digit
represented by the particular input lead over which the signal was
received. Each input lead of the converter 1010 represent a
different one of the digits 1 through 9 with the zero digit being
represented by the absence of an input to the converter 1010. For
the illustrative interconnection of the patchboard 1012 of FIG. 10,
a signal applied to output lead 1 of the automatic mode decoder
1014 would cause the converter 1010 to generate the BCD equivalent
of 2. A signal on the output lead 4 of the manual mode decoder 1018
would cause the converter 1010 to generate the BCD equivalent of 1,
etc.
The binary comparator 1008 compares the information received from
the binary counter 1004 with that received from the converter 1010
and applies a high signal to its output if a match occurs and a low
signal to its output if a mismatch occurs. Following the receipt of
each digit of a transmitted number, a high signal is applied to
lead 175 of a parity detector 1030 and this signal, together with
the high signal on lead CB (high for an incoming call), causes a
NAND gate 1032 to generate a low output signal. The low signal
generated by NAND gate 1032 is applied to a NAND gate 1034 causing
the NAND gate to apply a high signal to a NAND gate 1036. If the
output of the binary comparator 1008 is high (indicating a match),
the NAND gate 1036 generates a low signal which sets a flip-flop
1038. Setting the flip-flop 1038 will prevent the generation of a
low signal on lead NPP (which would indicate a mismatch) when a
high signal is subsequently received over lead 200. In addition,
the generation of a low signal on lead PP (indicating a match) will
be allowed upon receipt of the high signal on lead 200. When the
low signal on lead PP is generated, it causes a one shot circuit
1040 to apply a signal to lead PPS which steps the binary counter
1020 causing it to apply a new set of signals to its output. This
new set of signals, in turn, causes the automatic mode decoder 1014
or the manual mode decoder 1018, depending on which is enabled, to
apply a signal to a different one of its output leads. After each
digit of a transmitted number is received, the binary counter 1020
is caused to increase its count and thereby signal the appropriate
one of the decoders 1014 or 1018 to apply a signal to a different
one of its output leads, in effect, causing successive "read-out"
of the "stored" ID number.
The low signal on lead PP also causes the resetting of flip-flop
1038 and the binary counter 1004 (via a NAND gate 1022) in
preparation for comparing the next pair of digits.
If, upon comparison of a pair of digits, a mismatch occurs, NAND
gate 1036 is caused to apply a high signal to flip-flop 1038 which
does not change the condition of the flip-flop. Thus, upon the
subsequent receipt of a high signal on lead 200, a low signal is
generated on lead NPP. The low signal on lead NPP, of course,
causes the subscriber unit circuitry to reset.
After the receipt of the last digit of a transmitted number, the
manual mode decoder 1018 or the automatic mode decoder 1014 applies
a signal to a last digit detector 1050 causing the detector to
generate a low pulse on lead LDP, a high pulse on lead LDP and a
low signal on lead LD. The functions of such signals were described
earlier.
Now assume that the subscriber unit is transmitting the unit ID
number so that lead CB is low and lead CB is high. Low pulses
representing the digits of the ID number are received via lead CP
from the call base ID logic 556 (FIG. 5). Each such pulse cause the
NAND gate 1002 to apply a high signal to the binary counter 1004
which then increases its counter by one and applies the BCD
equivalent of the count to the binary comparator 1008. In a manner
similar to that described for the operation of the digit
decoder-encoder for the receipt of digits, the decimal-to-binary
converter 1010 applies a BCD equivalent of the digit of the ID
number which is to be transmitted. In effect, this digit and the
count output of the binary counter 1004 are successively compared.
After each increase in the count of the binary counter 1004, a low
signal is applied to lead PE by the call base ID logic 556. This
causes NAND gate 1034 to apply a high signal to NAND gate 1036 so
that if a high signal is being generated on the output of the
binary comparator 1008 (indicating a match of the present count in
the binary counter 1004 with the output of the converter 1010),
NAND gate 1036 will generate a low signal to set flip-flop 1038.
The results of this will be discussed shortly.
As long as a mismatch occurs between the count and the converter
1010 output, transmission of ID digit pulses to the base terminal
are allowed. Specifically, flip-flop 1038 remains in the reset
condition so that a low signal is applied to lead PFF and this
enables the call base ID logic 556 to continue to cause the
transmission of pulse representing the ID digit.
When the binary counter 1004 reaches a count which matches the
output of the converter 1010, the binary comparator 1008 applies a
high signal to NAND gate 1036 causing the flip-flop 1038 to set
bringing lead PFF high, in turn, inhibiting the call base ID logic
556 from causing the generation of further ID pulses. Upon the
occurrence of the match, lead PS is also brought low causing the
timer reset and power down logic 536 (FIG. 5) to reset the master
timer 546. Thereafter, when the master timer 546 applies a high
signal to lead 175 of the parity detector 1030 of FIG. 10, a NAND
gate 1052 applies a low signal to lead PP resetting the flip-flop
1038 and also the binary counter 1004. With the flip-flop 1038
reset, lead PFF is made low enabling the call base ID logic 556 to
commence to cause the generation of further ID digit pulses. Just
as in the case of receiving transmitted digits, after the last pair
of digits is compared, the automatic mode decoder 1014 or the
manual mode decoder 1018 applies a signal to the last digit
detector 1050 causing it to generate output signals designated by
the identifying symbols on the output leads.
Leads RS and IDR are for resetting various circuits of the digit
decoder-encoder. Lead LDS.CL is for maintaining lead LD low after
the disconnect memory is "loaded" as previously discussed.
The digit decoder-encoder of FIG. 10 in the manner described above
provides a simple and economical means of enabling the subscriber
unit to operate in either the IMTS mode or the MTS mode, for
determining when the subscriber unit is being called, and for
controlling the transmission of ID digits to the base terminal.
DESCRIPTION OF FIG. 11 -- MEMORY CIRCUITS AND OUTPUT CIRCUITS
The acknowledge memory 514, disconnect memory 522 and connect
memory 532 shown in FIG. 11 are all utilized in the course of an
incoming call. The disconnect memory 522 is also used in the course
of an outgoing call. The guard output circuit 524, disconnect
output circuit 526, connect output circuit 528 and carrier only
output circuit 530 also shown in FIG. 11 are utilized to initiate
and control the generation and transmission of guard tone,
disconnect tone, connect tone and carrier frequency respectively in
response to signals from the acknowledge memory 514, disconnect
memory 522, connect memory 532 and leads G, C and CO. The output
control circuit 558 provides for inhibiting the above-mentioned
output circuits from causing the generation of the respective tones
or carrier frequency whenever any of the inputs to a NAND gate 1102
are low. The mode control circuit 560 is utilized for operating the
output control circuit 1102 and for generating signals on leads MA
and MA for causing the subscriber unit to operate in either the
IMTS or MTS mode. When the switch 578 is in the closed position,
voltage from a positive voltage source +C is diverted to ground so
that a low condition is placed on lead MA and a high condition on
lead MA. Alternatively, when the switch 578 is placed in the open
position, the voltage source +C places a high condition on lead MA
and a low condition on lead MA.
The acknowledge memory 514 causes the generation of guard tone by
applying a low signal to lead ACK upon the receipt of high signal
over lead LDP and CB (the latter indicating that the subscriber
unit is receiving an incoming call). Output lead AK of the
acknowledge memory 514 also goes low when lead ACK goes low since a
high signal is applied to the base of a transistor 1106 turning off
the transistor thereby bringing lead AK low. The connection of the
base electrode of the transistor 1106 via a resistor and diode to
the "power out" terminal of the demand power supply 142 is provided
to ensure the maintenance of lead AK high when the demand power
supply is turned off.
The connect memory 532 causes the generation of connect tone
(during interval E of FIG. 2) by bringing lead CON low upon the
setting of a flip-flop 1110 in response to a low pulse over lead
HKP. After 400 milliseconds, at which time lead 400 is made low,
the flip-flop 1110 is reset bringing lead CON high terminating the
generation of the connect tone and causing circuitry 1112 to
generate a low pulse on lead CTE.
The disconnect memory 522 causes generation of the disconnect tone
by bringing lead DSCX high. Lead DSCX is made high when a flip-flop
1116 is set in response to either a low signal on lead CTE or a
high signal on lead LDP (and assuming that lead V is high and lead
CP is low). With lead DSCX high and a NAND gate 1114 generating a
high output signal in response to lead 25 being low, the disconnect
output circuit 526 generates a low signal on lead DX.
To generate a disconnect signal sequence the input signal on lead
25 alternately goes high for 25 milliseconds, low for 25
milliseconds, etc. thereby alternately causing the generation of 25
milliseconds of guard tone and then 25 milliseconds of disconnect
tone, etc. for an interval of 750 milliseconds. When lead 25 is
high, NAND gate 1114 applies a low signal to NAND gate 1132 of the
guard output circuit 524 and NAND gate 1134 of the disconnect
output circuit 526. The resulting high output produced by NAND gate
1132 causes NAND gate 1136 to produce a low signal on lead GX which
will cause the generation of guard tone. The resulting high output
produced on lead DX by NAND gate 1134 will, of course, not result
in the generation of disconnect tone. When lead 25 is low, the
disconnect tone will be produced and the guard tone will not be
produced. After 750 milliseconds, lead 750 goes low resetting
flip-flop 1116 and thereby terminating the generation of alternate
disconnect and guard tones. Resetting the flip-flop 1116 also
results in a high signal being applied to lead DSC which, in turn,
causes circuitry 1122 to apply a low pulse to lead DUL. These
signals cause resetting of the subscriber unit logic enabling the
subscriber unit to commence searching for an idle channel. Note
that flip-flop 1120 is set in response to a high signal on lead LDP
to maintain lead DSCX in a low condition after receipt of the last
digit of a phone number transmitted from the base terminal and
until conversation commences, i.e., until lead RS is made low
causing resetting of the flip-flop 1120.
DESCRIPTION OF FIG. 12 -- TRANSMITTER TURN-ON LOGIC AND CHANNEL
HOLD GENERATOR
The transmitter turn-on logic 540 is utilized for controlling the
generation of carrier frequency and for generating certain other
signals when such transmission is taking place. The transmitter
turn-on logic 540 causes the generation of carrier frequency by
bringing lead XMIT low in response to a low signal on either lead
GX, DX, CX, or COX or a low on lead HK3 together with the talk
switch 582 being closed. When a low signal appears on any of the
first four mentioned leads, a NAND gate 1202 generates a high
signal back biasing a diode 1204 enabling voltage from a positive
voltage source +C to be applied via a resistor 1205 and diode 1206
to the base of a transistor 1208. This turns the transistor on
bringing lead XMIT low. If lead HK3 is low and switch 582 is
closed, the resulting high signals from inverters 1210 and 1212
respectively forward bias a diode 1214 again turning on the
transistor 1208 bringing lead XMIT low.
A low signal is also generated on lead TX whenever NAND gate 1202
generates a high signal. This signal is for resetting the "dialing
out timer" of the timer reset and power down logic 536. In
addition, when NAND gate 1202 generates a high signal, voltage from
the positive voltage source +C is applied via a resistor 1217 and
diode 1218 to a transistor 1220 turning on the transistor and
bringing the lead labeled "mike mute" low to mute the microphone in
the telephone handset 122 of FIG. 1. The speaker 150 of FIG. 1 is
similarly muted when lead XMIT is made low since a diode 1224 of
the transmitter turn-on logic 540 is forward biased to divert
voltage from a voltage source +C away from the base of a transistor
1228 causing the transistor to turn off resulting in a high
condition being placed on lead XON. The high signal on lead XON is
applied to the muting circuit 118 (FIG. 1) causing it to prevent
the application of signals from the FM receiver 110 to the
amplifier 146 and speaker 150. The high signal on lead XON also
inhibits the channel search oscillator 520 (FIG. 5) from generating
channel search pulses.
Recall that the channel hold generator 542 generates so-called hold
signals during lulls in transmitting frequency (lulls in
transmitting voice or tone signals) from the subscriber unit to the
base terminal to notify the base terminal that the connection is
not to be "taken down." When carrier frequency is being transmitted
from the subscriber unit to the base terminal, a low signal is
applied by the VOX circuit 234 to lead XMIT and thus to the
transmitter turn-on logic 540. As already described, this forward
biases the diode 1224 turning off transistor 1228 and bringing lead
XON high. The high signal on lead XON causes an inverter 1232 to
apply a low signal to the channel hold generator 542 and
specifically to NAND gate 1224. The low signal input to NAND gate
1242 causes the NAND gate to apply a high signal via a diode 1243
to the base of a transistor 1244 turning on the transistor to
maintain a capacitor 1246 discharged. With the capacitor 1246
discharged, the voltage at the base of a unijunction transistor
1248 is not sufficient to cause the transistor 1248 to fire so that
the emitter of a transistor 1250 is maintained low. The transistor
1250 is thereby maintained in the "ON" condition so that the lead
labeled "hold" is maintained low and no channel hold signals are
caused to be generated.
When carrier frequency is not being transmitted by the subscriber
unit, lead XMIT is high to back bias a diode 1224 and cause the
transistor 1228 to be turned on. This brings lead XON low and thus
lead XON high causing NAND gate 1242 to generate a low output
signal (since lead DSC is high at this time). The voltage level at
the base of the transistor 1244 is thus brought low turning the
transistor off and enabling the capacitor 1246 to commence
charging. When the voltage across the capacitor 1246 reaches the
trigger voltage of the unijunction transistor 1248, the unijunction
transistor fires (assumes a conducting condition) enabling the
capacitor 1246 to discharge through the unijunction transistor and
bring the emitter of the transistor 1250 high. With the emitter of
transistor 1250 made high, the transistor 1250 turns off so that
the voltage at the collector of the transistor is brought high and
thus the "hold" lead is made high. This signal on the "hold" lead
causes the VOX circuit 234 of FIG. 2 to enable the transmission of
a channel hold signal (a burst of carrier frequency) to the base
terminal.
Following triggering of the unijunction transistor 1248, the
unijunction transistor returns to a nonconducting condition and
transistor 1250 turns on again bringing the "hold" lead low. The
capacitor then commences to charge again until the voltage
thereacross again reaches the trigger level of the unijunction
transistor 1248 and the firing cycle described above is
repeated.
DESCRIPTION OF FIG. 13 -- RINGING LOGIC AND NO-ANSWER LOGIC
The ringing logic 508 of FIG. 13 operates to increase the gain of
the amplifier 146 (FIG. 1) when a ringing signal sequence is being
received from the base terminal as described earlier. This is
accomplished by the ringing logic 508 bringing the "ring gate" lead
high in response to a low signal on lead LDP. A low signal on lead
LDP sets a flip-flop 1310 causing a high signal to be applied to a
NAND gate 1314. This high signal, together with the high signal on
lead V causes the NAND gate 1314 to apply a low signal to an
inverter 1318, thus causing a high signal to be generated on the
"ring gate" lead.
In further response to a low signal being applied to lead LDP, a
high signal is generated on lead RFF and a low signal is generated
on lead RFF. The high signal on lead RFF, among other things, arms
the no-answer logic 506 to respond to a predetermined period of
absence of idle and seize tones. Thus, when RFF is high and when
both IL and SL are high (indicating neither idle nor seize tone are
being received), a NAND gate 1302 of the no answer logic 506 is
caused to apply a low signal to an inverter 1304 causing the
inverter to generate a high output. This high output commences to
charge a capacitor 1306. If the high signals on leads IL and SL
continue for the predetermined period of time, the capacitor 1306
reaches a level which will cause a NAND Schmitt trigger 1308 to
apply a low signal to lead NA (providing leads HK2, RSX and PUN are
all high at this time). NAND gate 1308 is prevented from applying a
low signal to lead NA if any of the leads HK2, RSX or PUN are low.
The low signal on NA turns off the demand power supply and causes
the control logic unit circuitry to reset.
DESCRIPTION OF FIG. 14 -- CALL BASE GATING LOGIC
The call base gating logic of FIG. 14, in conjunction with the call
base ID logic 556 (FIG. 5), controls the generation and
transmission of the tone signals utilized in the initial contact
and identification interval (FIG. 3) of an outgoing call. When the
telephone handset is taken off the switch hook, lead HKO is made
low setting flip-flops 1402 and 1404 of the call base gating logic.
Setting flip-flop 1402 causes the application of a low signal to
lead CB and a high signal to lead CB both of which are utilized to
prepare the control logic unit for making an outgoing call as
heretofore described. Setting flip-flop 1404 places a high
condition on lead DR and this arms two NAND gates 1408 and 1412.
The high condition on lead DR also arms the timer reset and power
down logic 536 (FIG. 5) to bring lead PDA low in case seize tone is
not received from the base terminal following the dial request
procedure. Application of the high signal to NAND gate 1408 causes
the NAND gate to bring lead G low (since lead 350 is high at this
time) thereby causing the generation and transmission of guard
tone. Generation of the guard tone continues for 350 milliseconds
until lead 350 is made low and lead 350 is made high. At this time,
NAND gate 1408 brings lead G high terminating the generation of
guard tone and NAND gate 1412 brings lead C low causing the
generation and transmission of connect tone. Connect tone is
generated for 50 milliseconds and until lead 350 is made high again
and lead 350 is made low at which time NAND gate 1408 brings lead G
low causing guard tone to again be generated and NAND gate 1412
brings lead C high terminating the generation of connect tone.
Upon receipt of seize tone from the base terminal, lead SL is made
high and, since lead CB is high due to flip-flop 1402 being set, a
NAND gate 1416 applies a low signal to a flip-flop 1420 setting the
flip-flop. Lead IDR is also made low at this time and this causes
the timer reset and power down logic 536 to reset and prevent the
master timer 546 (FIG. 5) from operating. Setting the flip-flop
1420 arms a flip-flop 1424 to respond to a high signal to be
subsequently received over lead 175. After the seize tone is
removed from the channel, NAND gate 1416 generates a high output so
that lead IDR is made high. The high signal on lead IDR causes the
timer reset and power down logic 536 to start the master timer 546
operating to ultimately generate a high signal on lead 175. Upon
receipt of the high signal over lead 175, flip-flop 1424 is set
causing a NAND gate 1428 to bring lead IDE low (since lead LD is
high until the last digit of the identification number is
transmitted on an outgoing call). Setting flip-flop 1424 causes the
resetting of flip-flop 1404 and the removal of the high condition
from lead DR. As a result, the NAND gate 1408 brings lead G high
and the generation of guard tone is terminated. Bringing lead IDE
low causes the call base ID logic 556 (FIG. 5) to initiate the
generation of tone signals for the identification interval (FIG.
4). After the identification interval, lead LD is made low causing
the NAND gate 1428 to bring lead IDE high.
DESCRIPTION OF FIG. 15 -- CALL BASE ID LOGIC
The call base ID logic of FIG. 5 controls the transmission of the
subscriber unit identification number to the base terminal. When
the telephone handset is removed from the switch hook in
preparation for making an outgoing call, the call base gating logic
554 (FIG. 5) applies a high signal to lead CB arming the call base
ID logic of FIG. 15. After the initial contact is made with the
base terminal, the call base gating logic 554 applies a low signal
to lead IDE to enable the call base ID logic of FIG. 15 to commence
generating the signals necessary to cause the transmission of
appropriate guard and connect tone bursts representing the
subscriber unit identification number. The low signal on lead IDE
causes an inverter 1502 to apply a high signal to a NAND gate 1504
so that upon the subsequent receipt of clock pulses from the master
timer 546 over lead CL, the NAND gate 1504 will apply low pulses to
its output lead ID.
Before the first of the low pulses is produced on lead ID,
flip-flops 1506 and 1508 of ID sequence logic 1510 are both in the
reset condition in response to a low signal having been received
via lead IDR from the call base gating logic 554 (so that output
leads Q of both the flip-flops are high and output leads Q of both
the flip-flops are low). When the call base ID logic is first
enabled by application of a low signal to lead IDE, an inverter
1512 applies a high signal to NAND gates 1514, 1516 and 1518. Since
flip-flop 1506 is applying a high signal to its output lead Q, NAND
gate 1514 applies a low signal to the output lead labeled "guard.".
This low signal is applied to the guard output circuitry 524 which
causes the generation and transmission of guard tone to the base
terminal.
Upon production of the first low pulse on lead ID (specifically the
trailing edge of the low pulse), flip-flop 1506 is caused to apply
a low signal to its output lead Q and a high signal to its output
lead Q. This results in the NAND gate 1514 applying a high signal
to the "guard" output lead and NAND gate 1516 applying a low signal
to the output lead labeled "connect." Generation and transmission
of the guard tone is thereby terminated and connect tone is
generated and transmitted to the base terminal. Upon application of
the next low pulse to lead ID, the flip-flop 1506 is triggered to
again apply a high signal to its output lead Q and a low signal to
its output lead Q. The high signal on output lead Q of the
flip-flop 1506 causes the flip-flop 1508 to apply a low signal to
its output lead Q and a high signal to its output lead Q. Since the
inputs to NAND gate 1518 are high, a low signal is applied the
output lead labeled "carrier only" and carrier frequency is thus
generated and transmitted to the base terminal. Upon application of
the next low pulse to lead ID, the flip-flop 1506 again changes the
conditions on both of its output leads bringing lead Q low and lead
Q high. With flip-flop 1506 output leads Q low and Q high, NAND
gate 1518 applies a high signal to its output and NAND gate 1516
applies a low signal to its output. Connect tone is thus again
generated and transmitted to the base terminal. With the next low
pulse on lead ID, the output signals on both flip-flops 1506 and
1508 are changed so that NAND gate 1514 again generates a low
output signal causing the generation and transmission of guard
tone. In the manner described, the call base ID logic causes the
generation of guard tone, connect tone, carrier only, connect tone,
guard tone, connect tone, etc. Note that flip-flop 1506 changes
condition with each low pulse (i.e., trailing edge) received over
lead ID and flip-flop 1508 changes condition with every other low
pulse received over lead ID.
After each connect tone signal is generated on the "connect" output
lead, a low pulse is applied via lead CP to the digit
decoder-encoder 510 providing the decoder-encoder with an
indication of the number of connect tone bursts generated. This is
accomplished by a flip-flop 1522 which responds to the initial low
pulse on lead ID by applying a high signal to NAND gate 1526 which,
together with the high signal applied to the other input of the
NAND gate 1526 (by way of an inverter 1530 from the ID lead)
results in a low pulse being applied to the lead CP. Upon the
application of the next low pulse to lead ID, the flip-flop 1522
applies a low signal to its output lead so that NAND gate 1526 is
inhibited from applying a low pulse to lead CP. Then, upon
application of the next low pulse to lead ID, the flip-flop 1522
brings its output lead high and NAND gate 1526 again applies a low
pulse to lead CP. Thus, with every other low pulse produced on lead
ID, a low pulse is similarly produced on lead CP and these latter
pulses are counted by the binary counter 1004 as already described
in connection with FIG. 10.
After each low pulse is produced on lead CP and lead ID returns to
a high condition, the inverter 1530 applies a low signal to a NAND
gate 1524 causing it to generate a high signal on its output lead.
This causes a capacitor 1526 to commence charging. When the voltage
across the capacitor 1526 reaches a certain level, NAND gate 1532
is caused to generate a low signal on lead PE (since lead CB is
high at this time). The low signal on lead PE enables the parity
detector 1030 of the digit decoder-encoder 510 to receive from the
binary comparator 1008 the results of comparing the count then
stored in the binary counter 1004 with the corresponding digit of
the subscriber unit's identification number. If the comparison
result indicates a match (in turn indicating that the correct
number of connect tone bursts have been transmitted), the parity
detector applies a high signal to lead PFF causing an inverter 1534
to apply a low signal to the NAND gate 1504 inhibiting further
application of low pulses to lead ID in response to clock pulses
received over lead CL. WIth the production of low pulses on lead ID
inhibited, the ID sequence logic 1510 remains in its then-present
condition. Depending upon which digit of the subscriber unit
identification number was represented by the previously transmitted
group of connect tones, the ID sequence logic 1510 will at this
time be applying a low signal to either the "guard" lead or the
"carrier only" lead. After a period of 175 milliseconds, the high
signal on lead PFF is removed by the digit decoder-encoder 510 and
the process of generating appropriate guard, connect and carrier
only signals representing the next digit in the subscriber unit
identification number is commenced.
Flip-flop 1536 is provided to prevent generation of a low signal on
lead PE during the 25 milliseconds preceding the arrival of the
first clock pulse over lead CL. This is necessary to prevent any
premature comparison results from being received by the parity
detector 1030. The flip-flop 1536 is reset whenever lead IDE is
made high (preceding and following generation of the subscriber
unit identification number) as a result of a low signal received
from the inverter 1502. When the flip-flop 1536 is reset, a high
signal is applied to an inverter 1538 causing it to bring its
output low. With the output of inverter 1538, low, capacitor 1528
is prevented from charging so that NAND gate 1532 maintains lead PE
in a high condition. Upon generation of the first pulse on lead CP,
flip-flop 1536 is set causing the inverter 1538 to bring its output
high and thereby enable the capacitor 1528 to charge in response to
a high output signal from NAND gate 1524.
After generation and transmission of the last digit of the
identification number, the digit decoder-encoder 510 signals the
call base gating logic 554 causing it to apply a high signal to
lead IDE disabling the call base ID logic from further
operation.
DESCRIPTION OF FIG. 16 -- CALL BASE DIALING LOGIC
The call base dialing logic of FIG. 16 simply provides for the
generation of alternate connect and guard tone signals representing
the called number. After the preliminary actions have taken place
in preparation for dialing the number, leads LDS and CB are in the
high condition. When the handset dial mechanism 574 is "cocked,"
the switch labeled "cock" is closed diverting to ground the voltage
from a positive voltage source +C and causing an inverter 1602 to
apply a high signal to a NAND gate 1604. Since the other inputs to
the NAND gate 1604 are also high, the NAND gate applies a low
signal to an inverter 1606 causing it to apply a high signal to
NAND gate 1608 and 1610. At this time, the switch labeled "digit"
of the handset dial mechanism 574 is also closed diverting voltage
from the voltage source +C to ground away from an inverter 1612.
The output of the inverter 1612 is thus high and this together with
the high output of the inverter 1606 causes the NAND gate 1610 to
apply a low signal to the "guard" output lead. When the handset
dial mechanism 574 is released, the switch labeled "digit" is
alternately opened and closed resulting in low signals being
generated on the "connect" lead and "guard" leads respectively.
Specifically, when the switch labeled "digit" is open, the voltage
from the voltage source +C to the NAND gate 1608 and to the
inverter 1612 causes the NAND gate 1608 to apply a low signal to
the "connect" lead and causes the inverter 1612 to apply a low
signal to the NAND gate 1610 which thus applies a high signal to
the "guard" lead. When the switch labeled "digit" is closed,
voltage is diverted from both the NAND gate 1608 and the inverter
1612 so that the NAND gate 1608 applies a high signal to the
"connect" lead and the NAND gate 1610 is caused to apply a low
signal to the "guard" lead. The call base dialing logic of FIG. 16
is disabled from generating connect or guard signals whenever a low
signal is applied to either lead LDS or CB.
DESCRIPTION OF FIG. 17 -- TIMER RESET AND POWER DOWN LOGIC
As the name indicates, the timer reset and power down logic of FIG.
17 provides for controlling the operation of the master timer 546
and the demand power supply 142. When the output lead TR of the
timer reset and power down logic is brought high, the master timer
546 is reset and inhibited from operation. When lead TR is brought
low, the master timer 546 is allowed to commence timing. Lead TR is
high when the outputs of both an inverter 1702 and a NAND gate 1704
are high and is low when either of the outputs of the inverter 1702
or the NAND gate 1704 are low. NAND gate 1704 produces a low output
when all inputs thereto are high. The upper input of NAND gate 1704
is high when lead TP is high, lead PPS is low, lead RS is high so
that flip-flop 1710 is applying a low signal to a NAND gate 1712 or
lead CB is low, lead LDP is high, lead HKP is high and lead VI is
high. When the condition on any of these leads changes, the upper
input lead of NAND gate 1704 becomes low and the output of the NAND
gate 1704 thus becomes high. The middle input to the NAND gate 1704
is high when lead IDR is high. Finally, the lower input lead to the
NAND gate 1704 is high when lead RS is low, lead PS is high, and
either lead CB is low or a flip-flop 1720 is in the reset state so
that it is applying a low signal to NAND gate 1722. Again, if
either the middle or lower input lead to NAND gate 1704 becomes
low, the output of the NAND gate becomes high.
Recall that one of the novel features mentioned for the present
embodiment is that the master timer 546 is reset and restarted with
each burst of idle or seize tone received during the initial
contact signalling interval of an incoming call (interval B of FIG.
2). That is, each time an idle or seize tone burst is received, a
low pulse is applied to lead TP causing NAND gate 1704 to apply a
high pulse to lead TR which resets and restarts the master timer
546.
Output leads PD and PDA are utilized, as described earlier, for
turning off the demand power supply 142 (FIG. 5). In addition, lead
PDA is utilized for signalling the controlled reset logic 544 (FIG.
5) to cause the generation of reset signals over leads CRS, RS and
RS, as also described earlier. A low signal is typically generated
on lead PD a predetermined period of time after transmission by the
subscriber unit of the last digit of a called number. Specifically,
referring to FIG. 17, after transmission of the last digit of a
called number, lead DSC will be high since the disconnect memory
522 (FIG. 5) will have been "loaded" following transmission of the
last digit of the subscriber unit identification number, lead HK2
will be low since the telephone handset will be off-hook pursuant
to the placing of the call, and lead TX will be high following
transmission of the last digit of the called number so that the
output of a NAND gate 1732 will be low. The low signal on the
output lead of the NAND gate 1732 forward biases a diode 1736 thus
diverting voltage from the voltage source +B away from the base of
a transistor 1734 to turn off the transistor. With the transistor
1734 turned off, a capacitor 1738 commences to charge and when the
voltage thereacross reaches a certain predetermined "firing
voltage," a unijunction transistor 1740 is caused to fire. The
capacitor 1738 is chosen to provide a predetermined delay before
the unijunction transistor 1740 is fired following generation of
the low signal by NAND gate 1732. When the unijunction transistor
1740 fires, a high signal is applied by the unijunction transistor
via a resistor 1744 to a NAND gate 1746. Since the other input to
the NAND gate 1746 from an inverter 1735 is high (since the output
of the NAND gate 1732 is low), the NAND gate 1746 applies a low
signal to lead PD to turn off the demand power supply.
The timing circuitry generally identified as block 1730 of FIG. 17
was referred to earlier as the "dialing out timer," when discussing
FIG. 5. As is clear from the above description of the timing
circuitry 1730, after transmission of any digit of a called number,
lead TX is made high causing the capacitor 1738 to commence
charging, i.e., causing the circuitry 1730 to commence timing. If
another digit of the called number is transmitted, a low signal is
applied to lead TX so that the output of NAND gate 1732 is high and
voltage from the voltage source +B is not diverted from the base of
the transistor 1734 so that the transistor is turned on. With the
transistor 1734 turned on, the capacitor 1738 discharges and the
timing circuitry 1730 ceases to time.
A low signal on lead PDA is generated under any of the following
circumstances: (1) if idle tone is not received by the subscriber
unit within a certain predetermined period of time following
receipt of seize tone in the "initial contact signalling" interval
of an incoming call (see FIG. 2), (2) if a telephone number
received from the base terminal fails to match the subscriber unit
number, (3) if any digit of a telephone number being transmitted
from the base terminal is not received within a certain period of
time following receipt of the previous digit of the number, (4) if
idle tone is not being received by the subscriber unit following
receipt of the initial burst of guard tone in the "initial contact"
interval of an outgoing call (see FIG. 3), (5) if idle tone has not
been removed from the channel after receipt of the initial burst of
guard tone and the burst of connect tone in the "initial contact"
interval of an outgoing call (FIG. 3), and (6) if seize tone is not
received within a certain period of time after the initiation of
the "initial contact" interval of an outgoing call. The circuitry
which causes the generation of the low signal on PDA under each of
the above-named conditions will now be described.
Referring to condition (1) above, upon initiation of the "initial
contact signalling" interval of an incoming call, the demand power
supply of the subscriber unit is turned on causing a low signal to
be applied to lead RS thereby setting flip-flop 1710 of FIG. 17.
Setting flip-flop 1710 causes output lead 1752 to be made low
forward biasing a diode 1754 and diverting voltage from a voltage
source +B away from the base of a transistor 1762. With the voltage
diverted away from the base of the transistor 1762, the transistor
turns off thereby enabling a capacitor 1764 to commence charging,
i.e., the path to ground for discharging the capacitor is
"removed." When the voltage across the capacitor 1764 reaches a
certain predetermined level, i.e., after a certain predetermined
period of time, the unijunction transistor 1740 is caused to fire
resulting in a high signal being applied by the unijunction
transistor via a resistor 1745 to a NAND gate 1747 thereby causing
the NAND gate to bring its output lead low. With the output lead of
NAND gate 1747 brought low, an inverter 1772 applies a high signal
to a NAND gate 1774 which, together with a high signal on the other
input of NAND gate 1774, causes the NAND gate 1774 to apply a low
signal to lead PDA. The capacitor 1764 is prevented from charging
to its predetermined voltage level if, within a certain
predetermined period of time following the setting of the flip-flop
1710, idle tone is received by the subscriber unit causing a low
signal to be generated on lead IL. The low signal on lead IL resets
the flip-flop 1710 causing lead 1752 to be made high reverse
biasing the diode 1754 and enabling voltage to be applied to the
base of the transistor 1762. This turns on the transistor 1762 so
that a path for discharging the capacitor 1764 is provided and the
capacitor is prevented from reaching the predetermined voltage
level.
When the second condition named above occurs, the digit
decoder-encoder applies a low pulse to lead NPP low causing the
inverter 1772 to apply a high pulse to the NAND gate 1774, in turn,
causing the NAND gate 1774 to apply a low pulse to lead PDA. Of
course, if all digits of a received telephone number match the
subscriber unit number, a low pulse is never applied to lead NPP by
the digit decoder-encoder and thus no low signal is generated on
lead PDA.
The circuitry for generating the low signal on lead PDA under
condition (3) above includes the flip-flop 1720 which is set via
lead PP each time a digit of a received telephone number matches
the corresponding digit of the subscriber unit number. When the
flip-flop 1720 is set, its output lead 1721 is brought low forward
biasing a diode 1758 and thus diverting voltage from the base of
the transistor 1762. The transistor 1762 is thus turned off so that
the capacitor 1764 may commence to charge. Of course, if the
capacitor 1764 is not prevented from reaching the predetermined
voltage level necessary to cause the unijunction transistor 1740 to
fire, then a low signal will be generated on lead PDA as previously
described. If, before the capacitor 1764 reaches this predetermined
voltage level, a high signal is received over lead PR from the
digit decoder-encoder 510 (FIG. 5), indicating that another digit
of a transmitted telephone number has been received, the flip-flop
1720 is reset causing the flip-flop output lead 1721 to be made
high reverse biasing the diode 1758 and enabling the application of
voltage to the base of the transistor 1762 to turn on the
transistor and discharge the capacitor 1764. Thus, as described, if
a digit of a telephone number is not received from the base
terminal within a predetermined period of time following receipt of
the previously transmitted digit, a low signal is generated on lead
PDA.
Note that the first three conditions named above all concern the
generation of a low signal on lead PDA during the course of an
incoming call. The remaining named conditions, on the other hand,
concern the generation of a low signal on lead PDA during the
course of an outgoing call as will now be described.
Under condition (4) above, lead DR from the call base gating logic
554 (FIG. 5) is high so that upon receipt of a high pulse on lead
350P and if lead IL is high indicating that idle tone is not being
received by the subscriber unit, a NAND gate 1776 generates a low
pulse on its output lead. The low output pulse of NAND gate 1776
causes the inverter 1772 to apply a high pulse to the NAND gate
1774 which, in turn, generates a low pulse on lead PDA.
A NAND gate 1778 is utilized to cause the generation of a low
signal on lead PDA under condition (5) above. That is, since a high
signal is still being applied to lead DR under condition (5), the
NAND gate 1778 generates a low output signal if, upon receipt of a
high signal over lead 425, lead IL is low indicating that idle tone
has not been removed from the channel. The low output signal from
NAND gate 1778, of course, causes generation of a low signal on
lead PDA as required.
The high signal on lead 425 also establishes the conditions under
which condition (6) above may occur. Specifically, the high signal
on lead 425 causes a NAND gate 1782 to apply a low signal to a
flip-flop 1784 setting the flip-flop. Setting flip-flop 1784 causes
the flip-flop output lead 1786 to be brought low forward biasing a
diode 1756 and thus diverting voltage from the base of the
transistor 1762. As with conditions (1) and (3), this causes the
transistor 1776 to turn off so that a low signal will be generated
on lead PDA after a predetermined interval unless, before the end
of that interval, the transistor 1762 is again turned on. If a
seize tone is received before the end of this interval, lead SL is
made low and this resets the flip-flop 1784 causing the flip-flop's
output lead 1786 to be brought high. This, of course, causes the
transistor 1776 to turn on and discharge the capacitor 1764.
Lead PPS is provided to inhibit the spurious generation of a low
signal on lead PDA when a match occurs between a digit of a
received telephone number and the corresponding digit of the
subscriber unit number. When such a match occurs, lead PPS is made
high so that an inverter 1773 brings its output low. This inhibits
NAND gate 1774 from bringing lead PDA low.
DESCRIPTION OF FIG. 18 -- CHANNEL SEARCH OSCILLATOR, CSO LOCK,
EARPHONE MUTE AND SPEAKER MUTE CIRCUITS
The CSO lock circuit 512 and the channel search oscillator 520 of
FIG. 18 control the channel searching operation of the subscriber
unit. The subscriber unit "searches" over the channels in response
to channel search pulses on output lead CSO. These pulses are
generated when leads HK2, XON and either SL or PUF are low and
leads IL, MA and CSL are high. Thus, if lead XON is low, an
inverter 1800 applies a high signal to a NAND gate 1804. If either
lead SL or PUF are low, then a NAND gate 1802 applies a high signal
to the NAND gate 1804. Then, since leads IL and CSL are high and
since input lead 1806 is normally high, the NAND gate 1804
generates a low output signal. This low output signal forward
biases a diode 1808 diverting voltage from a voltage source +C away
from the base of a transistor 1812 thereby turning off the
transistor. With the transistor 1812 turned off, a capacitor 1816
is allowed to commence charging (since the transistor 1812 no
longer provides a discharge path to ground). When the voltage
across the capacitor 1816 reaches a predetermined level, a
transistor 1820 is caused to conduct thereby bringing lead 1824
high which, together with the high conditions on the other two
input leads to a NAND Schmitt trigger 1828, causes the NAND Schmitt
trigger 1828 to generate a low pulse. Since leads HK2 and XON are
both low resulting in inverters 1834 and 1836 generating high
output signals, the low pulse from the NAND Schmitt trigger 1828
causes an inverter 1832 to generate a high pulse on lead CSO. The
high pulse on lead CSO also causes an inverter 1838 to generate a
low pulse on lead CSO. The low pulse produced by the NAND Schmitt
trigger 1828 also forward biases a diode 1842 so that a capacitor
1844 is discharged. With the discharge of the capacitor 1844, lead
1806 is brought low causing the NAND gate 1804 to generate a high
output signal. This high output signal reverse biases the diode
1808 enabling voltage from the voltage source +C to be applied to
the base of the transistor 1812 causing the transistor to turn on
and discharge the capacitor 1816. Since the low output pulse of the
NAND Schmitt trigger 1828 persists for only a short time, input
lead 1806 to the NAND gate 1804 is maintained low for only a short
time, the diode 1842 is forward biased for only a short time after
which it again assumes a reverse bias condition allowing the
capacitor 1842 to charge bringing lead 1806 high again. Withe lead
1806 high enough to enable the NAND gate 1804 to generate a low
output signal, the transistor 1812 is again turned off allowing the
capacitor 1816 to commence charging. The above-described sequence
is then repeated.
As is apparent from the examination of FIG. 18, if any of the leads
HK2, XON, or SL and PUF are made high or if any of the leads IL, MA
or CSL are made low, then the channel search oscillator 520 is
prevented from generating "channel search" pulses on lead CSO.
Thus, if either leads HK2 or XON are made high, then lead CSO is
maintained low by operation of inverters 1836 and 1834
respectively. Also, if any of the inputs to the NAND gate 1804 are
made low, i.e., if either lead IL or CSO are made low or lead XON
or lead SL and PUF are made high, then the NAND gate 1804 generates
a high output signal enabling the transistor 1812 to be turned on
to prevent the capacitor 1816 from charging. Finally, if lead MA is
made low, the NAND Schmitt trigger 1828 is prevented from
generating the low output pulse.
The CSO lock circuit 512 is provided to inhibit the operation of
the channel search oscillator 520 following receipt of the last
digit of a telephone number transmitted from the base terminal or
transmission of the last digit of the subscriber unit number. When
either such receipt or transmission occurs, a high pulse is applied
to lead LDP causing a NAND gate 1852 of the CSO lock circuit 512 to
apply a low pulse to a flip-flop 1854 thereby setting the
flip-flop. With the flip-flop 1854 set, a low signal is generated
by the flip-flop on lead CSL to inhibit the operation of the
channel search oscillator 520 as previously described. The
flip-flop 1854 is reset and thus the low signal on lead CSL is
removed upon receipt of a low pulse over lead CRS.
The earphone mute circuit 518 and speaker mute circuit 516, as
their names indicate, are for muting or inhibiting the operation of
the earphone of the telephone handset and the speaker respectively
at various times in the course of the operation of the subscriber
unit. The earphone of the handset is prevented from operating when
the lead labeled "ear mute" is high and is allowed to operate when
that lead is low. The "ear mute" lead is made low when either the
flip-flop 1854 is set or lead MA is low. Thus, the earphone is
allowed to operate following receipt of a high pulse over lead LDP
by the CSO lock circuit 512 or when the subscriber unit is
operating in the manual mode so that the MA is low. When the
flip-flop 1854 is set, an inverter 1860 applies a low signal to the
"ear mute" lead. When lead MA is low, a diode 1862 is forward
biased bringing the "ear mute" lead low.
The amplifier 146 and thus the speaker 150 (FIG. 10 are muted or
inhibited from operating when the "speaker mute" lead is low and
are allowed to operate when the "speaker mute" lead is high. The
"speaker mute" lead is low when the output of either NAND gate 1876
or NAND gate 1878 are low. The output of NAND gate 1876 is low when
all of the inputs thereto are high and similarly the output of NAND
gate 1878 is low when all the inputs thereto are high.
Specifically, a low signal is generated on the "speaker mute" lead
when (1) the subscriber unit is operating in the automatic mode
(lead MA is high), no ringing signals are being received from the
subscriber unit (lead RFF is high) and flip-flop 1854 is in the
reset state, or (2) no ringing signals are being received and
either a "speaker off switch" is closed to divert voltage from a
voltage source +C to ground, the subscriber unit is transmitting
(lead XMIT is low to divert voltage from the voltage source +C) or
lead TX is low. A high signal is generated on the "speaker mute"
lead to enable operation of the speaker when (1) ringing signals
are being received (lead RFF is low), or (2) the subscriber unit is
operating in the manual mode (lead MA is low) and the speaker off
switch 1872 is open, the leads XMIT and TX are both high, or (3)
the flip-flop 1854 is in the set state (so that lead CSL is low),
the speaker off switch 1872 is open and leads XMIT and TX are
high.
The function of the resistor 1873 and the capacitor 1875 of the
speaker mute circuit 516 is to filter out and prevent RF signal
components from affecting the operation of the NAND gate 1874.
DESCRIPTION OF FIG. 19 -- RADIO FREQUENCY SIGNAL GENERATOR
FIG. 19 shows the detailed construction of the radio frequency
signal generator 402 of FIG. 4. The FIG. 19 circuit includes an
adjustable oscillator circuit 1902 which is capable of generating a
radio frequency sine wave signal at any one of 11 different
frequencies. For the presently used telephone company mobile unit
transmit frequency set forth above (and bearing in mind that the
signal generated by the FIG. 19 circuitry is multiplied by a factor
of 18 to obtain the transmitted carrier), the lowest frequency to
be generated by the oscillator circuit 1902 is 8.765 megahertz and
the highest frequency is 8.782 megahertz, with the remaining nine
frequencies spaced therebetween and separated by a factor of
approximately 1.67 kilohertz. The oscillator circuit 1902 includes
a transistor 1910 and a set of eleven identical and individual
crystal circuits 1912-1922 which operate in a one-at-a-time manner
to provide the eleven different radio frequency signals. Only the
first two crystal circuits 1912 and 1913 and the last crystal
circuit 1922 are shown in detail. Other than the frequency of the
particular crystal used in each of these circuits, the circuits are
of identical construction.
The operative status of each of the crystal circuits 1912-1922 is
determined by the voltage condition on conductors 1923-1933
respectively. The voltage condition on these conductors is, in
turn, controlled by a stepping circuit 1906 and the settings of a
set of 11 selector switches 1934-1944. Each of the switches
1934-1944 includes a pair of fixed contacts labeled "S" (selected)
and "NS" (non-selected), one of which is contacted by the movable
element of the switch at any given instant. The "S" contacts of the
switches 1934-1944 are connected respectively to conductors
1923-1933. The "NS" contact of the switches is connected to a
common conductor 1946 which will be considered later. The movable
element of each of the switches is connected to the stepping
circuit 1906.
Assuming for the moment that each of the selector switches
1934-1944 is set to the "S" position, then stepping circuit 1906
operates to turn on or activate the crystal circuits 1912-1922 one
at a time in a sequential manner in response to a series of channel
search pulses applied to lead CSO. More particularly, each channel
search pulse supplied over lead CSO is applied by way of an
inverter 1950 to one input terminal of a one-shot multi vibrator
circuit 1951. Each negative-going pulse at this input causes the
multi vibrator 1951 to produce a negative-going pulse at its output
which is supplied to the counting input of a pulse counter 1952. In
the present embodiment, counter 1952 is a "count of 11" counter,
i.e., it counts from one to 11 and then repeats itself. Counter
1952 drives a four-line to 11-line decoder 1953, the 11 output
lines of which are each connected to a different one of the movable
elements of the selector switches 1934-1944. The output of the
counter 1952 is a four-bit parallel-type binary coded output and in
response thereto the decoder 1953 selects one of its output lines
to the exclusion of the other 10. The output circuits of the
decoder 1953 are constructed such that the selected output line is
placed at ground level voltage and the unselected output lines are
placed in an open circuit condition. The particular output line
selected, of course, depends on the condition of the four output
lines from counter 1952. By way of example only, if counter 1952
contains a count of one, then the decoder output lne connected to
the switch 1934 is selected (grounded) and the other 10 output
lines are unselected (open circuited), if counter 1952 contains a
count of two then the decoder output line connected to switch 1935
is selected (grounded) and the other ten lines are unselected (open
circuited), etc.
When a selector switch is set to its "S" position, the grounding of
the corresponding decoder output line activates the crystal circuit
to which the selector switch is connected to in effect connect the
crystal of that crystal circuit to the base of the transistor 1910.
Conversely, when a selector switch is set in its "NS" position or
when the corresponding decoder output line is in an open circuit
condition, the crystal circuit connected to that switch is disabled
so that in effect the crystal of that crystal circuit is
disconnected from the transistor 1910.
In order to illustrate the operation of selecting a particular
crystal circuit, it will be assumed that the crystal circuit 1912
is activated (control conductor 1923 grounded) and that the
remainder of the crystal circuits 1913-1922 are disabled (control
conductors open circuited). With the control conductor 1923
grounded, current flows from the +B power supply through resistor
1960, resistor 1961, choke coil 1962, diode 1963 and the choke coil
1964 to the control conductor 1923 and thus to ground. In this
mode, the diode 1963 is conductive thereby, in effect, connecting
the upper terminal of crystal 1965 by way of capacitor 1966 to the
base of the transistor 1910. This transforms the circuit associated
with the transistor 1910 into a crystal controlled oscillator
circuit with the resonant frequency thereof being determined by the
crystal 1965. Feedback by way of capacitor 1967 provides the energy
for keeping the crystal 1965 oscillating with oscillation of the
crystal 1965 initially being induced by the electrical noise in the
circuit.
The open circuit condition on control conductor 1924 of the second
crystal circuit 1913 causes the crystal 1968 thereof to, in effect,
be disconnected from the transistor 1910. Specifically, with the
lower end of the control conductor 1924 open circuited (caused by
the open circuit condition of the corresponding output lead of the
decoder 1953), current flows from the +B power supply through
resistor 1969, choke coil 1970, diode 1971, conductor 1972,
resistor 1961, choke coil 1962, diode 1963, choke coil 1964,
control conductor 1923 and switch 1934 to ground. Since the anode
of diode 1973 is at almost ground potential while the cathode is at
a positive potential somewhat less than the +B power supply
potential, the diode 1973 is nonconductive and the crystal 1968 is,
in effect, disconnected from the transistor 1910. At the same time,
the upper terminal of the crystal 1968 is effectively grounded from
an alternating current standpoint by way of diode 1971 (which is
conductive) and capacitor 1974. Choke coil 1962 presents a
relatively high alternating current impedance to further insure
that no oscillations from the crystal 1968 can reach the transistor
1910 by way of the circuit branch formed by such coil 1962 and
resistor 1961. The remainder of the crystal circuits 1914-1922 are
at this time also disconnected from the transistor 1910 in the same
manner as for the crytsal 1913. The other crystals are selected one
at a time by grounding their control conductors and placing an open
circuit on the remainder of the control conductors all under the
control of the decoder 1953.
The oscillating signals produced by the oscillator circuit 1902 are
supplied by way of a buffer stage 1904, an amplifier 1905 and a
filter 1907 to an output terminal 1909. Buffer stage 1904 includes
a field effect transistor 1976 arranged to provide a
source-follower type circuit. Filter 1907 is a band-pass type
filter for preventing passage of higher order harmonics of the
basic oscillator signal. The signal produced at the output terminal
1909, of course, constitutes the radio frequency output signal for
the signal generator of FIG. 19.
For the IMTS mode of operation, selector switches 1934-1944 can all
be set in the "S" position. In such case, the subscriber unit will
search through all eleven available telephone company channels
until it finds an idle channel. If desired, however, one or more of
the 11 possible channels may be excluded from this channel
searching operation by setting the appropriate ones of the selector
switches 1934-1944 to their "NS" positions. The crystal circuits
corresponding to the selector switches thus set to the "NS"
position will then be excluded (disabled) from the process of
sequentially switching from one crystal circuit to the next when
searching for an idle channel.
In the present embodiment, the channel search pulses received over
lead CSO may be spaced, for example, 100 milliseconds apart. Thus,
when searching for a new idle channel, the decoder 1953 swiatches
from one to the next of its output leads at 100 milliseconds
intervals. In the event that one or more of the crystal circuits
1912-1922 is placed in a non-selected condition so as to always be
excluded from the searching operation, then it is desirable that
the decoder 1953 not wait the entire 100 milliseconds period before
switching from one of its non-selected output leads to the next one
of its output leads which is in a selected condition. In other
words, it is desirable that the searching operation be shortened by
causing the decoder 1953 to rapidly skip over any one of its output
leads for which the corresponding one of the selector switches
1934-1944 is set in the "NS" position. This is accomplished by
means of a channel skip circuit 1980. Operation of the channel skip
circuit 1980 is determined by the selector switches 1934-1944 whose
"NS" contacts are connected via an inverter 1981 to a first input
of a NOR gate 1982. If all of the selector switches 1934-1944 are
in the "S" position, then the channel skip circuit 1980 remains
disabled and the binary counter 1952 functions in a normal manner
to advance the decoder 1953 one position each time a channel search
pulse is received.
Assume that one of the selector switches 1934-1944 is in the "NS"
position. So long as the output line of the decoder 1953
corresponding to that switch is in the ungrounded condition, the
input to the inverter 1981 is at the +C level (due to the +C power
supply) so that the output of the inverter 1981 is at a zero
voltage level. This output causes the NOR gate 1982 to generate a
high signal. The other input to the NOR gate 1982 is normally at a
high level except during the occurrence of a negative-going output
pulse at the output of the one-shot multi vibrator 1951. (The logic
of a NOR gate is that its output will be high if either input is
low.) With the output of the NOR gate 1982 high, the output of an
open collector type NAND gate 1983 is at zero or ground level. The
NAND gate 1983 is such that when its input is high, its output is
at ground level whereas when its input is low, its output is in an
open circuit condition. The ground level output of the NAND gate
1983 grounds a timing capacitor 1984 and maintains the same in a
discharged condition. This turns off a transistor 1985 which, in
turn, turns off transistor 1986. This places the input to an
inverter 1987 in a low condition causing its output to be high.
This high condition is fed back to the one-shot multi vibrator 1951
and the multi vibrator 1951 simply remains in its unpulsed
condition.
Now assume that in response to channel search pulses received over
lead CSO, the decoder 1953 grounds the output line corresponding to
the selector switch which is placed in its "NS" position. Since the
switch is in the "NS" position, it is desired that the decoder 1953
immediately step to the next position so as to ground the next
output line. This is accomplished as hereafter described. Grounding
the output line corresponding to the selector switch in the "NS"
position places the input to the inverter 1981 at ground level
causing the output thereof to become high. Since both inputs to the
NOR gate 1982 are high, the output thereof is low and this causes
the output of the NAND gate 1983 to assume an open circuit
condition. The capacitor 1984 is thus allowed to commence charging
by way of current flow through a resistor 1988. As the voltage
builds up across the capacitor 1984, a point is reached at which
the transistor 1985 is turned on and this, in turn, turns on the
transistor 1986. The input to the inverter 1987 is thus brought
high causing the inverter to generate a low output signal which
triggers the one-shot multi vibrator 1951. The negative-going pulse
produced by the one-shot multi vibrator 1951 is supplied to the
binary counter 1952 which causes the decoder 1953 to skip to the
next output line, i.e., causes the decoder 1953 to ground the next
output line following the one corresponding to the selector switch
in the "NS" position. The negative-going pulse at the output of the
one-shot multi vibrator 1951 is also supplied to the NOR gate 1982
causing the output thereof to return to the high level. This
returns the output of the NAND gate 1983 to the ground level to
discharge the capacitor 1984. If the selector switch connected to
the decoder 1953 output line most recently grounded is set in the
"S" position, then nothing further happens and the stepping circuit
1906 "waits" until the receipt of the next channel search pulse on
lead CSO. If, on the other hand, the selector switch connected to
the most recently grounded decoder output line is also in the "NS"
position, then the output of the inverter 1981 continues in the
high condition. Then, upon termination of the negative-going output
pulse from the one-shot multi vibrator 1951, the channel skip
circuit 1980 immediately returns to the condition where the output
of the NAND gate 1983 is "open circuited." This enables the
capacitor 1984 to begin charging again so as to repeat the
above-described cycle in which another negative-going output pulse
is produced at the output of the one-shot multi vibrator 1951.
Thus, as long as the input to the inverter 1981 remains grounded,
the channel skip circuit continues to operate and negative-going
pulses continue to be generated at the output of the one-shot multi
vibrator 1951. When the input to the inverter 1981 becomes
ungrounded, the production of the so-called channel-skip pulses
ceases and the stepping circuit "awaits" the arrival of the next
channel search pulse over lead CSO. In the MTS mode of operation,
the normal operating procedure is to place only one of the selector
switches 1934-1944 in the "S" position at a time and to place the
remainder of the selector switches in the "NS" position. When this
is done, the channel skip circuit 1980 automatically operates to
pulse the binary counter 1952 to a condition where the decoder 1953
provides a ground condition for the output line connected to the
selector switch in the "S" position. In effect, the search for an
idle channel is carried out by manually and on a one-at-a-time
basis placing the selector switches 1934-1944 in the "S"
position.
DESCRIPTION OF FIG. 20 -- VOX CIRCUIT
The VOX circuit, as discussed earlier in connection with FIG. 4,
provides for enabling a gated amplifier 418 (FIG. 4) in response to
audio signal received from the audio amplifier 426 or channel hold
signals received from the control logic unit 126 (FIG. 1). The VOX
circuit responds to the audio signals only when a switch 446 is in
the "VOX ON" position, but responds to the channel hold signal
regardless of the setting of the switch 446. The purpose of the VOX
circuit of FIG. 20 enabling the gated amplifier 418 is to enable
transmission of signals by the subscriber unit to the base
terminal.
Assume that neither audio nor channel hold signals are being
applied to the VOX circuit and that the switch 446 is in the "VOX
ON" position. Under these conditions, positive voltage is supplied
by the positive voltage source +B via resistor 2002, resistor 2003
and a potentiometer 2004 to the positive input terminal of an
operational amplifier 2012. As will be discussed later, positive
voltage is also supplied by way of a transistor 2024 and resistor
2023 under the conditions assumed. The signal applied to the
positive input terminal of the amplifier 2012 is referred to as the
reference signal. A lower level positive voltage signal is also
applied to the negative input terminal of the amplifier 2012 via a
resistor 2005 from the potentiometer 2004. When the voltage level
at the positive input terminal of the amplifier 2012 is higher than
the voltage level at the negative input terminal thereof, the
amplifier 2012 operates to produce a high level positive output
signal. Conversely, when the voltage level at the negative input
terminal of the amplifier 2012 is greater than the voltage level at
the positive input terminal thereof, the amplifier 2012 operates to
produce a zero level output signal. Thus, under the conditions
assumed above, the amplifier 2012 generates a high level positive
output signal which reverse biases a diode 2014. With the diode
2014 reverse biased and thus in a nonconductive state, a capacitor
2007 is allowed to charge with current supplied from the power
supply +B via a resistor 2008. The voltage across the charged
capacitor 2007 maintains a PNP-type transistor 2020 in the "OFF"
condition causing the collector of the transisor 2020 to be
maintained at a low voltage level. The low level voltage on the
collector of the transistor 2020, in turn, maintains a PNP-type
transistor 2040 in the "ON" condition and an NPN-type transistor
2028 in the "OFF" condition. As indicated earlier, when the
transistor 2024 is on, a reference voltage is supplied to the
positive input terminal of the amplifier 2012. When the transistor
2028 is in the "off" condition, the collector thereof is at a high
level so that the gated amplifier to which the collector is
connected is disabled.
Now assume that an audio signal is applied to input terminal 2000.
This signal is applied via a capacitor 2030, a resistor 2032 to a
diode 2034. The positive going portions of the audio signal forward
bias the diode 2034 and are thus transferred via the diode to the
negative input terminal of the amplifier 2012. If the amplitude of
the audio signal is greater than the reference voltage level at the
positive input terminal of the amplifier 2012, the amplifier
operates to place its output at the zero or ground voltage level.
This forward biases the diode 2014 discharging the capacitor 2007
and thereby bringing the level of the voltage at the base of the
transistor 2020 low. The transistor 2020 is thus turned on so that
its collector terminal is made high to turn off the transistor 2024
and turn on the transistor 2028. With the transistor 2028 turned
on, its collector terminal assumes a substantially ground voltage
level and this enables or activates the gated amplifier 418 of FIG.
4.
Turning off the transistor 2024 lowers the reference voltage level
at the positive input terminal of the amplifier 2012 to provide a
type of hysteresis effect in deactivating the VOX circuit. That is,
since the reference voltage at the positive input terminal of the
amplifier 2012 is higher when the VOX circuit is not active (i.e.,
is applying a high signal to the gated amplifier 418) than when the
VOX circuit is active, the audio signal level necessary to activate
the VOX circuit is higher than the audio signal level necessary to
maintain the VOX circuit in the active condition.
Operation of the VOX circuit of FIG. 20 in response to channel hold
signals applied to the terminal 2001 is essentially the same as
that for the application of audio signals to the terminal 2000
except that channel hold signals will activate the VOX circuit
regardless of the position of the switch 446. When the switch 446
is in the "VOX OFF" position, any audio signals applied to the
terminal 2000 are transferred via the capacitor 2030, the resistor
2032 and the switch 446 to ground. Thus, when the switch 446 is in
the "VOX OFF" position, the VOX circuit ignores audio signals.
However, since the channel hold signals applied to terminal 2001
are applied via a diode 2036 directly to the negative input
terminal of the amplifier 2012, the setting of the switch 446 in no
way affects the channel hold signals.
Transistor 2016 and its associated circuitry are provided for
preventing inadvertent activation of the VOX circuit when power
from the power supply +B is initially applied to the circuit. If
the transistor 2016 and its associated circuitry were not provided,
when power from the +B power supply were initially supplied to the
VOX circuit, the capacitor 2007, being in a discharged condition,
would cause the transistor 2020 to turn on and remain turned on
until the capacitor 2007 were charged. Of course, while the
transistor 2020 were turned on, the collector of the transistor
2028 would be at a low level thereby enabling the gated amplifier
418. This is not desirable and the transistor 2016 and its
associated circuitry prevents its occurrence as next described.
When power is applied to the VOX circuit by the +B power supply,
the emitter voltage of the transistor 2016 is placed at the +B
level and the base voltage of the transistor 2016 is placed at a
lower level because of the voltage drop across resistor 2015. This
turns on the transistor 2016 bringing the base voltage level of the
transistor 2020 high and thereby preventing the transistor 2020
from turning on. Since the transistor 2020 is prevented from being
turned on, the transistor 2028 remains off so that a high voltage
is applied to the gated amplifier 418.
It should be understood that the embodiment of the radio telephone
subscriber unit described herein is only illustrative of the
principles of the present invention. Numerous circuit
configurations could be employed without departing from the spirit
and scope of the present invention. For example, the signal
frequencies of the control signals employed, the number of control
signals utilized, the time duration and the time intervals between
the generation of the various control signals, and the specific
circuit configurations for generating such control signals should
be understood to be illustrative and not limiting of the present
invention. The appended claims are intended to cover all
modifications and changes which might be made in the disclosed
embodiment which do not depart from the spirit and scope of the
invention.
* * * * *