U.S. patent number 3,786,219 [Application Number 05/212,351] was granted by the patent office on 1974-01-15 for solid state induction cooking systems for ranges and surface cooking units.
This patent grant is currently assigned to General Electric Company. Invention is credited to John D. Harnden, Jr., William P. Kornrumpf.
United States Patent |
3,786,219 |
Kornrumpf , et al. |
January 15, 1974 |
SOLID STATE INDUCTION COOKING SYSTEMS FOR RANGES AND SURFACE
COOKING UNITS
Abstract
Solid state induction surface cooking units for domestic
electric ranges and other cooking appliances are defined with
respect to the operating parameters and functional components of
complete induction heating systems suited for this use. The surface
cooking units are designed for reliable, convenient, and safe
operation, and for circuit packaging using hybrid and monolithic
integrated circuits. Wide range power control of the inverter power
circuits is needed for general cooking but is obtained within a
limited ultrasonic operating range of the power semiconductors. The
inter-dependent electrical and magnetic characteristics utilized in
solid state induction cooking are related to the achievement of
such desirable user features as the cool cooking surface, fast
utensil warm-up, responsive heating, and unrestrained utensil
mobility. In addition to cooking by changing the relative heating
level, cooking is performed by setting the desired utensil
temperature and by setting the desired utensil power level.
Inventors: |
Kornrumpf; William P.
(Schenectady, NY), Harnden, Jr.; John D. (Schenectady,
NY) |
Assignee: |
General Electric Company
(Schenectady, NY)
|
Family
ID: |
22790644 |
Appl.
No.: |
05/212,351 |
Filed: |
December 27, 1971 |
Current U.S.
Class: |
219/626; 363/57;
219/665; 219/668 |
Current CPC
Class: |
G05D
23/24 (20130101); H02M 5/27 (20130101); H02M
7/53871 (20130101); H02M 7/523 (20130101); H02M
7/525 (20130101); H05B 6/062 (20130101); H02M
1/0085 (20210501) |
Current International
Class: |
H02M
5/02 (20060101); H02M 5/27 (20060101); H05B
6/06 (20060101); H02M 7/505 (20060101); H02M
7/525 (20060101); H02M 7/5387 (20060101); H02M
7/523 (20060101); H05B 6/12 (20060101); G05D
23/20 (20060101); G05D 23/24 (20060101); H05b
005/04 () |
Field of
Search: |
;219/10.49,10.75,10.77,10.79 ;321/10,14,18,43,45 |
References Cited
[Referenced By]
U.S. Patent Documents
Other References
Mapham, "A Low Cost, Ultrasonic Frequency Inventer Using A Single
SCR," G. E. Application Note 200.4a, Feb, 1967. .
Bedford & Hoft, "Principles of Inventor Circuits," J. Wiley
& Sons, pp. 235-238. .
"SCR Manual," 4th Ed., General Electric Co., pp. 182, 331-334, 314,
315..
|
Primary Examiner: Reynolds; Bruce A.
Attorney, Agent or Firm: John F. Ahern et al.
Claims
What we claim as new and desire to secure by Letters Patent of the
United States is:
1. A domestic induction surface cooking unit comprising
a nominally flat induction heating coil mounted adjacent a
substantially unbroken non-metallic utensil support to thereby
provide a relatively cool cooking surface,
a solid state power conversion circuit for converting a supply
voltage to ultrasonic output power that drives said induction
heating coil and generates an alternating magnetic field for
coupling the power to a cooking utensil, wherein
the ultrasonic output power is between 50 and 2,500 watts and has a
frequency between 18 and 40 kilohertz, and the solid state power
conversion circuit produces wide range ultrasonic output power for
general cooking purposes with a ratio of maximum to minimum output
power of 10:1 to 50:1.
2. A cooking unit according to claim 1 in which the maximum output
power is about 1,500 watts and the minimum output power is about 50
watts.
3. A cooking unit according to claim 1 in which said solid state
power conversion circuit includes a full bridge inverter
constructed with power semiconductors that produce rectangular
voltage pulses, and
means for controlling said power semiconductors to pulse width
modulate said rectangular voltage pulses to adjust the power
coupled to the cooking utensil.
4. A cooking unit according to claim 3 in which said bridge
inverter is additionally operated at a variable ultrasonic
frequency to achieve wide range power control.
5. A domestic induction surface cooking unit comprising
a nominally flat induction heating coil mounted adjacent a
substantially unbroken non-metallic utensil support to thereby
provide a relatively cool cooking surface,
a solid state power conversion circuit for converting a supply
voltage to ultrasonic output power that drives said induction
heating coil and generates an alternating magnetic field for
coupling the power to a cooking utensil, wherein
the output power is between 50 and 2,500 watts and has a frequency
between 18 and 40 kilohertz, and
said solid state power conversion circuit produces a unidirectional
voltage and includes filter means for filtering the unidirectional
voltage, and further includes an inverter energized by the filtered
unidirectional voltage that produces wide range ultrasonic output
power for general cooking purposes with a ratio of maximum to
minimum output power of 10:1 to 50:1.
6. A cooking unit according to claim 5 in which the maximum output
power is about 1,500 watts and the minimum output power is about 50
watts.
7. A cooking unit according to claim 5 in which said solid state
power conversion circuit includes a time ratio control circuit
coupled between said filter means and inverter for changing the
magnitude of the filtered uni-directional voltage energizing the
inverter for wide range power control.
8. A domestic induction surface cooking unit comprising
a nominally flat induction heating coil mounted adjacent a
substantially unbroken non-metallic utensil support plate to
thereby provide a relatively cool cooking surface,
a static power conversion circuit including filter means and an
inverter controlled by solid state power device means for
converting a filtered unidirectional voltage to an ultrasonic
frequency wave that drives said induction heating coil for coupling
output power to a cooking utensil,
a gating circuit for selecting the intervals of conduction of said
power device means,
an inhibit circuit coupled to said gating circuit for selectively
inhibiting operation of said inverter,
start-up and shut-down circuit means coupled to said inhibit
circuit and gating circuit for controlling starting and stopping
transients and the application to and removal of voltage from said
inverter,
device protection means for protecting said power device means from
undesired voltages and currents,
output power adjustment means coupled to said gating circuit and
inhibit circuit for varying the output power of said inverter and
therefore the heating level of the utensil, and
user control means for energizing and de-energizing said static
power conversion circuit and setting a selected utensil heating
level.
9. A cooking unit according to claim 8 further including surge
protection means and a radio frequency interference filter
connected across the input terminals of said static power
conversion circuit.
10. A cooking unit according to claim 8 wherein said static power
conversion circuit further includes a full wave rectifier and means
for controlling the magnitude of the filtered unidirectional
voltage to obtain wide range control of the output power and
therefore of the utensil heating level.
11. A cooking unit according to claim 8 further including cooling
means for said induction heating coil and static power conversion
circuit.
12. A cooking unit according to claim 8 further including a current
meter located between said filter means and inverter for displaying
the state of the circuit to the user.
13. A cooking unit according to claim 8 further including utensil
presence detection circuit means coupled to said gating circuit for
sensing the absence of a cooking utensil coupled to said induction
heating coil and modifying the operation of said gating
circuit.
14. A cooking unit according to claim 8 wherein said device
protection means comprises means for monitoring the filtered
unidirectional voltage supplied to said inverter and actuating said
inhibit circuit in response to the sensing of a predetermined low
voltage level.
15. A cooking unit according to claim 8 wherein said device
protection means comprises means for monitoring the voltage at a
terminal of said solid state power device means and reducing the
power output of said inverter in response to the sensing of a
predetermined high voltage level.
16. A solid state induction surface cooking unit comprising
an induction heating coil for inductively heating a cooking
utensil,
a solid state power conversion circuit for converting a
unidirectional voltage to variable ultrasonic output power that is
applied to said induction heating coil and produces a range of
utensil heating levels,
a gating circuit for controlling said solid state power conversion
circuit to produce a heating level in dependence upon the algebraic
sum of a plurality of input signals,
a plurality of control logic circuits each generating one of said
input signals and including start circuit means, stop circuit
means, watts control means, user safety means, and circuit
protection means,
summing means for deriving the sum of the control logic circuit
input signals and applying the sum to said gating circuit, and
user control means for energizing and de-energizing said solid
state power conversion circuit and setting said watts control means
to obtain a selected heating level.
17. A cooking unit according to claim 16 in which said solid state
power conversion circuit includes input voltage control means for
reducing the magnitude of said unidirectional voltage for wide
range control of the ultrasonic output power and therefore the
range of utensil heating levels.
18. A cooking unit according to claim 16 in which said user safety
means comprises a utensil presence detection circuit that is
operative when metallic objects significantly smaller than a
cooking utensil are coupled with said induction heating coil as
well as when a cooking utensil is not coupled therewith.
Description
CROSS-REFERENCE TO RELATED APPLICATIONS
The power converter circuit used in describing a specific example
of the practice of the invention is disclosed and claimed in the
concurrently filed application Ser. No. 211,926 by William P.
Kornrumpf and John D. Harnden, Jr., entitled "Reliable Solid State
Induction Cooking Appliance with Control Logic," and assigned to
the same assignee as the present invention.
BACKGROUND OF THE INVENTION
This invention relates to solid state induction heating systems
uniquely suitable for electric ranges and other cooking appliances
for inductively heating cooking utensils.
The idea of applying induction heating to the cooking of food has
been known generally for a number of years but has not resulted in
a successful product that is competitive with the widely used gas
range and the common electric range based on resistance heating.
The basic mechanism of induction cooking is that an alternating
magnetic field is coupled across a gap with the utensil bottom,
which acts as a single turn secondary winding. Theoretically the
process is efficient since heat is generated only in the metallic
utensil where it is wanted. However, prior art proposals were bulky
and expensive and otherwise not satisfactory for wide usage.
The development of solid state induction cooking appliances
operating at ultrasonic frequencies of 18 kHz and above has made
possible a significant reduction in cost and size and overcomes
other deficiences of the prior art equipment. Suitable solid state
power circuits that can be used as ultrasonic frequency generators
in an induction surface cooking unit for domestic electric ranges
and other cooking appliances are described in the following two
copending applications: Ser. No. 200,526 by David L. Bowers, Donald
S. Heidtmann, and John D. Harnden, Jr.; and Ser. No. 200,424 by
John D. Harnden, Jr. and William P. Kornrumpf, both filed Nov. 19,
1971, and assigned to the same assignee as this invention. Cool top
appliances as therein described typically are comprised by a flat
induction heating coil driven by a static power conversion circuit
that includes a solid state inverter as an essential component. The
power output of the inverter is modulated to change the heating
level in the utensil and therefore the temperature at which the
food is cooked.
The present invention is directed to other features of a complete
induction heating system needed to build surface cooking units and
ranges for performing a variety of cooking tasks more
satisfactorily, and which is reliable and convenient for operation
by technically unskilled persons such as housewives and chefs.
Static power converters, especially those with semiconductor
components, require protection to prevent malfunction and failure
under abnormal circuit conditions such as overvoltages and
overcurrents. Furthermore, the coupled utensil is the inverter load
and the reflected impedance changes the inverter's electrical
parameters. There are severe load requirements if the unit is to be
operable with a variety of pots and pans of different sizes and
materials, under both load and no-load conditions, and even with
loads the unit is not designed to heat since this is beyond the
control of the manufacturer. The requirement for automatic and
continuous operation means that the circuit design must anticipate
circumstances that could cause failure or temporary shutdown. In an
improved cooking unit it would further be desirable to have the
option of heating the utensil to a specific temperature, as opposed
to watts control of the inverter output, for the cooking of foods
such as bacon that are best cooked within an acceptable temperature
band.
SUMMARY OF THE INVENTION
Induction surface cooking units for typical domestic usage in
electric ranges and built-in cooktop installations are
characterized by a relatively cool, unobstructed cooking surface in
the form of a substantially unbroken non-metallic utensil support
plate beneath which the induction heating coil is mounted. The
utensil support plate can be made of plastic as well as glass or
ceramic material. A defining condition for successful induction
cooking is the power-frequency relationship of the ultrasonic
output power generated by the solid state power conversion circuit
that drives the induction heating coil. All domestic cooking is
performed with ultrasonic output power that has a power level
between 50 and 2,500 watts and a frequency between 18 and 40
kilohertz. General purpose cooking requires wide range output power
greater than a 10:1 ratio to the maximum 50:1 ratio, but this must
be produced within the feasible operating range of solid state
power devices without descending to audible frequencies. The 18-40
kHz frequency range is also desirable because the skin depth of
current penetration is sufficiently thin that relatively light
weight magnetic and non-magnetic cooking utensils can be used. The
light weight utensils make possible fast warm-up and responsive
heating. The cooking utensil is freely movable on the cooking
surface since the utensil and support plate are not required to be
optically flat and also because there are insignificant
ponderomotive forces.
A complete induction surface cooking unit preferably employs a
static power conversion circuit including filter means and an
inverter for converting a filtered unidirectional voltage to
ultrasonic power for driving the induction heating coil. Minimum
components for reliable and convenient cooking in addition to the
gating circuit for the inverter power devices include an inhibit
circuit for selectively inhibiting operation of the inverter;
start-up and shut-down means coupled to the inhibit and gating
circuits for controlling transients and the application and removal
of voltage from the inverter; device protection means; output power
adjustment means; and user controls. A number of these functions
can desirably be provided by an integrated circuit gating control
circuit for controlling the inverter. Optional components depending
on the model and circuitry are such things as surge protection
means and an RFI filter connected across the input terminals,
impedance matching or switching means, cooling means, a utensil
presence detection circuit, a temperature regulating system, etc.
The induction cooking system is described with respect to a
specific surface cooking unit in an electric range or cooktop, and
also with respect to a generalized system. Similar systems are
given for the special cases using a thyristor inverter energized by
an a-c source, and a transistor inverter energized by a d-c source.
Another generalized system is described in terms of logic signal
inputs and the other inputs for controlling the solid state power
conversion circuit.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a plan view of a flat spiral induction heating coil and a
block representation of a solid state power conversion circuit for
supplying ultrasonic frequency power to the coil;
FIG. 2 is a schematic cross-sectional view showing the relation of
the induction heating coil to the utensil support and cooking
utensil;
FIG. 3 is a cross-sectional view of a different type of cooking
utensil with an attached temperature sensor and an embedded
receptor plate for coupling power to the utensil;
FIG. 4 is a fragmentary perspective view of an electric range with
a smooth utensil support plate or cooking surface;
FIG. 5 is a schematic circuit diagram showing by way of
illustration a solid state power converter suitable for the
practice of the invention which comprises a phase controlled
rectifier and a variable frequency series resonant inverter;
FIGS. 6a and 6b are waveform diagrams of the induction coil current
and commutating capacitor voltage for the static power conversion
circuit of FIG. 5, showing in each diagram the waveforms at two
different output frequencies;
FIG. 6c is a waveform diagram of the thyristor forward voltage
under load and no-load conditions (the sinusoidal induction coil
current is illustrated for reference purposes);
FIG. 7 is a detailed schematic diagram of the gating control
circuit shown in block diagram form in FIG. 5;
FIG. 8 illustrates the power-frequency operating "window" for
domestic solid state induction surface cooking units;
FIGS. 9 and 10 show waveforms useful in explaining the principles
of power modulation with circuits that generate sine wave and
square wave shapes;
FIG. 11 shows in full lines the power-frequency characteristic for
the converter of FIG. 5 obtained by solely varying the output
frequency, while the desired characteristic with an extended low
output power range is shown in dashed lines;
FIGS. 12 and 13 are respectively resistivity-temperature and
permeability-temperature characteristics for suitable magnetic
utensil materials;
FIG. 14 is a hysteresis loop for magnetic utensil materials
illustrating minor loop operation for asymmetrical electrical
circuits such as the FIG. 5 converter;
FIG. 15 is a power-thickness characteristic for non-magnetic
utensil materials;
FIG. 16 is a schematic circuit diagram of a full bridge inverter
implemented with transistors for producing the pulse width
modulated square wave shapes given in FIG. 10;
FIG. 17 is similar to FIG. 16 but includes an impedance matching
transformer;
FIG. 18 is a schematic circuit diagram of a d-c power supply with
two other techniques for varying the input voltage, by phase
controlling the alternating supply voltage in advance of the
rectifier and by chopping the filtered d-c voltage;
FIG. 19 is a block diagram of the functional components of a
generalized complete induction heating system for solid state
induction surface cooking units, including some features that are
optional;
FIG. 20 is a block diagram similar to FIG. 19 of a complete
induction surface cooking appliance that is energized by a
commercially available a-c source and incorporates an inverter with
thyristor switches and commutation circuitry;
FIG. 21 is similar to FIG. 20 but shows by comparison the
functional components of an induction surface cooking appliance
energized from a d-c source that incorporates a transistor
inverter; and
FIG. 22 is a logic type of block diagram of the required and
optional function components and features of a complete induction
cooking system for solid state surface cooking units.
DESCRIPTION OF THE PREFERRED EMBODIMENTS
Introduction
The induction cooking appliance shown in FIGS. 1-4 will be
described with regard to an induction surface cooking unit in a
domestic electric range but essentially the same mechanical
structure and circuitry in higher and lower power versions is
suitable for commercial cooking equipment and counter-top food
cooking or warming appliances. The solid state power conversion
circuit indicated generally at 12 is energized by either a source
of alternating voltage or a source of direct voltage, and includes
as an essential component a solid state inverter for generating an
ultrasonic frequency wave that drives an induction heating coil 15.
Induction heating coil 15 typically is a single layer, annular,
flat spiral, air-core coil wound with braided ribbon or solid flat
strip conductor with a rectangular cross section. To generate
sufficient magnetic flux to heat the utensil to the desired heating
level or specific utensil temperature, coil 15 is tightly wound
with the short cross-sectional dimension of the conductor facing
upwards and adjacent turns separated by a flat insulating strip 20.
While coil 15 is ordinarily flat, it is within the scope of the
invention to use a nominally flat coil such as one that is slightly
dished to improve the field distribution. Coils with ferrite return
paths can also be used.
In the surface cooking unit (FIG. 2), induction heating coil 15 is
appropriately mounted in a horizontal position immediately below a
non-metallic utensil support 16 typically made of a thin sheet of
glass or plastic. If required, support 16 can have some metallic
content for shielding and decorative purposes, but this is
necessarily limited to a small amount. Support plate 16 is commonly
referred to as the cooking surface and supports the metallic
cooking utensil 17 to be heated. Cooking utensil 17 is more
particularly an ordinary cooking pot or pan, a frying pan, or some
other available metallic utensil used in food preparation. The
utensil can be made of a magnetic material such as magnetic
stainless steel, enameled steel, or cast iron; a non-magnetic
material such as aluminum and aluminum foil: or a laminated product
such as copper-clad stainless steel or triple-clad (stainless-cast
iron-stainless steel). Special cooking utensils are not required
although the best and most efficient results are obtained by
optimizing the size, shape, and material of the cooking utensil.
High loss magnetic steel utensils couple well to coil 15 and are
heated most efficiently, while copper-clad utensils and thick
aluminum utensils do not couple well to the coil, and the laminated
and cast iron utensils are inbetween. Additionally, it is important
to impedance match the utensil to the power circuit for best
overall efficiency. FIG. 3 shows a non-metallic utensil 17', made
for instance of plastic, with a metallic receptor plate 18 embedded
in the utensil bottom to be heated inductively by coil 15. Any of
these utensils may be used with an induction surface cooking unit
when the coil 15, solid state power conversion circuit 12, and the
gap between coil and utensil are properly designed. Ordinarily a
gap of at least one-eighth inch is required between the top of coil
15 and the bottom of utensil 17 or receptor plate 18 to allow space
for support 16, and the gap is no greater than about one-half inch
in order to couple sufficient power into the utensil to produce
adequate heating for cooking purposes.
Operation of solid state power conversion circuit 12 to impress an
ultrasonic frequency wave on induction heating coil 15 results in
the generation of an alternating magnetic field, and the magnetic
flux which is produced is coupled across the air gap through
non-metallic support 16 to utensil 17 or receptor plate 18. An
ultrasonic frequency above 18 kHz or so is considered to be the
upper limit of human hearing and is selected to make the cooking
appliance inaudible to most people. The other end of the band of
feasible ultrasonic frequencies is 40 kHz and is determined
primarily by economic considerations in conjunction with the high
frequency limitations of available power devices. An essential
feature of the invention is the non-metallic support plate 16
which, as shown in FIG. 4, has a relatively smooth and
substantially unbroken utensil supporting surface. This is not to
preclude the existence of small apertures in the cooking surface
for sensors or indicators. At ultrasonic frequencies, there are
insignificant reaction forces of attraction or repulsion which at
lower frequencies would cause utensil 17 to move horizontally when
placed on the cooking surface approximately centered with respect
to one of the induction surface cooking unit positions illustrated
in dashed lines. FIG. 4 shows the induction surface cooking unit
incorporated in an electric range, with a control knob 21 for each
unit on the upstanding control panel for turning the individual
unit on and off and setting the desired heating level or power
level. In the model illustrated, one cooking unit has an additional
control knob 21' for setting a specific utensil temperature to
which the utensil is to be heated. Indicator light 20 turns on when
power is applied to indicate an energized unit. Built-in
counter-top induction surface cooking units, often referred to as
cooktops, have the same configuration.
The transfer of energy to utensil 17 to heat it is relatively
efficient since heat is generated only in the utensil and none is
lost because of mismatch in size between the heating element (coil)
and utensil. Hence, less electrical power is used as compared to
conventional electric ranges and the operating costs are lower, and
is consistent throughout the life of the appliance. Another feature
of induction cooking is that the surface of support plate 16 is
relatively cool since in addition to not being heated directly by
the induction heating mechanism, the highest temperatures involved
are about 450.degree.-500.degree.F, the approximate maximum
temperature to which the bottom of utensil 17 is heated to cook
food. Because of the cool cooking surface, spilled foods do not
burn and char and therefore both support plate 16 and utensil 17
are easy to clean. A cool, smooth cooking surface also makes it
possible to use the surface before cooking, or even immediately
after cooking, for other functions relating to food preparation
such as opening cans, trimming and cutting vegetables, transferring
cooked foods from a cooking utensil to a serving dish, etc. The
utensil is heated more uniformly than is the case with the
conventional gas range or electric range based on resistance
heating, and in particular there is an absence of localized hot
spots at high heating levels. Moreover, the inductive heating of
cooking utensils results in a low thermal mass system. Heating
begins promptly because of the fast warm-up period. Since there is
a relatively low storage of heat in utensil 17, the temperature to
which the utensil is heated can be changed rapidly, as from boiling
to simmering to warming temperatures.
Complete induction heating systems uniquely suited for solid state
induction surface cooking units for domestic usage are illustrated
in block diagram form in FIGS. 19 to 22. The details of these
heating systems are tailored for domestic ranges and cooktop units,
whether built-in or portable, with a complete range of available
heating levels for a variety of cooking tasks from rapid boiling to
warming easily burned foods. It will be appreciated, however, that
to some extent the principles discussed are applicable to
commercial cooking equipment, on one hand, and portable food
warming appliances with a power output of 50-400 watts, on the
other hand. The desirable characteristics of the electrical and
magnetic systems for these induction surface cooking units are
discussed with regard to FIGS. 8 to 18. This discussion touches on
some of the alternative electrical circuits that are not mentioned
elsewhere in this application or in the cross-referenced
applications. The same comment can be made that some of these
characterictics are specifically for domestic ranges and cooktops,
but many are of general applicability in higher and lower power
cooking and warming units. To facilitate the understanding of these
block diagrams, characteristics, and circuits, it is advantageous
to review in some detail the structure and operation of one form of
induction surface cooking unit that is illustratory of the practice
of the invention. The description is largely by way of summary of
the operation of the circuit, and for further details the reader is
referred to the aforementioned concurrently filed application, Ser.
No. 211,926. Identical components are designated by the same
reference numerals and operate in the same manner.
Detailed Circuits of a Specific Induction Surface Cooking Unit
Solid state power conversion circuit 12 in FIG. 5 is energized by a
commercially available source of alternating voltage and includes
as major components a phase controlled rectifier 13 and a variable
frequency one-thyristor series resonant inverter 14 in which
induction heating coil 15 is used in a dual function to couple
power to the utensil as well as to provide commutating inductance
in the thyristor commutation circuit. The inverter is therefore
relatively simple and inexpensive and requires only one gating or
firing circuit. The input terminals 22 and 23 of power converter 12
are energized by a 120 volt, 60 Hz single phase source of a-c
supply voltage. Where the energy source is the utility power
supply, the solid state equipment usually requires the connection
of a surge protection device or circuit 130 and an RFI filter 131
between input terminals 22 and 23. The first protects the surface
cooking unit from voltage surges in the power distribution system,
while the second prevents ultrasonic or radio frequency energy
generated by the cooking unit from creating a disturbance in the
utility power system. Conventional devices and networks can be
used. The d-c power supply, provided by full wave phase controlled
bridge rectifier 13 and a filter network including series filter
inductor 24' and a shunt filter capacitor 24, produces a varying
d-c input voltage for inverter 14. This is one technique for
controlling the power output of the inverter and therefore the
heating level or specific utensil temperature. Another power
control mechanism is to change the inverter output frequency and
therefore the rate of supplying current pulses to the induction
heating coil. Suitable phase control circuits for the SCR's in
rectifier 13 are given in the SCR Manual, 4th edition, published by
the General Electric Company, Semiconductor Products Department,
Syracuse, N.Y. copyright 1967. Rectifier 13 can be a full wave
diode rectifier when it is desired to control the power output of
inverter 14 solely by varying the inverter output frequency in the
manner to be explained.
The power circuit connected between d-c input terminals 25 and 26
comprises induction heating coil 15 connected in series with a
commutating capacitor 27 and the inverse-parallel combination of a
unidirectional conducting thyristor 28 and a power diode 29. A
series RC snubber circuit 30 is also coupled across the load
terminals of thyristor 28 for dv/dt protection to limit the rate of
rise of reapplied forward voltage to the device. A reset inductor
31 connected directly across commutating capacitor 27 functions to
recharge capacitor 27 between cycles of operation when both
thyristor 28 and diode 29 are non-conducting. The load for the
inverter is the electrical loss in the utensil. As the physical
equivalent for utensil 17 in FIG. 5 suggests, utensil 17 functions
as a single turn secondary winding with a series resistance 17r
representing the resistive part of the I.sup.2 R or eddy current
losses, and hysteresis losses where applicable. Induction heating
coil 15 functions as the primary winding of the air-core
transformer, and the current and voltages induced in utensil 17
when the induction surface cooking unit is in operation are
determined essentially by the transformer laws. In an equivalent
electrical circuit (not here illustrated) for coil 15 and utensil
17, coil 15 is represented by a series connected inductance 15i and
resistance 15r and these are in turn in series with the parallel
combination of a resistance 17r and an inductance 17i representing
the utensil.
With the utensil load in place, the commutating inductance for the
series resonant circuit comprising coil 15 and commutating
capacitor 17 is composed of both the coil inductance 15i and the
reflected utensil inductance 17i. Under no-load conditions when the
utensil is removed from the induction surface unit, the amount of
commutating inductance increases. This causes a change in the
resonant frequency of the series resonant circuit and there is a
decrease in the inverter output frequency. With an average or
selected utensil load in place, this series resonant circuit is
tuned to resonance at a resonant frequency higher than the highest
desired output frequency. In explaining the operation of the power
circuit, it is assumed that the surface cooking unit is operated in
the watts control mode by setting the desired utensil heating level
by the use of control knob 21. Gating control circuit 33 supplies
gating or firing signals at a variable repetition rate to the gate
of thyristor 28, to operate the inverter with a corresponding
repetition rate or output frequency according to the power output
in watts that is desired. Under steady state operating conditions,
it is assumed that commutating capacitor 27 is reset negatively by
the operation of reset inductor 31 in the interval following the
previous conduction cycle. The application of a gating pulse to
thyristor 28 causes it to turn on, energizing the damped series
R-L-C oscillatory circuit comprising coil 15, commutating capacitor
27, and the reflected inductance and losses in utensil 17. A
positive polarity half-sinusoidal current pulse flows through
induction heating coil 15 and charges commutating capacitor 27 to a
value exceeding the supply voltage V.sub.dc. At the end of the half
cycle, the voltage on commutating capacitor 27 reaches a peak and
the current drops to zero and then reverses as commutating
capacitor 27 discharges negatively through diode 29. Commutating
capacitor 27 applies a reverse bias to thyristor 28, and turn-off
of the thyristor is assured by the reverse voltage applied by
conducting diode 29. At the end of the negative polarity half
cycle, the current through induction heating coil 15 remains zero
since the next gating pulse is not applied to thyristor 28 at this
time. While devices 28 and 29 were conducting, the current in reset
inductor 31 was increasing due to the net positive d-c voltage on
commutating capacitor 27 during the conduction cycle. During the
power circuit off-time, reset inductor 31 discharges thereby
leaving commutating capacitor 27 with a net negative charge at the
end of the circuit off-time. The supplying of a gating pulse to
thyristor 28 begins the next complete cycle of operation. FIG. 6a
shows in full lines the sinusoidal induction current coil for two
complete cycles of operation separated by a time delay interval 34
corresponding to the circuit off-time. The corresponding
commutating capacitor voltage under steady state conditions with
the utensil load in place is shown in full lines in FIG. 6b. At the
end of the conduction cycle the magnitude of the negative voltage
on capacitor 27 is lower than the peak positive voltage, and the
action of reset inductor 31 during the interval 34 is to change the
capacitor voltage almost linearly as indicated at 35, leaving the
capacitor with a net negative charge at the end of interval 34. Due
to this extra charge on commutating capacitor 27, the peak
capacitor voltage 36 during the next cycle of operation is higher,
as compared to a power circuit without reset inductor 31, since the
system energy is replenished. The effect of shortening the off-time
interval 34 by increasing the repetition rate of the gating pulses
is to increase the inverter output frequency and therefore the
current and power supplied to utensil 17. Increasing the inverter
output frequency also has the beneficial result of increasing the
amplitude of the sinusoidal current pulses as well as their
frequency. This is illustrated in FIG. 6a by the second cycle
dashed line current waveform. By advancing the thyristor gating
pulse, the ratio of conduction time to capacitor recharge time
increases, thereby on a steady state basis increasing the average
current in reset inductor 31. The result is that, referring to the
dashed line capacitor voltage characteristic of FIG. 6b,
commutating capacitor 27 is charged negatively to a higher negative
voltage during the circuit off-time as indicated at 35' so that the
peak capacitor voltage 36' during the next conduction cycle is
higher than the peak voltage 36 for the lower inverter frequency
case. A limit on inverter frequency is reached when the value of
the current in reset inductor 31 becomes significant in comparison
to the high frequency reverse current pulse in coil 15 and
commutating capacitor 27, since this in effect reduces the
commutation time available to the thyristor. In summary, there are
two effects that increase the power in watts applied to utensil 17
when the inverter output frequency is increased. There are larger
and more frequently applied current pulses in induction heating
coil 15. In addition, watts control of the amount of heat generated
in utensil 17 can be obtained by varying the input d-c voltage by
using the phase controlled rectifier 13.
The function of gating or firing control circuit 33 in FIG. 5 is
not only to generate a train of variable repetition rate gating
pulses for thyristor 28, but also to incorporate control logic
which ensures reliable, automatic, and satisfactory operation of
the induction surface cooking unit. This is done in this control
circuit by modifying the normal operation of the control circuit
and in particular the operation of the turn-on circuitry for
producing the gating or firing signals that initiate turn-on of
thyristor 28. The gating pulse repetition rate is changed to a
lower, more satisfactory value, and the generation of gating pulses
in inhibited completely when certain predetermined abnormal circuit
conditions are sensed that tend to lead to malfunction or failure
of the power device or other power circuit components. In addition
to these protective circuit features the control circuit is used
during startup and shutdown of the unit, and to adapt the unit for
operation in the no-load condition by sensing the absence of the
utensil coupled to the induction heating coil and modifying the
operation of the control circuit.
Gating control circuit 33 is preferably fabricated as a monolithic
or hybrid integrated circuit. In order to avoid the addition of
power consuming components to the inverter power circuit, the trade
off is made of retaining a relatively simple and inexpensive power
circuit at the expense of increasing the complexity of the control
circuit. Hence the desirability of manufacturing it in integrated
circuit form. It is also desirable to fabricate the thyristor-diode
combination 28, 29 and power rectifier 13 as hybrid or monolithic
integrated circuits. These low cost approaches are needed
especially in consumer oriented appliances to reduce the cost, save
space, and improve reliability and serviceability I.C. gating
control circuit 33 includes a low voltage power supply which, for
proper operation of the gating circuit, is energized when power is
applied to inverter 14. Accordingly, the low voltage power supply
can be connected to power rectifier terminal 25'. An alternative
arrangement here shown is to supply gating control circuit 33 with
continuous direct voltage independent of the power circuit by using
an additional pair of half wave rectifiers 36 connected to the
input terminals of main rectifier 13. The low voltage power supply
is then connected to output terminal 37 of the auxiliary rectifier.
Another important feature of gating control circuit 33 in terms of
use in consumer appliances is that it is adjusted to the desired
setting by appropriate user controls 40 that are accessible to the
user, such as an adjustable resistor or potentiometer that is
adjusted by turning control knob 21.
The components illustrated in the detailed circuit diagram of
gating control circuit 33 in FIG. 7 are numbered consecutively from
left to right for the convenience of the reader. Control circuit 33
is energized by a low voltage d-c power supply 48 which establishes
a positive low voltage terminal 49 and the common negative terminal
26 between which most of the components of the control circuit are
connected. Low voltage d-c power supply 48 comprises a pair of
voltage dropping resistors 118 and 121 connected in parallel
between the auxiliary d-c supply terminal 37 and low voltage
terminal 49, and also a pair of Zener diodes 124 and 125 and two
filter capacitors 123 and 126 all connected between low voltage
terminals 49 and 26. Filter capacitor 123 is an energy storage
electrolytic capacitor while filter capacitor 126 is a high
frequency ceramic capacitor to provide a low source impedance so
that there is sufficient current to generate a gating pulse of the
required magnitude. The Zener regulated supply provided at the low
voltage terminals is typically 15 volts.
Voltage controlled pulse generator 46 produces a train of gating
pulses at a variable repetition rate which are amplified by gating
pulse amplifier 47 before being applied to the gate electrode of
power thyristor 28. Output frequency control circuit 41 determines
the basic input voltage level to voltage controlled pulse generator
46 and thus the gating pulse repetition rate and consequently the
inverter output frequency. These functional units in combination
are the turn-on circuitry for initiating a complete cycle of
conduction of thyristor 28 and diode 29.
Voltage controlled pulse generator 46 comprises essentially a
complementary unijunction transistor relaxation oscillator. The
emitter of complementary unijunction transistor 113 is connected to
the junction of a main timing capacitor 109 and a transistor 110
which functions as a variable impedance in the charging circuit by
virtue of the fact that the collector current is a function of the
base voltage. The d-c voltage level on a control capacitor 108
connected between the base of transistor 110 and terminal 26
determines the rate of charging of capacitor 109 and hence the
pulse generation rate. In operation, main timing capacitor 109
charges negatively through transistor 110 and emitter resistor 111
and causes complementary unijunction 113 to break over and conduct
in each charging cycle when the emitter peak point voltage is
reached. Capacitor 109 then discharges through base resistor 112
and generates a current pulse that is amplified by gating or firing
pulse amplifier 47. Because control capacitor 108 is relatively
large the repetition rate ramps from one setting to another as the
power level is adjusted or as the protection circuits and other
circuits operate automatically in the manner to be explained.
Gating pulse amplifier 47 comprises a small transistor amplifier
115 having its base connected to the base 1 of complementary
unijunction 113. The voltage level between emitter resistors 116
and 117 produced when transistor 115 is turned on is the input
voltage to a Darlington amplifier comprising transistors 119 and
122. A relatively high current gating pulse is assured by the low
source impedance provided by filter capacitor 126 as previously
mentioned. Emitter resistor 120 assures a rapid turn-off of
transistor 112 when the pulse is completed. Output frequency
control 41 is basically a variable resistance divider network for
adjusting the d-c voltage level on control capacitor 108. User
adjustment potentiometer 40 is connected through isolating resistor
51 to the positive terminal 108p of control capacitor 108, and
places a variable amount of resistance in series with the control
capacitor. The value of resistor 52 determines to a first order the
maximum output frequency that is possible, while the value of
resistor 54 determines the minimum output frequency. The pointer of
potentiometer 40 is connected for movement with control knob 21
(FIG. 4), which is referred to as the watts control since it
adjusts the power output of inverter 14.
As is well known, failure of thyristor 28 can occur if the anode
voltage exceeds the peak forward voltage of the device or if there
is insufficient turn-off time to switch the device from the
conducting to the forward blocking condition. In gating control
circuit 33, maximum frequency control 42 and thyristor overvoltage
detection circuit 45 provide device protection by overriding output
frequency control 41 upon the detection of certain abnormal circuit
conditions. In addition, snubber circuit 30 in the power circuit
(FIG. 5) provides additional device protection by preventing dv/dt
firing. Maximum frequency control circuit 42 sets the output
frequency limit by operating as a clamp on the voltage across
control capacitor 108. A maximum frequency limit is needed to
prevent the inverter from entering the unstable short commutation
time mode of operation for the reasons given in the discussion of
FIG. 6a. Diode 55 is normally reverse biased, but when the
potential of terminal 108p rises above a critical voltage as
determined by the setting of potentiometer 57, the diode becomes
forward biased and conducts. Diode 55 and the portion of
potentiometer 57 between its pointer and negative terminal 26 is in
parallel with control capacitor 108 so that the voltage across the
capacitor is limited to 0.6 volts above the value set by
potentiometer 57.
Thyristor overvoltage detection circuit 45 monitors the thyristor
forward blocking voltage at the anode of the device and adjusts the
repetition rate of voltage controlled pulse generator 46 to keep
the thyristor in a safe operating mode. Due to the fact that the
amplitude of the sinusoidal current pulses in the inverter and the
commutating capacitor voltage increases with an increase in
inverter output frequency, circuit 45 lowers the output frequency
when the forward blocking voltage exceeds a predetermined critical
value lower than the peak forward voltage rating of the thyristor.
This reduces the forward blocking voltage applied to the thyristor.
A string of Zener diodes 81 (only one is illustrated) or other
suitable voltage responsive sensors such as metal oxide varistors
sense the voltage at the anode of thyristor 28. Zener diode 81 is
normally nonconductive, but supplies current to resistor string
82-85 when the overvoltage threshold level is reached. The
resulting voltage drop across resistor 85 turns on a transistor 89
with the result that control capacitor 108 is discharged through
resistor 88 and the collector-emitter path of transistor 89.
Resistors 84 and 85 set the level of overvoltage detection and
provide a positive turn-off bias for transistor 89. Resistor 83 and
capacitor 80 form a low pass filter which is used to eliminate any
transient component of rising thyristor anode voltage passed by the
Zener string. Until capacitor 80 charges to a predetermined
voltage, there is insufficient voltage across resistors 84 and 85
to supply the required base drive current for transistor 89. Diode
86 becomes conductive under appropriate conditions to prevent the
application of an overvoltage to transistor 89.
Low input voltage detection circuit 43 monitors the input voltage
to inverter 14 at positive input d-c supply terminal 25 and is
operative to initially reduce the repetition rate of gating pulse
generator 46 and, after a predetermined time delay, to lock out or
inhibit the pulse generator. This circuit operates during start-up
when the unit is initially energized but before filter capacitor 24
is fully charged, and is effective to control starting transients
caused by the interaction of the series resonant power circuit and
the parallel resonant circuit formed by reset inductor 31 and
capacitor 27. These transients could under certain conditions cause
a commutation failure. During shut-down when the induction cooking
unit is turned off this circuit operates to remove power from the
power circuit in a satisfactory, controlled manner since the pulse
generator continues to operate for a short time after sensing a low
power circuit voltage. Furthermore, when the input voltage is too
low to yield sufficient commutation energy in commutating capacitor
27, as during a temporary voltage reduction or a brown-out, there
may be a commutation failure. A low input d-c voltage below a
predetermined level is sensed by a Zener diode 90 or other voltage
responsive sensor. Under normal conditions, Zener diode 90 is
conductive and supplies current to the remainder of the detection
circuit, and it is the absence of this current that triggers the
operation of the circuit. A transistor 97 is normally biased to the
non-conducting state by the current flow through Zener diode 90 and
resistors 91 and 92 which establishes a reverse biasing potential
at the base of the transistor. The sensing of a low input voltage
establishes base drive current for transistor 97 by the connection
of the base to negative terminal 26 through resistors 93 and 92.
Another transistor 95 also turns on in snap-action fashion by means
of the feedback connection established with transistor 97 by
resistors 98 and 94. The clamping circuit comprising diode 95a,
adjustable resistor 95b, the collector-emitter of transistor 95,
and Zener diode 96 is connected directly across the terminals of
control capacitor 108. Upon the turn-on of transistor 95, the
voltage across control capacitor 108 is clamped by the forward
biased diode 95a and conducting transistor 95 to the voltage of
Zener diode 96. This voltage level sets the basic inverter output
frequency to the lower frequency limit, typically 18 kHz. At this
frequency, it would be safe to start firing thyristor 28 at any
voltage above the lower limits set by Zener diode 90.
A continuation of the low input voltage condition requires that the
firing of thyristor 28 be halted completely. This is accomplished
by clamping the voltage across main timing capacitor 109 which is
effected by rendering conductive a clamping transistor 107
connected directly across its terminals. The change of state of
transistor 97 from non-conducting to conducting also initiates
current flow through the low pass filter comprising a resistor 100
and time delay capacitor 99. After a predetermined time delay
dependent upon their time constant, capacitor 99 is charged to a
voltage level sufficient to cause Zener diode 102 to breakover and
conduct. The voltage drop across a resistor 103 in series with
Zener diode 102 biases a transistor 106 to the conducting state,
and the resulting current flow through series connected resistors
104 and 105 supplies base drive current to clamping transistor 107.
Since main timing capacitor 109 cannot charge up, voltage
controlled pulse generator 46 is inhibited and prevents the
subsequent generation of firing pulses. Upon the return of
sufficient input d-c voltage to enable satisfactory operation of
the power circuit, Zener diode 90 conducts causing transistors 97
and 95 to turn off initially. Upon the discharge of capacitor 99
through discharge resistor 101, transistors 106 and 107 also turn
off. Control circuit 33 then starts generating gating pulses at a
safe minimum repetition rate and increases the repetition rate to
obtain the desired inverter output frequency at a rate determined
by the time constant of control capacitor 108 and the control
impedance of output frequency control circuit 41. During shutdown
of the induction cooking unit, when power is removed, the main
power supply filter capacitor 24 of course requires a few 60 Hz
cycles to discharge. As soon as the input voltage sensed by Zener
diode 90 drops to a low enough value, tranistors 97 and 95 turn on
to clamp control capacitor 108 to a voltage resulting in a low
repetition rate. At the end of the time delay, a clamping
transistor 107 conducts and inhibits further generation of gating
pulses. This controlled de-energization of the power circuit
controls the stopping transients, which could cause a commutation
failure.
Utensil presence detection circuit 44 lowers the repetition rate of
the gating pulses generated by voltage controlled pulse generator
46 to an audible level when the induction surface cooking unit has
no load. This is one way to annunciate to the user an operating
unit. In the event the audible annunciation is not desired an
alternate procedure is to reduce the output frequency to the lower
limit (18 kHz). This circuit is rendered operative by the sensing
of a power circuit parameter indicative of the absence of a utensil
coupled with the induction heating coil, in particular the high
initial reapplied forward voltage at the anode of thyristor 28. The
principle of operation of utensil presence detection circuit 44 is
that with no utensil load coupled to induction heating coil 15, the
inverter power circuit is essentially an undamped oscillatory L-C
circuit with little loss in the high frequency resonant circuit.
This means that commutating capacitor 27 (before the additional
charge supplied by reset inductor 31) charges negatively almost as
far as it does positively. By comparison, in the loaded case (see
FIG. 6b) the peak negative capacitor voltage at the end of the
conduction cycle is considerably less than the peak positive
capacitor voltage. Conversely, looking at the thyristor forward
voltage at the anode of the device as shown in FIG. 6c, the initial
reapplied forward voltage for the no-load situation illustrated in
full lines during the interval t.sub.1 is characteristically higher
than for the load situation shown in dashed lines. The induction
coil current is drawn in dot-dash lines for reference purposes.
Utensil presence detection circuit 44 recognizes the initial value
only of the reapplied thyristor anode voltage, and is operative in
response to the sensing of a predetermined voltage level indicative
of the absence of a coupled utensil to reduce the inverter output
frequency to a safe, low frequency.
Portions of utensil presence detection circuit 44 are identical or
similar to the thyristor overvoltage detection circuit 45
previously described. These are Zener diode string 71 (only one is
illustrated), resistors 72-75, protective diode 76, low pass filter
capacitor 70, and resistor 78 and transistor 79. The overriding
discharge circuit for control capacitor 108 includes a variable
resistor 77 in addition to resistor 78 and transistor 79. A
predetermined relatively high thyristor anode voltage, less than
needed to actuate Zener diode string 81, causes Zener diode string
71 to breakover and conduct to thereby turn on transistor 79 and
tend to discharge control capacitor 108. A monostable multivibrator
arrangement is used to inhibit transistor 79 so that it can become
conductive only during the relatively short time interval t.sub.1
(such as 4 microseconds) after the appearance of an initial high
reapplied forward voltage at the anode of the thyristor. The
monostable timing circuit (components 58-68) has a connection to
the anode of thyristor 28 and includes two normally conducting
transistors 63 and 68. Transistor 63 is ordinarily biased to the
conducting condition by the voltage across resistor 62, while
transistor 68 is biased by resistors 66 and 67. Capacitor 65 is
thus charged to approximately 15 volts, positive at the lefthand
plate. The collector of transistor 68 is near ground potential and
is connected directly to the base of transistor 79, thereby
clamping transistor 79 off.
When the thyristor anode voltage goes positive in each conduction
cycle due to the reapplied forward voltage, a reverse bias is
applied through resistor 58 and capacitor 60 to the base of
transistor 63, which turns off. Capacitor 65 is still charged,
however, and due to the fact that the positive plate is not coupled
to negative terminal 26 through resistor 64, the base of transistor
68 is driven sharply negative and turns off. During the ensuing
interval t.sub.1 before transistor 68 turns back on, the
overvoltage detection circuit comprising components 70 to 79 is
free to operate. As soon as transistor 68 turns off, capacitor 65
discharges through resistors 64, 66, and 67, and at the end of the
interval t.sub.1 transistor 68 is no longer reverse biased and
again turns on. The inhibiting of transistor 79 by the monostable
timing circuit with the exception of the time interval t.sub.1
occurs in each conduction cycle. During those cycles when the
utensil is not coupled with the induction heating coil, the initial
high reapplied forward voltage is sensed by Zener diode string 71,
as a result of which transistor 79 turns on during the interval
t.sub.1 in each conduction cycle and partially discharges control
capacitor 108. This arrangement overrides output frequency control
41 and reduces the inverter output frequency to the audible range,
where it can be heard by the user. The power output at the reduced
frequency is sufficiently low that there is little danger involved
in heating other metallic objects that may be inadvertantly placed
on the cooking surface. A small metallic object such as a spatula,
which has considerable area but is relatively thin, is a small load
for the inverter and does not prevent turning down the power by
operation of the utensil presence detection circuit.
In the foregoing discussion, the induction surface cooking unit is
in the watts control mode of operation in which control knob 21 on
the upstanding control panel of the range (FIG. 4) is adjusted to
obtain the desired heating level in the utensil. The watts output
is adjustable continuously, but control knob 21 can of course have
a scale with a series of spaced indications to which the user sets
the control knob to effectively achieve stepped control of the
watts output much as in the modern push-button range. To obtain
power outputs lower than that corresponding to the lower limit of
the ultrasonic frequency range (18 kHz), phase controlled
rectififer 13 is operated to reduce the d-c input voltage to
inverter 14. The gating circuit for the phase controlled thyristors
in rectifier 13 preferably has an adjustable resistor to select the
phase control angle, and this adjustable resistor is arranged with
user potentiometer 40 such that there is continuous control of the
output power. Alternatively, the induction surface cooking unit can
be used in the temperature control mode of operation in which the
other control knob 21' on the range control panel is associated
with a scale graduated in degrees representing a specific
temperature to which the utensil is to be heated. As was previously
mentioned, by way of illustration the temperature is measured by
means of a thermistor 19 (FIG. 3) removably attached to utensil 17
or 17' with a pair of wires that extend beneath utensil support 16
and have connection with gating control circuit 33. Specifically,
thermistor 19 is assumed to have a positive temperature coefficient
and is effectively connected in parallel with resistor 52 in output
frequency control 41 with an interlocking switch 127 to insert one
resistive element in the circuit and remove the other and vice
versa. A negative temperature coefficient thermistor is in similar
manner connected in parallel with resistor 54.
As is well known, thermistor 19 has a variable resistance depending
upon the sensed utensil temperature. For a positive temperature
coefficient thermistor, the resistance increases with increasing
temperature. The result is that the total amount of resistance in
the resistive voltage divider formed by thermistor 19,
potentiometer 40, and resistor 54 is now variable, rather than
being fixed as before. Assuming that the surface cooking unit and
thermistor 19 are properly calibrated, setting control knob 21' to
the desired temperature adjusts the position of the pointer along
potentiometer 40. When thermistor 19 senses a utensil temperature
lower than the set value, its resistance is also low. In the
voltage divider, the ratio of the resistance below the pointer to
that above the pointer is relatively high, so that control
capacitor 108 charges to a higher voltage thereby increasing the
repetition rate of the generation of gating pulses. Consequently
more power is coupled to the utensil and it heats up to a higher
temperature. Conversely, when thermistor 19 senses a higher utensil
temperature than is desired, its resistance is also relatively
high, and consequently the voltage on control capacitor 108
decreases. A reduced amount of power is coupled to the utensil and
its temperature decreases until an equilibrium is established
between the repetition rate of voltage controlled pulse generator
46 and the sensed temperature.
Conventional recipes for cooking food are expressed in relative
heating or cooking terms, or give a temperature to be set. Many
recipes call for high, medium, or low heat, or use widely known
cooking terms such as warm, simmer, and low boil. Other recipes
call for cooking at a particular specified temperature. It is
recognized that the watts control and temperature control modes of
operation of the induction surface cooking unit are used with
recipes that give instructions in this manner. Induction cooking
makes possible a new type of food cooking recipe in which the
instructions are given in terms of power levels to which the
cooking equipment is set, for example, heat at 500 watts for ten
minutes. The underlying principle of the new cooking technique is
that for the first time it is possible to measure the approximate
power actually coupled to the utensil and used by the utensil for
cooking the food, and is consistent and repeatable to use. Due to
the transformer relation between the utensil and the electronic
circuit in the cooking equipment, the power actually delivered to
the utensil is approximated by measuring the primary side power.
This requires the addition of a wattmeter or other power measuring
instrumentation to the surface cooking unit. To follow cooking
instructions specifying the watts setting, the user simply adjusts
the power level by turning control knob 21 to set the pointer of
the wattmeter at the watts level given by the recipe. The direct
setting of watts is also possible with the adjustment to that
setting being made automatically by the circuit. Further
information on this new method of cooking food and appropriate
instrumentation is given in the concurrently filed application,
Serial No. 212,058 by the same inventors, assigned to the same
assignee, entitled "Method and Equipment for Cooking Electronically
by Specifying Watts Setting."
Electrical and Magnetic Characteristics of Solid State Cooking
Systems
The solid state induction cooking units herein described have a set
of interlocking or matching electrical and magnetic characteristics
that combine to produce cooking appliances with new and improved
features as compared to prior cooking equipment whether based on
induction heating or some other principle. The new cooking
appliances are unique in that the cooking surface is cool to the
human touch even immediately after removing a heated utensil from
the surface. The magnetic flux of course does not directly generate
heat in the non-metallic or non-conducting utensil support plate
16, and as was previously mentioned the utensil temperature at no
time rises above 450.degree.-500.degree.F. Consequently, it is
possible for the first time to use plastic counter-top cooking
surfaces. The magnetic field distribution of the flat or nominally
flat induction heating coil 15 is such that the utensil is heated
relatively uniformly without excessive temperature gradients in the
utensil bottom or localized hot spots corresponding to the burner
or coil positions in conventional gas and electric ranges. An
important feature to the user is the complete, unrestrained freedom
to move the utensil on the cooking surface, as when stirring. The
pondermotive forces at ultrasonic frequencies are insignificant,
and there are further no attraction forces of a mechanical nature
between the utensil and support plate since it is not necessary
that there be optically flat surfaces to promote the transfer of
heat as in some of the glass-ceramic resistance heated tops. When
using a 60 Hz a-c voltage source, it is necessary to provide a
well-filtered d-c input voltage to the inverter to prevent
vibration of the utensil due to a 120 Hz modulation of the power
coupled to the utensil. The ultrasonic operating range is selected
primarily to make the cooking unit inaudible to the user, but an
added advantage of this frequency range is that the skin depth of
induction heating at these frequencies makes possible the use of
relatively, thin, light weight utensils. By comparison, at 60 Hz
the skin depth is much thicker and requires the use of relatively
heavy, thick utensils in order to take advantage of the full
heating capacity of the alternating magnetic field. The use of
relatively thin, efficiently heated utensils provides for fast
warm-up and quick response to changes in heating levels.
There are several important physical and electrical constraints to
be observed in the construction of a practical solid state
induction surface cooking unit. An obvious constraint is the
outside diameter of induction heating coil 15, which must transfer
the required power to the utensil yet have a maximum diameter
suitable for use with ordinary sized pots and pans, and yet not
interact with adjacent coils or other pans. A diameter of 6-12
inches is appropriate for a variety of different sizes of utensils.
A similar type of constraint is the range of impedances of ordinary
utensils. Efficiency of power transfer to the load is promoted by
source-to-load impedance matching, but the situation here is that
the input circuit impedance is fixed if minimum cost is to result.
This is because the utensil bottom functions as a single turn
secondary winding, and the primary side supply voltage is fixed at
120 or 240 volts, 60 Hz, from which it follows that the primary
side impedance is also fixed. This dictates certain impedance
matching characteristics in the power conditioning equipment. It is
possible for the primary side power converter to include an
impedance matching transformer, however none is used in the
converter shown in FIG. 5 in order to reduce the number of
components and the cost of the circuit.
A critical constraint in the construction of solid state induction
surface cooking units are the limits of the feasible ultrasonic
high frequency range, namely, 18 kHz at one end and 40 kHz at the
other. As has been mentioned, the upper limit of 40 kHz is
determined by economic considerations in conjunction with the high
frequency limitations of available power semiconductors with
sufficient current carrying capacity to deliver the required power
for a full range of cooking tasks. At higher frequencies, moreover,
the rfi filtering problems are increasingly difficult and costly,
making compliance with government communication agencies more
difficult. In domestic appliances, this power output range is from
2500 watts to 50 watts for the full spectrum of cooking tasks from
extremely rapid heating and boiling, on one hand, and warming
easily burned foods such as rice, on the other hand. In FIG. 8 the
feasible ultrasonic frequency range, 18-40 kHz, is plotted against
the required power range for successful cooking, 50-2,500 watts.
The area or "window" that is created is in a pictorial manner the
defining condition for successful solid state induction cooking. A
power range of 2,500-50 watts is a 50:1 control range and this must
be obtained within the limitations that the operating frequency can
only be between 18 and 40 kHz. Some ranges and cooktop units, of
course, use only a portion of this frequency range above 18 kHz,
for example, 18-30 kHz, and do reasonably good cooking with a power
range of 12:1 or 15:1, for example, 1,200-100 watts. Food warming
appliances require a much more limited power and frequency range.
Some induction cooking inverter circuits such as a parallel
resonant inverter may operate at a single operating frequency and
vary the output power over a limited range in some other manner.
The "window" concept of FIG. 8 is intended to encompass all of
these and to convey the interpretation that domestic solid state
induction cooking is carried out within these power limits and
frequency limits. For general cooking, a power range of at least
10:1 up to 50:1 is needed.
Among the characteristics of a solid state inverter for induction
cooking appliances, in addition to being operable within at least a
portion of this frequency range, are that it be capable of being
inhibited, started and stopped without issuing audio information.
The inverter must be controlled by a control element that is easily
operated by a non-technical user, and the inverter must not fail
when the control element such as user potentiometer 40 is slewed,
that is changed rapidly from one setting to another. In considering
the requirement for a wide range of output power, such as 10:1 to
50:1, the two general types of idealized wave shapes which can be
utilized are illustrated in FIGS. 9 and 10. FIG. 9 is recognized as
the non-symmetrical sinusoidal wave shape produced by the
single-thyristor series resonant inverter such as that shown in
FIG. 5, but inverters that produce symmetrical sinusoidal current
pulses are also suitable. The time delay interval t.sub.2 between
discrete sinusoidal pulses is made as small as possible but cannot
be reduced to zero to assure reliability of the thyristor
commutation, especially in view of the variety of loads to be
heated. The output power is modulated by widening the interval
t.sub.2 until limited by the threshold of audio frequencies, and by
supplying a variable d-c input voltage which lowers the peak
amplitudes of the waves. In a perfectly linear system in which the
power is controlled only by changing the operating frequency, a 2:1
power range is achieved with the upper limit at 36 kHz, a 10:1
power range with the upper limit at 180 kHz, and a 30:1 range with
the upper limit at 540 kHz. The latter two situations are clearly
impractical. The desirable one-thyristor series resonant inverter
of FIG. 5, which generates a amplitude current pulse as the
operating frequency is increased, produces a power-frequency
characteristic such as is shown by the solid line curve in FIG. 11.
A power range in the order of 5:1 to 7:1 is obtained, and to obtain
a power output below about 400 watts, it is necessary to use some
other power control technique such as varying the d-c input
voltage, changing the commutation circuit parameters, making use of
pulse width modulation techniques, etc. The full range
power-frequency characteristic shown in dashed lines in FIG. 11 is
the one ideally sought after. It will be noted that solely changing
the d-c input voltage usually does not obtain the wide range power
control. In FIG. 7, by way of example, low input voltage detection
circuit 43 is operable at 90 volts for a normal d-c input voltage
of 150 volts.
Another suitable system for obtaining wide range power control is
to use an inverter that produces square or rectangular wave shapes
such as is shown in FIG. 10. The power is controlled by the pulse
width modulation technique, by decreasing the width of each pulse
to produce lower power outputs. The narrower pulses have increased
harmonic content, but this occurs at decreased power levels, and
therefore the ability of the system to deal with increased harmonic
content is favorable. Pulse width modulation can be combined with
the frequency deviation technique for wide range power control.
Some of the magnetic characteristics of induction cooking systems
will be discussed with regard to FIGS. 12-15. Referring to FIG. 12,
the resistivity of metals increases with increasing temperature,
thus producing greater power losses in the utensil. This is a
favorable situation from the standpoint of power control and
impedance matching. The utensil or power receptor magnetic material
must be one that has a Curie temperature in excess of about
500.degree.F, which has been established as being the maximum pan
bottom temperature in induction cooking. At the Curie temperature
there is a change in permeability with a resulting poorer, less
efficient coupling to the induction heating coil. The condition of
a substantially constant permeability at least until 500.degree.F
is shown in FIG. 13. The induction cooking system may or may not
make use of the full B-H hysteresis loop of the magnetic material
depending on the nature of the ultrasonic generator and the extent
to which it may produce a non-symmetrical wave shape. Minor loop
operation results from the use of a converter such as that in FIG.
5 with an asymmetrical current pulse output. This is illustrated in
FIG. 14. The dashed line hysteresis loop is a completely
symmetrical minor loop, while the full line asymmetrical loop
within it is produced by an asymmetrical cooking system such as
FIG. 5. The d-c loop is shaded.
The skin depth of inductively heated magnetic materials at
operating frequencies of 18 to 40 kHz is such that full advantage
can be taken of the induction heating phenomenon while still using
relatively thin utensils. The proper choice of material is governed
by an understanding of the process of heating in utensil 17 or
receptor plate 18. The depth of penetration is generally give as
being proportional to the square root of resistivity divided by the
relative permeability times the frequency. Thus, the depth of
penetration varies with the square root of frequency and is
dependent both on resistivity and the magnetic property
characteristics of the material. Some typical metal thicknesses may
be of help in understanding the numbers involved. For 52S aluminum
the depth of penetration at 25 kHz is approximately 0.030 inches
while for copper it is approximately 0.016 inches. Since the
magnetic properties do not enter into the choice of these material,
the only thing that has to be considered then is the resistance
coefficient as a function of temperature which is positive and
essentially linear for the materials. By contrast, the depth of
penetration for iron and steel is in the order of 5.7 mils at 25
kHz. Skin depth should be less than the utensil or power receptor
thickness for most efficient heating. The utensils at these
operating frequencies can be relatively thin, but are efficiently
heated so that there is fast warm-up and fast response to changes
in the power level. In general, the thickness of the magnetic
material is no less than the skin depth, but can be up to several
times greater. As here used, lightweight magnetic utensils are
considered to have a thickness of about 25-50 mils. Referring to
FIG. 15, the amount of power coupled to non-magnetic utensils and
receptors such as aluminum or copper is a function of thickness and
has an optimum value. For the frequency range of interest, the
power is most efficiently coupled to the utensil when it has a
thickness of about 0.5 mils, the thickness of aluminum foil, and
there is very poor coupling at thicknesses of less than 0.1 mil and
greater than 2 mils.
Some of the other types of inverters and d-c power supplies that
can be used are illustrated in FIGS. 16-18. In addition to the
one-thyristor series resonant circuit in FIG. 5, other
one-transistor, two-thyristor, and two-transistor series and
parallel resonant inverters and multicylinder inverters can be used
in constructing induction surface cooking units. FIG. 16 shows a
four-transistor full bridge inverter suitable for generating the
pulse width modulated square wave shapes shown in FIG. 10. Each
pair of opposite transistors is turned on and off for a variable
amount of time to modulate the output power. In this inverter the
transistors directly supply power to induction heating coil 15
which is connected across opposite junctures of the bridge, the
other two opposite junctures being connected to d-c input terminals
25 and 26. FIG. 17 shows the same circuit with the addition of an
impedance matching transformer 140 between the transistor bridge
and induction heating coil 15. The preferred arrangement shown in
FIG. 5 does not use an impedance matching transformer but it may be
required in some circuits where the primary side impedance cannot
in some other manner be matched to the fixed secondary side with
the single turn secondary winding and fixed load presented by
utensil 17. FIG. 18 shows two additional ways, other than using a
phase controlled rectifier, for reducing the input voltage to
achieve wide range power control. The first involves phase
controlling the a-c input voltage by connecting a solid state triac
device 141 between input terminal 22 and one of the inputs to full
wave diode bridge rectifier 13. Triac device 141 is a bidirectional
conducting thyristor that can be phase controlled for each polarity
of the supply voltage in the same manner as a silicon controlled
rectifier. The other technique (only one is used in a given
circuit) is to use a chopper or time ratio control circuit 142 to
reduce the magnitude of the filtered d-c voltage produced by the
full wave diode rectifier 13 and filter network 24', 24. In this
known d-c to d-c conversion circuit, the ratio of on-time to
off-time of a thyristor 143 varies the voltage across an auxiliary
d-c supply capacitor 144, across which the d-c input terminals 25
and 26 for the inverter are taken.
Block Diagrams of Complete Solid State Induction Cooking
Systems
FIG. 19 shows the block diagram of a generalized solid state
induction cooking system including some features that are optional
depending upon the particular model of the electric range or
cooktop unit. In view of the extensive foregoing discussion, it is
believed only a minimum number of remarks need be made by way of
further explanation. As important point, however, is that the
foregoing circuits are illustrative of the practice of the
invention, and other circuit approaches can be used to obtain the
same function. Moreover the functional components can be
interrelated in a different manner that has been specifically
shown. In these block diagrams the functional components that are
readily identifiable and have the same functional relationship to
the other components as they do in FIGS. 1-7 are identified by the
numerals. Additional components and functional units not previously
designated by a separate numeral are identified by new numerals. In
FIG. 19 the energy source is a generalized alternating or direct
voltage source. The application of power to static solid state
power conversion circuit 12 by the closing of switch or contactor
21 is displayed to the user by a load indication means such as the
indicator light 20 in FIG. 4. Switch or contactor 21 also energizes
the start-up circuit means 150 which acts through an inhibit 151 to
control static solid state power conversion circuit 12. In gating
control circuit 33, FIG. 7, the start-up circuit is provided by the
operation of low input voltage detection circuit 43, and the
inhibit circuit function is provided by clamping transistor 107 and
its operating circuitry. Start-up circuit means 150 controls the
starting transients and assures the safe and controlled application
of power to the load coupling means or induction heating coil 15.
Load receptor means 18 can be provided by the bottom of utensil 17,
which is the load, or by a separate plate 18 embedded in the
utensil as shown in FIG. 3. Output power adjustment means 153 is
the watts control that adjusts the power level or heating level,
and this component also acts through inhibit circuit 151 to control
or shut down static solid state power conversion circuit 12 under
certain conditions, as when a maximum output frequency is exceeded.
It is essential in solid state equipment to provide a device
protection means 154 to assure proper functioning of the
circuit.
A fan or other cooling means 155 for static power converter 12 and
load coupling means 15 may or may not be needed depending upon the
amount of heat generated by the solid state circuit and the coil,
as well as such considerations as packaging. The load presence
means 44, which need not be identical to the utensil presence
circuit 44 disclosed in FIG. 7, is clearly an optional feature that
is desirable from the standpoint of ease of operation in reducing
power consumption and user safety, but is not essential to a low
cost model. The temperature regulating means or temperature control
156 is also an optional feature that is provided only on deluxe
models. As is indicated by the dashed lines, the type of
temperature control here disclosed senses the temperature by means
of thermistor 19 (FIG. 3) and operates to change the heating level
by means of output power adjustment means 153 to obtain the
temperature set by control knob 21'. The temperature control
function is also obtained by operating through inhibit circuit 151
to selectively and temporarily inhibit operation of static power
conversion circuit 12. Either an on-off temperature control system
can be used or a proportional mode system that permits current flow
for a variable number of cycles while inhibiting power generation
for the remainder of a base interval. An on-off temperature control
system using a thermostat to control the static power converter is
disclosed in aforementioned application Ser. No. 200,526.
FIG. 20 is a block diagram of a solid state induction cooking
system in which the energy source is the utility power supply and
which uses an inverter 14 constructed with thyristor devices. The
energy source is a 60 Hz, 120 or 240 volt source of a-c voltage.
Although not heretofore mentioned, the same cooking system can be
used with 50 Hz supply common in Europe in view of the ability of
rectifier 13 to rectify any input supply voltage regardless as to
the frequency. Similarly polyphase or single phase power can be
utilized. Surge protection circuit 130 and RFI filter 131 function,
as was mentioned in the discussion of FIG. 5, to respectively
protect the cooking system from power supply surges, and to prevent
high frequency disturbances in the utility power supply caused by
the operation of the cooking unit. Input voltage control means 157
is obtained, for instance, by using a phase controlled rectifier or
by using one of the alternative circuits shown in FIG. 18 for phase
controlling the input voltage by means of a triac or chopping the
filtered d-c voltage by means of a time ratio control circuit. An
optional feature is a current or power indicator 158, in the form
of an ammeter or wattmeter on the upstanding range control panel
(FIG. 4) to display the state of the circuit to the user. The power
indicating instrument is required if the range or surface cooking
unit is to be equipped with the ability to cook using recipes that
specify the watts setting, as previously explained.
An impedance matching means 140 such as impedance matching
transformer 140 (FIG. 17) may be required to some circuits to match
the primary side impedance to the fixed secondary side impedance
for the reasons given previously. It may also be desired to have an
impedance switching scheme to obtain efficient power coupling over
a greater load range. Gating circuit 159 is here shown as a
separate functional unit. Components 150-154 and 44 have the
functional relationship to gating circuit 159 as is used in
implementing gating control circuit 33, FIG. 7. The temperature
regulating means 156 is again an optional feature.
FIG. 21 is a similar block diagram of a solid state induction
cooking system that operates from a battery or other direct voltage
supply and uses an inverter implemented with power transistors.
Transistor devices, of course, do not require a commutation
circuit. In view of the similarity to FIG. 20, it is believed that
no further comments are needed. It is noted, however, that a filter
network 24, 24' is still needed to assure a well-regulated source
of d-c input voltage for inverter 14.
FIG. 22 is a logic type of block diagram for a generalized solid
state induction cooking system. It is another way of presenting
much of the material given in FIGS. 19-21. As in gating control
circuit 33, FIG. 7, the output frequency of static solid state
conversion circuit 12 is determined by a master voltage controlled
oscillator 165. The various logic inputs that determine the
repetition rate of master voltage control oscillator 165 are
combined in a summing circuit 166. Summing circuit 166 is in the
form of an operational amplifier equipped for addition by means of
a resistor between the amplifier output and input, and another
resistor connected between this same amplifier input and the source
of logic signals. The two types of logic signals are the control
advance signals that normally operate to increase the repetition
rate of master oscillator 165, and the control retard logic signals
that ordinarily operate to decrease the repetition rate. The system
is energized by means of user input No. 1 which operates on-off
switch 21. The start logic signals are controlled by user input No.
2, and this is the only type of control advance logic applied to
summing circuit 166.
The various control retard logic signals are combined in a second
summing circuit 167 and applied to the first summing circuit 166.
The control retard logic includes start logic, stop logic,
temperature control logic, watts control logic, user safety logic,
and circuit protection logic. The start logic can also operate to
retard master oscillator 165 if the proper starting conditions are
not present, such as insufficient input voltage to assure enough
commutation energy in the commutating capacitor for proper
operation of the inverter. The user safety logic can be provided,
for instance, by utensil presence detection circuit 44, since this
circuit automatically turns down the power output of static power
converter 12 when there is no utensil coupled with the load
coupling means (coil 15). Consequently, miscellaneous metallic
objects that are inadvertantly placed on the cooking surface, such
as jewelery, spatulas, or other small food preparation implements,
are not heated to high temperature that could be dangerous to the
user. Specific types of circuit protection logic were explained in
detail with regard to FIG. 7, and include protection against a low
supply voltage, a high active device voltage, insufficient
commutation energy, and lack of proper gate drive. These different
types of control retard logic signals are combined in summing
circuit 167 such that any one of them, or their combined effect,
causes a reduction in the repetition rate of master oscillator
165.
The output power of static power converter 12 is also reduced
independently by the input voltage control technique. User input
No. 3 operates the input power retard logic, which in turn directly
controls the input voltage control, the watts control logic, and
temperture control logic.
In summary, solid state induction surface cooking units for
domestic ranges and other cooking appliances incorporate unique
induction heating systems that have been described with emphasis on
the operating parameters and functional features that enhance their
acceptability for mass usage by assuring reliable and convenient
operation. These new cooking appliances are based on inter-related
electrical and magnetic characteristics that achieve improved
appliances with a good looking, easy to clean, cool cooking surface
which for the first time can be made of plastics as well as other
non-metallic materials. Other desirable user features are
consistent performance, fast warm-up of lightweight utensils,
responsive heating without temperature gradients, and complete
freedom to move the utensil without restraint. In addition to
cooking by adjusting the relative heating level, induction ranges
and surface cooking units when properly equipped perform cooking by
setting the utensil temperature and for the first time by setting
the utensil power level.
While the invention has been particularly shown and described with
reference to several preferred embodiments thereof, it will be
understood by those skilled in the art that the foregoing and other
changes in form and detail may be made therein without departing
from the spirit and scope of the invention.
* * * * *