U.S. patent number 3,754,160 [Application Number 05/193,449] was granted by the patent office on 1973-08-21 for four-lamp driver circuit for fluorescent lamps.
This patent grant is currently assigned to Radiant Industries, Inc.. Invention is credited to Stephen A. Jensen.
United States Patent |
3,754,160 |
Jensen |
August 21, 1973 |
FOUR-LAMP DRIVER CIRCUIT FOR FLUORESCENT LAMPS
Abstract
A two-transistor, high-frequency, non-saturating inverter for
operating four fluorescent lamps connected in a series-parallel
arrangement. The inverter is supplied either directly from a DC
source, or from an AC source via a full-wave bridge rectifier.
Transient supression, power-factor correction, and load-balancing
networks are provided. Failure or removal of any one lamp will
leave two lamps operating in a fail-safe mode.
Inventors: |
Jensen; Stephen A. (North
Hollywood, CA) |
Assignee: |
Radiant Industries, Inc. (North
Hollywood, CA)
|
Family
ID: |
22713684 |
Appl.
No.: |
05/193,449 |
Filed: |
October 28, 1971 |
Current U.S.
Class: |
315/97;
315/DIG.2; 315/DIG.7; 315/257; 315/297; 315/324; 331/113A |
Current CPC
Class: |
H02M
7/53846 (20130101); H02M 5/458 (20130101); H02M
7/53862 (20130101); Y10S 315/07 (20130101); Y10S
315/02 (20130101) |
Current International
Class: |
H02M
7/5383 (20060101); H02M 5/00 (20060101); H02M
5/458 (20060101); H03k 003/30 (); H05b
041/29 () |
Field of
Search: |
;315/96,97,205,254,257,297,324,DIG.2,DIG.5,DIG.7 ;331/113A |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Lake; Roy
Assistant Examiner: Grimm; Siegfried H.
Claims
What is claimed is:
1. Apparatus for energizing a plurality of
hot-cathode gaseous-discharge lamps, comprising:
rectifier means having a pair of input terminals for receiving
operating potential for said apparatus, and having a pair of
direct-current output leads;
means connected to said output leads for changing the
direct-current therefrom to an alternating current having a
frequency which is substantially higher than the frequency of said
operating potential applied to said input terminals;
a first pair of series-connected lamps;
a second pair of series-connected lamps;
means connecting one terminal of each of said pairs of lamps in
common to one alternating-current output terminal of said current
changing means;
current dividing means having an input connected to the remaining
alternating-current output terminal of said current changing means
and having a first output connected to the other terminal of said
first pair of series-connected lamps, and a second output connected
to the other terminal of said second pair of series-connected
lamps, for dividing the current from said current changing means
equally between the two pairs of series-connected lamps;
said current changing means comprises:
a saturating two-transistor inverter;
said inverter includes:
an autotransformer having a continuous multi-tap winding, one end
of said winding corresponding to said one alternating-current
output terminal and the other end of said winding corresponding to
said remaining alternating-current output terminal; and
first and second resistance-capacitance coupled timing network
means, each connected between a corresponding one of said two
transistors and said autotransformer, for cyclically transferring
conduction between said two transistors at a rate which is
independent of variations in the magnetic circuit of said
autotransformer.
2. Apparatus as defined in claim 1 including:
first and second transient suppression network means, each
connected to a corresponding one of said two transistors, for
preventing spurious transient voltages from being reflected from
said autotransformer to their respective transistors.
3. Apparatus as defined in claim 1 wherein
each of said lamps includes:
a pair of spaced-apart heaters; and, said autotransformer
includes
a plurality of low-voltage windings, inductively coupled to said
continuous multi-tap winding, each of which is operatively
connected to a corresponding one of said heaters.
4. Apparatus for energizing a plurality of
hot-cathode gaseous-discharge lamps, comprising:
rectifier means having a pair of input terminals for receiving
operating potential for said apparatus, and having a pair of
direct-current output leads;
means connected to said output leads for changing the
direct-current therefrom to an alternating current having a
frequency which is substantially higher than the frequency of said
operating potential applied to said input terminals;
a first pair of series-connected lamps;
a second pair of series-connected lamps;
means connecting one terminal of each of said pairs of lamps in
common to one alternating-current output terminal of said current
changing means;
current dividing means having an input connected to the remaining
alternating-current output terminal of said current changing means
and having a first output connected to the other terminal of said
first pair of series-connected lamps, and a second output connected
to the other terminal of said second pair of series--connected
lamps, for dividing the current from said current changing means
equally between the two pairs of series-connected lamps;
said current dividing means comprises:
first and second windings having a 1:1 ratio and inductively
coupled in opposition to a common electromagnetic circuit, one end
of each of said windings being connected in common to said current
changing means and the remaining ends of said windings being
connected to respective pairs of said series-connected lamps.
5. Apparatus as defined in claim 4 wherein
said rectifier means comprises:
a full-wave diode bridge rectifier, thereby permitting both
alternating-current and unpolarized direct-current to properly
function as said operating potential.
6. Apparatus as defined in claim 4 including:
capacitive reactance means connected across said remaining ends of
said windings of said current dividing means.
Description
BACKGROUND OF THE INVENTION
As is well known, hot cathode gaseous-discharge lamps, commonly
referred to as "fluorescent lamps" are characterized by a
relatively high impedance prior to being started or ignited, and a
substantially lower impedance once ignition is established. Thus, a
higher voltage is required to ignite the lamp than is required to
maintain its operating state. Various means have been provided
heretofore which are capable of providing the relatively high
ignition voltage necessary, and thereafter limit the operating
current once the lamp is ignited. As a class, these devices are
called lamp ballasts and comprise a wide variety of circuit
devices.
Multiple lamp ballasts are available for operation of a plurality
of lamps from a common 60 H.sub.z commercial power supply. These
ballasts allow operation of fluorescent lamps at a current
frequency equal to the commercial main frequency; usually 60
H.sub.z. Such ballasts suffer from various shortcomings, including
audible noise, heavy weight, and low efficiency compared to that
available with high frequency lamp operation. Attempts to utilize
high frequency static inverters to overcome these shortcomings have
met with difficulties concerning switching losses in power
transistors when operating at frequencies above the audible range
and at the power levels required for the application. These losses
are aggravated by the fact that most inverters utilize a saturating
magnetic core to determine the period of oscillation of the
inverter. At the time of switching, a large peak current flows in
the collector of the conducting transistor as a result of the
saturation of the core. The duration of this current is as long as
the transistor storage time and is generally a significant period
of time compared to a period of oscillation. This results in
excessive heating of the transistors and generally renders such
circuits impractical to operate reliably in the environment
afforded by a typical fluorescent light fixture.
The present invention combines a novel and improved solid state
inverter which drives a plurality of fluorescent lamps and an
operating frequency that is above the audible range. This is
accomplished by means of a nonsaturating type inverter which avoids
the current peaks discussed earlier. By operating at above audio
frequencies, the efficiency of fluorescent lamps is substantially
improved over that achieved at 60 H.sub.z. This results in less
power consumption for a given unit of light output than that
achieved by conventional ballasts. The non-saturating inverter
circuit described herein yields such high efficiency as to allow
reliable operation in high temperature environments such as those
found in recessed fluorescent fixture.
BREIF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a block diagram illustrating an embodiment of the
invention for driving four fluorescent lamps from a commercial AC
power source.
FIG. 2 is a schematic circuit diagram of the system shown in FIG.
1.
DESCRIPTION OF THE PREFERRED EMBODIMENT
There is shown in FIG. 1 a block diagram of a four-lamp driver
designed to operate directly from a conventional 115 volt, 60 Hz,
AC power source. The input power is applied across terminals 1 and
2 which energizes the AC to DC converter 1. In a typical
construction, converter 1 may comprise a full-wave rectifier with a
suitable smoothing filter. The positive output voltage on line 4,
and the negative output voltage on line 5, are supplied to a
non-saturating, two-transistor inverter comprising transistors Q1
and Q2. The inverter is provided with a pair of
transient-suppression networks 6 and 7, and a pair of timing and
speed-up networks 8 and 9. The inverter serves to convert the 160
volt peak DC from converter 1 to an AC voltage having a nominal
frequency of 20 KHz. This arrangement makes the system insensitive
to the main power supply frequency applied to terminals 1 and 2,
which may for example range from 50 Hz to 1,000 Hz. Optionally, the
system may be connected directly to a 130 volt DC power source
(without regard to polarity) at terminals 1 and 2.
Transistors Q1 and Q2 function essentially as switches to produce a
square-wave output which is supplied via networks 8 and 9,
respectively, to the input winding of autotransformer 11 via lead
10. Initial application of power to terminals 1 and 2 produces a DC
voltage on lines 4 and 5 which establishes a forward bias on the
collector-emitter junctions of both Q1 and Q2. Transistor Q1 will
then be biased into conduction by base current flowing through the
timing network 8 into the base of Q1. This incipient conduction
causes Q1 to be regeneratively switched into "hard" conduction with
the supporting base drive obtained via the input winding of
autotransformer 11 (lead 10) and the speed-up network 8.
As conduction continues in Q1, the capacitive element of network 8
charges and causes the base current at Q1 to decay until Q1 stops
conducting. This action takes place prior to saturation of the core
of autotransformer 11, thereby obviating high peak currents and the
losses resulting from core saturation.
When Q1 stops conducting, the emitter voltage of Q1 will drop and
the voltage to the second winding (via line 20) on the
autotransformer will become zero. Conduction will then commence in
Q2 until this half of the cycle is terminated by the action of
network 9. All timing is dependent upon the properties of the
networks 8 and 9, rather than the properties of the
autotransformer. The resulting square-wave applied to the
autotransformer produces an output voltage which is four times the
peak AC line voltage at terminals 1 and 2. If, for example, the
input supply is 160 volts peak-to-peak, then the high voltage
available to the lamp circuit is 640 volts peak-to-peak. This high
voltage is then impressed across lamps 12-15, which are connected
in a series-parallel arrangement (as will be described more fully
hereinafter).
The functions of the networks 8 and 9 are several-fold. Their first
purpose is to supply base current to whichever transistor (Q1 or
Q2) is then in conduction, and to cause the base current thereto to
diminish to a value below which conduction cannot be sustained in
the initially conducting one of the transistors. Additionally, each
of these networks (8 and 9) functions to strongly reverse bias its
associated transistor immediately upon cessation of conduction
thereof, so as to positively define the cut-off point and to insure
repeatability. This further insures that no collector current can
flow in the associated transistor once its conduction has been
terminated. In this way, the possibility of current flowing in both
transistors simultaneously, is eliminated.
Unlike conventional saturating-core type of inverters, this circuit
precludes large peak currents flowing through the transistors. The
result is an increase in efficiency and a reduction in overall heat
rise.
Transient suppression networks 6 and 7, previously referred to,
serve to block any spikes or spurious voltage transients which
might be reflected from the autotransformer 11 during the ignition
of the lamps 12-15. Also, these networks (6 and 7) protect the
inverter transistors under a no-load condition such as would occur
if all of the lamps were to be removed from the circuit while the
power is on. This condition produces a reflection from the output
having large voltage transients which would otherwise damage the
transistors by raising the collector-to-emitter voltage (in the
cut-off condition) beyond their rated value. Such transients are
absorbed by networks 6 and 7 and are passive during normal
operation of the circuit.
Autotransformer 11 has a single continuous winding with a plurality
of taps, the individual functions of which will be explained in
detail in connection with the description of the schematic diagram
of FIG. 2. In general, however, these taps provide base drive to
transistors Q1 and Q2, and base current to networks 8 and 9.
Additionally, the aforementioned 640 volt peak-to-peak square wave,
from which the lamp operating power is derived, is obtained from
autotransformer 11.
The circuit is designed to utilize so-called "rapid start" lamps
(12-15). This type of lamp is provided with electrodes which are
continously heated during lamp operation. The hot electrodes (viz.,
cathode) permits somewhat greater lamp current to be utilized and
produces lower overall lighting costs in addition to the
convenience of a rapid-start feature. The autotransformer 11 is
provided with winding taps that continuously provide the required
voltage and current for heating of heaters 16-19 and 21-24. When
the system is energized, these winding taps cause the electrodes to
be quickly heated, releasing enough electrons within the
fluorescent lamp for an arc to be established in response to the
application of the high voltage from the high-voltage taps.
The voltage from the high-voltage taps is impressed across the
series-parallel four-lamp load through the load-balancing network
25, which serves to uniformly divide the current between the lamps
12-15, and to limit the maximum current to conform to the
specifications (viz., manufacturer's ratings) of the lamps. Since
the light output is directly proportional to the current flowing
through each lamp, equal division of the available current among
the four lamps will assure uniform operating brilliance. Further,
the network 25 optimizes the power factor by limiting the peak
current demand of the lamp load to a point in the operating cycle
other than the time at which switching of the transistors Q1 and Q2
occurs. This results in a substantial improvement over the
capacitive ballast technique of the prior art wherein the peak of
the current load coincides with the point in time of the operating
cycle at which switching takes place. When the transistors switch
under conditions of high load current, they necessarily dissipate
more power than they would if they were switching under low load
currents.
Incorporation of the network 25 into the novel circuit of the
present invention causes the current into the load to be very near
zero at the moment when there is a switching transition between
transistors Q1 and Q2. The peak current load occurs approximately
one-quarter of the way into the corresponding half-cycle of the
inverter operation.
There is shown in FIG. 2 a more detailed diagram of a preferred
embodiment of the invention. As in the previous description of the
apparatus of FIG. 1, the operating power is applied to input
terminals 1 and 2. The applied alternating current is rectified via
the full-wave bridge comprising diodes 26-29. Filter capacitor 31
(C1) smooths the DC which comprises the operating potential for the
inverter.
In order to follow a typical cycle of operation, assume as the
initial condition that transistor Q1 is biased into conduction by
the base current flowing through resistor R6 into the base of Q1.
Additional base drive is supplied from winding W1 of
autotransformer 11 via capacitor C2 and resistor R1 and conduction
proceeds regeneratively to saturation of transistor Q1. This action
will cause capacitor C2 to charge to the level of the voltage drop
across resistor R1. The increasing voltage across capacitor C2 will
cause the base current of transistor Q1 to decay towards 0.
Some of the base current is bled off through diode CR2 and series
resistor R2, thereby causing the base emitter voltage of transistor
Q1 to sharply pass through 0 volts. This action assures a
well-defined cut-off of transistor Q1.
Diode CR1 is connected between the emitter and the base of
transistor Q1. During each cycle when the transistor is cut off, it
limits the maximum emitter base voltage to the threshold voltage of
the diode, slightly less than 1.0 volt. Otherwise, the full driving
voltage from the feed back coil would appear across that emitter
base and could punch through. During the conduction of the
transistor, the diode is reversed biased or cut off since polarity
from base to emitter has been reversed in order to permit
conduction of the transistor.
The above-described regenerative-conduction to cutoff cycle of
transistor Q1 occurs before saturation of the core of
autotransformer 11 can take place. When transistor Q1 stops
conducting, the emitter voltage will drop as will the voltage
across winding W3. Similarly, the voltage across winding W6 will
also go to 0. Inasmuch as winding W6 had been providing a cutoff
bias for transistor Q2 during the initial portion of the operating
cycle, its termination will permit the network comprising capacitor
C3 and resistor R4 to forward bias the base-emitter junction of
transistor Q2. Incipient conduction of transistor Q2 will establish
a positive-going voltage across winding W4, and hence winding W6
also.
This action will sustain a regenerative half-cycle in the same
manner as described previously in connection with transistor Q1.
Specifically, the build-up of a charge on capacitor C3 will
ultimately reach a level where it will cause reverse biasing of the
base of transistor Q2.
Diode CR3 and CR4, and resistor R3 perform similar functions to
respective counterpart components CR2 and CR1, and R2 previously
described.
A new cycle of operation commences and transistors Q1 and Q2
function as alternately conducting switches applying the supply
voltage from rectifier 3 to windings W1 and W6. The square-wave
train produced, generates four times the peak AC line voltage
across the overall winding (W1 through W6) of autotransformer 11.
This total voltage is connected across the series-connected pairs
of lamps 13,15 and 12,14.
The previously described transient-suppression networks comprise
diodes CR5 and CR6, capacitors C6 and C7, C8 and resistor R5.
Capacitor C4 is connected in series between one terminal of
autotransformer 11 (at winding W1) and current transformer T1. This
capacitor (C4) functions as a current limiter for the total current
flowing to all four lamps 12-15, by virtue of its capacitive
reactance. Transformer T1 has a 1:1 winding ratio and is connected
so that the two windings are bucking. Thus, if one pair of lamps
ignites prior to the remaining pair, the resulting current flow
through one winding of the transformer T1 will generate a voltage
in the other winding which is additive to the voltage at the
junction of capacitor C4 and the tranformer T1. This increased
voltage will insure the ignition of the other pair of lamps.
A second function of transformer T1 is to provide an
inductive-reactance component to the lamp load. This is obtained by
using the leakage reactance which appears as a series element in
the lamp current path. In the time domain, this arrangement results
in the inverter being lightly loaded during the actual switching
portion of the operating cycle, thereby minimizing switching
losses. The current peak, which would otherwise occur at the
instant of switching, is delayed to a point in time which is about
25 percent into the half cycle. This assures that the transistors
have ample time to become saturated before the heavy current is
conducted through them. Also, as has been mentioned previously, the
combination of capacitor C4 and transformer T1 provides a network
which yields a high frequency power-factor correction.
As can be seen, lamps 13 and 15 are connected in series between the
high-voltage terminals 32 and 33 of autotransformer 11 by reason of
their having their heaters 19 and 23 connected together. Similarly,
lamps 12 and 14 are connected in series, via heaters 17 and 21, and
placed across high-voltage terminals 32 and 33. Of course, it
should be noted that each of these series paths includes a
respective portion of the load-balancing network (C4, T1). The two
series-connected pairs of lamps (13,15 and 12,14) are connected in
parallel and each set is provided with corresponding low-voltage
windings on autotransformer 11 for energization of the respective
lamp heaters. For example, winding 35 powers heater 18 of lamp 13,
winding 36 powers parallel-connected heaters 19 and 23, and winding
37 powers heater 24 of lamp 15 and heater 22 of lamp 14.
Capacitor C5 permits two lamps to operate in the absence of the
remaining two lamps by partially bypassing the open secondary
reactance of transformer T1, which would otherwise prevent any lamp
from operating if one or more of the other lamps were removed from
the fixture or became inoperative.
From the foregoing it is seen that there is provided by the present
invention a novel and improved four-lamp driver circuit having very
high operating efficiency and will continue to function in a
fail-safe mode notwithstanding the removal from service of one or
more of the four lamps.
Modifications of the preferred embodiment described will be
apparent to those versed in the art, without the exercise of
invention. Thus, it is intended that the invention be limited only
by the appended claims.
* * * * *