U.S. patent number 3,750,125 [Application Number 05/190,842] was granted by the patent office on 1973-07-31 for transmission line presence sensor.
This patent grant is currently assigned to Sperry Rand Corporation. Invention is credited to David Lamensdorf, Gerald F. Ross.
United States Patent |
3,750,125 |
Ross , et al. |
July 31, 1973 |
TRANSMISSION LINE PRESENCE SENSOR
Abstract
A pulse generator-receiver system for detecting the presence or
proximity of objects including persons employs transmission of
short base-band or subnanosecond electromagnetic pulsed signals and
reception thereof within a dispersionless, broad band transmission
line energy coupling system with a receiver circuit cooperating
with a biased semiconductor device located within the transmission
line coupling system for instantaneously detecting substantially
the total energy of each coupled base-band pulse and for providing
corresponding outputs suitable for indication of the presence of
such proximate objects.
Inventors: |
Ross; Gerald F. (Lexington,
MA), Lamensdorf; David (Cambridge, MA) |
Assignee: |
Sperry Rand Corporation (New
York, NY)
|
Family
ID: |
22703018 |
Appl.
No.: |
05/190,842 |
Filed: |
October 20, 1971 |
Current U.S.
Class: |
340/561;
340/933 |
Current CPC
Class: |
G01V
3/105 (20130101); G08G 1/01 (20130101) |
Current International
Class: |
G08G
1/01 (20060101); G01V 3/10 (20060101); G08b
013/26 () |
Field of
Search: |
;340/258R,258C,258D,38R,38L,25R ;343/5PD ;324/52 ;325/43 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Trafton; David L.
Claims
We claim:
1. In combination:
passageway surface means having a principal direction of
passage,
dielectric substrate means having surface means substantially
coplanar with said passageway surface means,
signal generator means for supplying pulse signals,
transmission line energy coupling means excited by said pulse
signals comprising first and second transmission line conductor
means of finite length spaced apart in substantially parallel
relation on said substrate surface means and lying substantially
transverse of said principal direction,
said coupling means having a predetermined coupling characteristic
alterable according to the proximity of an object overlying at
least a portion of said coupling means,
receiver means for receiving presence detection signals propagating
on said second conductor means,
utilization means, and
gating means for passing said received presence detection signals
to said utilization means while rejecting spurious signals arising
adjacent the ends of said conductors of finite length.
2. Variable transmission line energy coupling object presence
detector means having a predetermined energy coupling
characteristic comprising:
dielectric substrate means having surface means adapted to be
placed in substantially coplanar relation with passageway surface
means,
first and second substantially parallel planar transmission line
conductor means at said dielectric surface means,
said substrate means and said conductor means being so constructed
and arranged as to respond to said object when overlying at least a
portion of said coupling means by a change in the degree of energy
coupling between said conductor means, and
means responsive to said change.
3. Apparatus as described in claim 2 wherein said dielectric
substrate means is adapted to be placed on said passageway surface
means.
4. Apparatus as described in claim 2 wherein said dielectric
substrate means is placed within a recess in said passageway
surface means.
5. Variable transmission line energy-coupling
object-weight-detection means having a predetermined energy
coupling characteristic comprising:
dielectric substrate means having surface means,
first and second substantially parallel planar transmission line
conductor means at said dielectric surface means,
flexible dielectric sheet means overlying said conductor means,
platform means overlying said dielectric sheet means, said platform
means having contact means for contacting said flexible sheet
means,
pulse generator means for exciting said first conductor means,
receiver means responsive to signals coupled to said second
conductor means in the presence of said object, and
utilization means responsive to said receiver means.
6. Variable transmission line energy coupling object presence
detector means having a predetermined energy coupling
characteristic comprising:
dielectric substrate means having surface means adapted to be
placed in substantially coplanar relation with passageway surface
means,
first and second substantially parallel planar transmission line
conductor means at said dielectric surface means.
said substrate means and said conductor means being so constructed
and arranged as to respond to said object when overlying at least a
portion of said coupling means by a change in the degree of energy
coupling between said conductor means,
means responsive to said change,
flexible layer means underlying said conductor means within said
dielectric means, and
dielectric sheet means overlying said conductor means,
said flexible layer means being adapted to be reversibly compressed
for permitting reversible variation of the amount of dielectric
material of said dielectric substrate lying between said conductor
means.
7. Variable transmission line energy coupling object presence
detector means having a predetermined energy coupling
characteristic comprising:
dielectric substrate means having surface means adapted to be
placed in substantially coplanar relation with passageway surface
means,
first and second substantially parallel planar transmission line
conductor means at said dielectric surface means,
said substrate means surface means including a recessed portion
between said conductor means,
flexible dielectric sheet means overlying said conductor means,
said flexible sheet means being adapted to be reversibly flexed
into said recessed portion of said surface means,
said substrate means and said conductor means being so constructed
and arranged as to respond to said object when overlying at least a
portion of said coupling means by a change in the degree of energy
coupling between said conductor means, and
means responsive to said change.
8. Presence detector means for detecting the presence of an object
comprising:
first and second transmission lines having a common directionally
coupling region for coupling high frequency signals from said first
to said second transmission line in the presence of said
object,
said first transmission line having input port means and first
absorber means at opposite ends of said directionally coupling
region,
said second transmission line having output port means and second
absorber means at opposite ends of said directionally coupling
region,
signal generator means for supplying high frequency signals at said
input port means,
receiver means for receiving presence detection signals at said
output port means,
utilization means, and
gating means responsive to said signal generator means for passing
said received presence detection signals to said utilization means
while rejecting spurious signals caused by any impedance mismatch
at said input port means, said output port means, or said first or
second absorber means.
9. Apparatus as described in claim 8 further including:
dielectric substrate means having a substantially planar
surface,
said first and second transmission lines being affixed to said
planar surface.
10. Apparatus as described in claim 9 wherein said planar surface
of said dielectric substrate means lies substantially in the plane
of passageway surface means for forming a substantially coplanar
extension of said passageway surface means.
11. Apparatus as described in claim 8 wherein said signal generator
means comprises pulse generator means.
12. Apparatus as described in claim 11 wherein said pulse generator
means is adapted to generate a train of base-band subnanosecond
electromagnetic pulses.
13. Apparatus as described in claim 11 wherein said receiver means
is adapted to respond to pulse signals.
14. Apparatus as described in claim 13 wherein said receiver means
is adapted to respond to the receipt of base-band subnanosecond
electromagnetic pulses.
15. Apparatus as described in claim 10 wherein said gating means is
operated in synchronism with said pulse generator means.
16. Apparatus as described in claim 8 wherein said utilization
means comprises alarm means.
17. Apparatus as described in claim 8 wherein said utilization
means includes visual display means.
18. Apparatus as described in claim 8 wherein said utilization
means includes control means adapted to control controllable means.
Description
CROSS REFERENCE TO COPENDING APPLICATIONS
This application relates to subject matter disclosed in application
Ser. No. 123,720, filed Mar. 12, 1971, now U.S. Pat. No. 3,662,316,
and applications Ser. Nos. 134,990, filed Apr. 16, 1971, and
137,355, filled Apr. 26, 1971.
BACKGROUND OF THE INVENTION
1. Field of the Invention
The invention relates to radio systems for the detection of the
presence or of other characteristics of objects such as persons or
vehicles and more particularly relates to the sensing of the
presence of such objects as may move through a door or passage way
or along a traffic lane. Detection is accomplished by a novel
transmission line energy coupling system, excited by base-band or
subnanosecond electromagnetic signals, wherein changes in the level
of energy coupling are caused by the passage of the object to be
sensed.
2. Description of the Prior Art
In prior art presence detectors operating with radio frequency
signals, it is common practice to employ relatively high radio
energy signal levels to ensure that the passage of an object such
as a person or vehicle is detected without failure. Such systems
tend to be expensive to operate, requiring radio frequency
generators which consume considerable power. In consequence of the
level of the power, undesired leakage radiation in excess of
government standards may occur. A further consequence is that such
prior art systems are often susceptible to interference because of
radiations generated by neighboring radio frequency signal
sources.
Accordingly, prior art presence detector systems may not generally
be operated in a wave band already alloted to conventional
transmitters and receivers. More particularly, there is not known
in the prior art a radio frequency presence detector system of the
just described type which can operate at very low or legal power
levels in such wave bands without it itself being the victim of
intolerable interference. Furthermore, there is not known in the
prior art a radio frequency presence detector system such as
described in the foregoing and also capable of employing signals
having an extremely wide frequency spectrum without interfering
with the transmission of ordinary radio communication signals.
SUMMARY OF THE INVENTION
The invention pertains to radio object presence detection systems
of a novel kind so constructed and arranged as to afford sensing of
objects without interference with conventional types of radio
communication systems, and, in turn, being substantially unaffected
in normal operation by the radiations of other radio frequency
systems or by ambient electrical noise signals.
While continuous wave or pulsed radio frequency signals may also be
used with advantage in the novel presence detector, it will be
preferred in many applications to use very short impulse signals.
For example, a transmitter appropriate for exciting the
transmission line coupling system may employ a non-dispersive
transmission line and a charging-discharging system for the cyclic
generation of such base band pulses. The novel coupling or sensing
system is also constructed of similarly non-dispersive transmission
line elements.
Cooperating with the sensor is a receiver suitable for detecting
and utilizing such coupled short base-band electromagnetic pulses
the receiver also employing a dispersionless transmission line,
with a utilization circuit cooperating with a semiconductor element
located within the receiver transmission line for instantaneously
detecting substantially the total coupled energy of the base-band
pulse and for supplying a corresponding output suitable for
application in presence indicating or control circuits. The
receiver transmission line system supplies substantially the total
energy of each undistorted coupled base-band pulse directly to the
receiver detector; thus, the receiver is adapted to operate
successfully with base-band pulse signals having a very wide
spectral extent. Further, the receiver may operate with base-band
pulse signals having spectral components each of such low
individual energy content as to escape detection by conventional
relatively narrow band receivers. The total energy in each
base-band pulse can, however, be relatively larger than the level
of noise or other interfering pulses or signals in the vicinity of
the novel receiver. Thus, by appropriately adjusting the output
level of the base-band pulse signal generator and the sensitivity
or threshold of the detector receiver, base-band signals not
affecting other receivers are readily generated. coupled, and
detected without the receiver, in turn, being affected in any
substantial degree by other radio energy transmissions. The
coupling and processing of the coupled signals is accomplished,
according to the invention, by simple base-band signal processing
circuits, thus avoiding the need for signal frequency conversion
and avoiding the problems associated with alignment and operation
of conventional radio and intermediate frequency amplifiers.
The novel base-band object presence sensing system operates with
very low energy consumption, so that power supply cost and size are
minimized. Furthermore, with such low power operation, inexpensive
components find long life use throughout the pulse generator. The
receiver circuits are similarly categorized, all constituent
elements being of simple nature and otherwise inexpensive of
installation, maintenance, and operation, adapting readily to
cooperative use with conventional alarm, display, or control
equipment.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a plan view of a preferred embodiment of the invention
showing components thereof and their electrical
interconnections.
FIG. 2 is an elevation cross section view taken at the line 2--2 of
FIG. 1.
FIGS. 3 through 7 illustrate alternative forms of the structure of
FIG. 2.
FIG. 8 is a block diagram of the receiver 11 of FIG. 1.
FIG. 9 is a detailed circuit diagram of a portion of the receiver
apparatus of FIG. 8.
FIGS. 10 to 12 are graphs showing representative wave forms useful
in explaining the operation of the system.
FIG. 13 is an elevation cross section view taken at the line 13--13
of FIG. 14.
FIG. 14 is an elevation view of an alternative form of FIG. 1.
FIG. 15 is an elevation cross section view of an alternative form
of the construction shown in FIG. 13.
FIG. 16 is a fragmentary perspective view, partly in cross section,
showing a further application of the invention.
DESCRIPTION OF THE PREFERRED EMBODIMENTS
The transmission line object-presence sensor shown in FIG. 1
detects the actual presence of an object traversing it in
contacting, substantially contacting, or other relation by
measuring a change caused by the presence of the object in the
amplitude of the signal coupled between the substantially parallel
high frequency transmission line conductors 1 and 2. The
transmission line system comprising conductors 1 and 2 may be of
the parallel plate or strip transmission line type conventionally
used in the high frequency art. In particular, the preferred
transmission line system will be one capable of propagating
electromagnetic energy in the low loss transverse electromagnetic
or TEM mode.
The high frequency conductors 1 and 2 are affixed to the top
surface of a substrate sheet 3 of low loss dielectric material. A
metallic ground conducting plane (not seen in FIG. 1) is affixed to
the bottom of sheet 3. At one end of the transmission line
conductors 1 and 2 are respectively located conventional impedance
matching connectors 6 and 7 for coupling to respective conventional
input and output transmission lines 8 and 9, which latter lines may
be coaxial transmission lines. At the end of the substrate sheet 3
opposite connectors 6 and 7, the strip conductors 1 and 2 are
coupled to impedance matched terminating resistors or energy
absorbers 4 and 5 for preventing reflections. Signal generator 10
is adapted to supply excitation signals to transmission line
conductor 1 via coaxial line 8 and also to supply synchronizing
signals, if required, to the gate generator 11 over conductor 13.
The output of gate generator 11 may be supplied via lead 13a to
control the receiver 11a. Receiver 11a is coupled to transmission
line conductor 2 via coaxial line 9 and supplies useful output
signals to utilization device 12 when an object contacts conductors
1 and 2 or otherwise distorts the coupling between conductors 1 and
2. It is recognized that utilization device 12 may be any
conventional type of alarm, latchable or otherwise. Simultaneously
or alternatively, a counter 12a or other display may be employed as
the utilization device. Similarly, a control device 12b may be
used, including an actuator for opening a door or other servo
devices.
Although other types of apparatus, such as pulsed or continuous
wave osillator systems, may be used to play the role of signal
generator 10, it is preferred to employ a short or base-band pulse
generator for that purpose. One such generator for producing short
base-band pulses is disclosed by G. F. Ross in the U.S. Pat. No.
3,402,370 for a "Pulse Generator," issued Nov. 30, 1965 and
assigned to the Sperry Rand Corporation. Switching systems adapted
for generating base band pulses are described in the H. C. Maguire
U.S. Pat. No. 3,564,277 for a "Coaxial Line Reed Switch Fast Rise
Signal Generator with Attenuation Means Forming Outer Section of
the Line," issued Feb. 16, 1971 and in the K. W. Robbins, G. F.
Ross U.S. Pat. No. 3,569,877 for a "High Frequency Switch," issued
Mar. 9, 1971, both patents being assigned to the Sperry Rand
Corporation.
The receiver 11a of FIG. 1 is a receiver again preferably designed
for operation with short base-band electromagnetic pulses; it may
be of the general type described by K. W. Robbins in the U.S. Pat.
Application Ser. No. 123,720 for a "Short Base-Band Pulse
Receiver," filed Mar. 12, 1971, issued as U.S. Pat. No. 3,662,316
May 9, 1972 and assigned to the Sperry Rand Corporation. A
preferred base-band receiver system, adapted for synchronous
operation with generator 10, is disclosed by G. F. Ross in the U.S.
Pat. application Ser. No. 137,355 for an "Energy Amplifying
Selector Gate for Base Band Signals," filed Apr. 26, 1971 and also
assigned to the Sperry Rand Corporation.
As noted above, the presence sensor may consist of two spaced
parallel strip conductors 1 and 2 placed across the path of the
object to be detected. Detection of the object (a wheel or a
vehicle or a shoe on a human foot, for example, occurs when the
presence of the object causes a change or distortion in the
electromagnetic-field-coupling pattern between conductors 1 and 2.
The sensor elements may, for instance, be placed in a shallow
groove in the surface of a road or walk or it may be fastened
directly to such a surface by a non-conducting cement such as an
epoxy or other similar cement. A similar material may be used to
form a protective coating over conductors 1 and 2.
In a simple arrangement, the sensor may take the form shown in FIG.
2, where conductors 1 and 2 are thin flexible conducting foils
affixed to a flexible low-loss sheet 14 of material such as rubber
or cloth that may be unrolled across the path to be monitored and
even fastened to the surface 15 of the flooring material. A thin
film 16 of conductive foil is generally fastened to the bottom of
the sensor before it is placed on f oor 15. It will be recognized
that the dimensions and proportions shown in the various figures
are exaggerated for convenience in making the drawings clear, and
that the dimensions and proportions are therefore not necessarily
those that would be used in actual practice. For example, the
vertical dimensions in the cross section of FIG. 2 are exaggerated,
since conductors 1, 2, and 16 may be made of relatively thin metal
foil. While conventional cloth strip transmission line is lossy, it
may be successfully used according to the invention to monitor a
relatively narrow passage way.
Conventional low loss strip transmission line is readily available
in rigid form and may be laid in a shallow groove across the path
to be monitored, as in FIG. 3. Such conventional strip lines have
good thermal stability and relatively little susceptibility to
environmental effects. Evidently, strip transmission lines of
superior quality may be constructed by a suitable choice of
preferred conductive and dielectric materials, of which a wide
variety is readily available.
In the system of FIG. 3, the dielectric slab 24 may constitute a
solid non-flexible low loss material such as a ceramic material
coated on one side with a conductive ground plane 26 made of copper
and supporting on an upper surface 27 the spaced copper strip lines
1 and 2. The upper surface 27 of dielectric slab 24 is arranged to
be flush with the surface 15 of a non-conducting floor or roadway
surface. It is seen that an object such as a vehicle tire rolling
over conductors 1 and 2 changes or distorts the
electromagnetic-field-coupling pattern between strip lines 1 and 2.
To the extent that the pressure on the tire due to the weight of
the vehicle causes the tire to flex into the gap 20 between
conductors 1 and 2, the degree of electromagnetic-field-coupling
may be additionally altered over that when gap 20 is occupied only
by air. In FIGS. 4 and 5, it is illustrated that the strip
conductors 1 and 2 may be partially or totally inlaid within the
surface of dielectric slab 24, leaving gaps 20 of corresponding
shape. In some applications, the configuration of FIG. 5 may be
preferred, since the upper surfaces of strip conductors 1 and 2 are
flush with the surface 15 of a floor or walk or road pavement.
In many instances, it may be desirable to protect the strip
transmission line sensor from water or dirt or the like. In others,
such as those in which the sensor is used to monitor the passage of
people, it may be particularly desirable to hide the transmission
line conductors 1 and 2 from view, as is accomplished in the
apparatus of FIGS. 6 and 7.
In FIG. 6, for example, the arrangement of ground plane 26,
dielectric slab 24, and strip transmission lines 1 and 2 is similar
to the arrangement used in FIG. 4, lines 1 and 2 being partly
inlaid within dielectric slab 24. A flexible rubber or other
covering sheet or rug 25, such as made of carpeting or other
material, may be used to hide the sensor from view. The sheet 25
may be used without modification, or may be provided with a groove
for accommodating conductors 1 and 2 and for covering gap 20. It is
clear that the weight of a person stepping on the carpet above
conductors 1 and 2 will depress sheet 25 into gap 20, changing the
character of the dielectric within gap 20 and consequently altering
the electromagnetic-field-coupling pattern between strip conductors
1 and 2. In FIG. 7, the same end result is accomplished by
employing strips 17, 18 of sponge rubber or other readily
compressible material underlying strip transmission conductors 1
and 2. A weight placed on the rubber mat or carpet 25 above
conductors 1 and 2 will compress the strips 17 and 18, permitting
strip transmission lines 1 and 2 to be pressed farther into
dielectric slap 24. Consequently, more of the dielectric ridge 19
of slab 24 is projected into the gap 20 between conductors 1 and 2,
again significantly altering the electromagnetic-field-coupling
pattern between conductors 1 and 2. Other transmission line
configurations which will respond to the presence of an object
having at least a predetermined weight according to the invention
will be apparent to those with skill in the high frequency art.
As noted above, the transmission line systems may be constructed of
flat metal, electrically-conducting strips 1 and 2 placed parallel
to each other on a suitable dielectric substrate. The widths of the
conductor strips 1 and 2 are determined by the desired impedance of
the transmission lines. For example, if the connecting coaxial
cables 8 and 9 are 50 ohm lines, 50 ohm strip lines 1 and 2 will be
chosen. The width of gap 20 is selected according to the desired
degree of coupling between conductors 1 and 2 and primarily upon
the type of devices chosen for generator 10 and receiver 11a. For
example, gap widths of from 1/32 to 11/16 inches have been found
useful in various circumstances.
As noted above, the apparatus of FIGS. 1 to 7 may be operated with
continuous wave or pulsed excitation. In order to discuss fully a
preferred form of the sensor system and its operation, it will be
assumed that signal generator 10 is a base-band pulse generator
having a convenient repetition rate and producing electromagnetic
impulses of subnanosecond duration. In this kind of system, a
base-band pulse is generated and is coupled through line 8 to
propagate down strip line 1. In a typical application, the pulses
are of about 10 volts amplitude and are 0.3 nanoseconds in
duration. The transmission line system including lines 1 and 2 acts
in a manner similar to a conventional microwave directional
coupler. A pulse from generator 10 is coupled into receiver 11a at
the point near connectors 6 and 7 where lines 1 and 2 become
parallel. This is pulse 21 of FIG. 10. When the pulse reaches
terminal of line 1, most of it is absorbed in the terminating
resistor 4. A small amount of energy is coupled into line 2 at the
termination and is seen as pulse 22 of FIG. 10. This signal is
minimized by the proper choice of terminating resistors 4 and 5 of
FIG. 1. The separation between pulses 21 and 22 will be
substantially 2L/c where L is the length of strip line 1 and c is
the velocity of propagation of electromagnetic energy in the
transmission line system. As seen in the representative
experimental curve of FIG. 10, which is a representation of an
actual cathode ray tube presentation, the region between pulses 21
and 22 will have only minor deviations from a substantially zero
amplitude or fixed level.
When an object is present on or over or passes over the
transmission line system 1, 2 at a local point along its length, a
localized change is produced in the field-coupling pattern between
lines 1 and 2 such as shown, for instance, in FIGS. 11 and 12. Part
of the generator 10 pulse propagating down line 1 is directly
coupled to line 2 at the local point because of the presence of the
detected object and is propagated along line 2 into output coaxial
line 9 and thence into receiver 11a. Such an event is represented
by pulse 23 in the typical oscilloscope record shown in FIG. 11 of
the response to a vehicle tire. Pulse 23 is characteristically a
doublet appearing 2s/c seconds after the first pulse 21 where s is
the distance between the connector (6, 7) end of the transmission
line system and the location of the detected object. If two
automobile tires contact conductors 1, 2, two doublet pulses will
appear between pulses 21 and 22, separated by 2w/c seconds, where w
is the distance between the tires. FIG. 12 presents a similar graph
representing the response 22a to the presence of a leather sole of
a shoe worn by a person.
The receiver 11a may be a threshold detector receiver of the type
in which an avalanche or other transistor is used that is time
gated by gate generator 11 to exclude spurious input pulses, such
as pulses 21 and 23 of FIGS. 11 and 12. The output of such a
receiver may be used to control an alarm indicator, counter, or
other device such as door opener when employed as utilization
device 12. Simple or latching alarms may be employed. FIGS. 8 and 9
illustrate a gating and receiver system particularly useful as the
gated or selective receiver 11a.
In FIG. 8, the gate generator 11 and receiver 11a are shown in
cooperative relation with a signal generator 10 which includes a
system synchronizer 27 and base-band pulse generator 28 whose train
of subnanosecond output pulses is coupled via coaxial line 8 to the
strip transmission line 1. Synchronizer 27 also provides system
synchronizing pulses 10A to the receiver via lead 29. For
controlling operation of the receiver, the synchronizer pulse 10A
is coupled by line 29 to a variable delay trigger circuit 30 for
the purpose of generating on output line 31 a corresponding pulse
30B. Pulse 30B may be generally similar in characteristics to pulse
10A, though delayed by an arbitrary time interval. Variable delay
trigger circuit 30 may be any of several well known adjustable
pulse delay circuits, including those, for instance, whose delay
characteristic may be varied according to the setting of a tap 32
adjustable along potentiometer 33 relative to lead 34, an
appropriate potential being supplied to the opposite end of
potentiometer 33 from a voltage source (not shown) connected to
terminal 35 and which may also be grounded at its opposite end.
Variable delay trigger circuit 30 serves to determine the
initiation of the time gate, while time gate generator 36, whose
input is supplied via line 31, determines the duration of the time
gate. This duration is determined, as will be further explained in
connection with FIG. 9, according to the length of transmission
line 37, whose center conductor is adapted to supply certain
necessary operating voltages via resistor 38 from terminal 39 to
the active circuit elements of time generator 36. The time gate
thus formed is the wave 36C.
Wave 36C is supplied by line 40 to low pass filter 41 whose
function is to provide a moderate integration to wave 36C, removing
any transients or over-shoots from the edges of wave 36C and thus
preventing false operation of succeeding circuits. Wave 41D is the
modified output of filter 41. Wave 41D is passed through inverter
42 to produce on line 43 the inverted or negative going wave 43E.
Wave 43E is generally similar to wave 41D, but is inverted in
polarity.
The inverted wave 43E is used to operate the time gated
receiver-detector 44 along with current source circuit 45 which
forms, as will be explained, the actual gating potential used to
control flow of signals through the gated receiver-detector 44 from
receiver input coaxial line 9 to output leads 46 (wave 46F). Gated
detector 44 is normally desensitized; when a gating signal is
present at the output of inverter 42, the gated detector 44 is made
sensitive to the presence of millivolt signals appearing on the
dispersionless transmission line 9 and propagated into gated
detector 44 from transmission line 2. Such sensitivity produces an
amplified selected or time gated output wave 46F on leads 46 of the
order of 3 volts. Such a signal is adequate to operate conventional
display or warning apparatus, such as a warning alarm or presence
indicator or control of conventional type.
In FIG. 9, circuit details of the receiver are further illustrated,
with elements which also appear in FIG. 8 bearing the same
reference numerals as used in FIG. 8, including time gate generator
36, low pass filter 41, inverter 42, current source circuit 45,
gated detector 44, and input coaxial line 9.
The output line 31 of variable delay trigger circuit 30 supplies
wave 30B via a coupling capacitor 50 and the junction 52 to the
base 54a of transistor 54, which transistor may be of the 2N5130
type. Junction 52, and therefore base 54a, is coupled to ground
through resistor 51. The collector 54b of transistor 54 is coupled
via the inner conductor of coaxial transmission line 37 of length d
through resistor 38 to a source (not shown) of positive potential
connected between terminal 39 and ground. The length d of
open-circuited delay line 37 is adjusted according to the desired
duration of the sampling or time gate wave 43E. The emitter 54c of
transistor 54 provides an output connection via lead 40 to low pass
filter 41. In a representative circuit resistor 38 has the value of
47 K ohms, while the voltage on terminal 39 may be from +200 to
+300 volts. Other avalanche transistor delay-line pulse generators
of known type may be employed as the time gate generator 36.
The emitter 54c of transistor 54 is coupled to junction 55 to
provide an input to low pass filter 41, which filter 41 is of
generally conventional nature and whose components include in
series relation junction 55, resistor 57, junction 58, resistor 60,
junction 61, resistor 63, resistor 64, junction 65, resistor 66,
and a ground connection. Junction 55 is coupled to ground via
resistor 56 and the respective junctions 58 and 61 are coupled to
ground through low pass filter capacitors 59 and 62. Junction 65
serves as an output terminal for the filter.
Junction 65 is coupled through the small coupling capacitor 67 to
junction 68 of the inverter circuit 42 and thence to the base 69a
of transistor 69, which may be of the 2N4258 kind. The emitter 69b
of transistor 69 is coupled through a series circuit including
junctions 79 and 74, resistor 70, and junction 73, to a source (not
shown) of positive potential applied at terminal 71 and connected
to ground at its opposite end. Junctions 73 and 79 are respectively
coupled to ground via capacitors 72 and 80, while junction 74 is
connected through potentiometer 75 and resistor 78 to ground.
Capacitors 72 and 80 serve as radio frequency by-pass and
decoupling elements in the conventional manner. The tap 76 of
potentiometer 75 is connected through resistor 77 to junction 68.
The collector 69c of transistor 69 is connected as an output of the
inverter 42 through diode 85. The resistance network associated
with potentiometer 75 serves to adjust the potential across
resistor 87 which determines the steady state hold off bias on the
detector.
Diode 85 is connected by line 43 to junction 86 through resistor 87
to ground and via line 88 to the emitter 44c of time gated detector
transistor 44, which may be of the 2N5130 type. The collector 44b
of transistor 44 is connected through junction 91 to the gate
electrode 93a of field effect transistor 93, which latter may be of
the 2N4274 type. The drain electrode 93b of transistor 93 is
connected to a source (not shown) of positive potential applied at
terminal 98 which may be of the order of +75 to +100 volts with
respect to its grounded terminal. The source electrode 93c of
transistor 93 is coupled via resistor 92 to junction 91 and via
coupling condenser 95 to the output 46 consisting of output leads
97 and 97a connected across load resistor 96.
Base-band or subnanosecond signals received from the sensor strip
line 2 to be gated are applied by coaxial line 9 to the base 44a of
detector transistor 44. Such base-band signals may be found across
the matching load resistor 90 attached across a conventional
non-dispersive TEM mode transmission line 9 such as a coaxial or
continuous two-wire line comprising constant impedance or uniformly
spaced parallel conductors or other TEM mode transmission line.
Operation of the time gated circuit will be understood from the
foregoing. It is seen that time gate generator 36 relies for its
operation upon characteristics inherent in the 2N5130 avalanche
transistor 54 and in the open circuited delay line 37 of length d.
In response to the positive triggering signal 31B, transistor 54
breaks into conduction and a voltage step wave is propagated into
delay line 37. When this step wave reaches the open end of line 37,
it is inverted there upon reflection and returns to collector 54b,
whereupon the current flow in transistor 54 is brought to zero and
the transistor reverts to its non-conducting condition. Thus, the
voltage wave 36C across filter resistor 56 is a sharply rising and
terminating positive pulse of duration 2d/c seconds, a duration
dictated by delay line 37 (c is the velocity of propagation of the
step wave in delay line 37).
In the quiescent state of the circuit of FIG. 9, transistor 69 in
inverter circuit 42 is normally fully conducting, causing a current
of about 30 milliamperes to flow through the emitter resistor 87
associated with detector transistor 44 (resistor 87 may have a
resistance value of about 100 ohms). The voltage consequently
appearing across resistor 87 will be about +3 volts and assures
that detector transistor 44 is in its non-conducting state. The
field effect transistor 93 acts as a constant current source,
assuring that a constant current is fed via the collector 44b and
emitter or c of detector transistor 44 in its quiescent of
non-conducting state so that its bias state is precisely
controlled. Resistor 92 in the collector circuit of detector
transistor 44 has a positive thermal coefficient and serves to
afford temperature compensation for the thermal characteristic of
the conduction threshold of detector transistor 44.
When wave 30B triggers time gate generator 36, the positive output
wave 36C produced by time gate generator 36, is as previously
explained, fed through low pass filter 41 to inverter 42. In
traversing filter 41, wave 36C is acted upon so that the positive
wave 41D results, having rounded rise and fall portions.
Accordingly, any high level transient near the start or the end of
wave 36C is removed, a desirable result since such spurious
transients might otherwise undesirably trigger detector transistor
44 into conduction.
The positive wave 41D, when coupled by capacitor 67 to inverter
circuit 42 and thus to the base 69a of transistor 69, causes
current conduction through transistor 69 to stop, forcing the
voltage across resistor 87 rapidly to fall to zero. This event
places detector transistor 44 in its fully sensitive state with
respect to any signal to be sampled that is propagated within
transmission line 2 and thereby arrives on line 9 at the base 44a
of transistor 44. Any signal sampled by detector transistor 44
appears as a negative amplified and time extended wave 46F on the
collector 44b of detector transistor 44 and is supplied by coupling
condenser 95 across load resistor 96, for example. It may be then
supplied to the aforementioned utilization apparatus via terminals
97 and 97a in the customary manner, since wave 46F is amplified and
time extended with respect to the received short base-band pulses.
Upon termination of the gating pulse 41D, the circuit returns to
its above described quiescent state, awaiting receipt of the next
succeeding triggering wave 30B.
It will be noted that transmission of short duration pulses from
their source, such as from base-band pulse generator 10 of FIG. 1,
is through a transmission line system or other medium that
preferably operates substantially solely in the TEM mode, and that
propagation modes that permit dispersion of pulses such as
subnanosecond or base-band pulses are not used. Thus, the full
energy of base-band pulses originating in transmission line 2 is
effectively directed to processing within the time gated detector
44. It will be apparent that variable delay trigger circuit 30 and
time gate generator 36 may readily be adjusted so that receiver 11a
is, in effect, sensitive only to pulses above a predetermined
threshold coupled to transmission line 2 when an object passes over
line 1, 2 in the restricted region encompassed by distance D in
FIG. 1. Thus, the spurious pulses 21 and 22 of FIGS. 11 and 12 are
not passed by receiver 11a and are not coupled to the alarm or
other utilization device 12.
It will also be seen that other time gating arrangements may be
employed; for example, the distance D in FIG. 1 may be divided into
a plurality of non-overlapping range or time bins by employing a
multiple time selector device, such as that disclosed in G. F. Ross
U.S. Pat. application Ser. No. 134,990 for a "Base Band Pulse
Object Sensor System," filed Apr. 16, 1971 and assigned to the
Sperry Rand Corporation. For example, the receiver 11a may readily
be time-gated according to the number of lanes of a highway, the
two strip transmission lines 1 and 2 extending across the highway
or aircraft taxi roadway so that all lanes are covered. Multiple
range gates may then be used to separate the signals due to returns
coming from individual traffic lanes. It will be appreciated that
two or more traffic lanes may be monitored by using parallel
multiple channel sensors or by the use of one range gate which is
cyclically scanned over the lanes sufficiently rapidly that no
vehicles are missed.
As previously noted, the novel sensor system provides presence
detection of objects having greater than relatively low
predetermined weights. The threshold sensitive characteristic of
the receiver 11a may also be employed, as in FIGS. 13 and 14, to
detect an object such as a package according to its weight with
respect to other threshold values. In FIG. 13, the configuration
employed in FIG. 3 comprising dielectric substrate 24, conducting
ground plane 26, and strip conductors 1 and 2 is again seen. These
elements are placed in a recess below the surface 15 of a floor or
other planar element. Over the combination is placed a layer 103 of
compressible material, such as sponge rubber or other flexible
material. Across the layer 103 is located an array of substantially
regularly spaced contacting metal bars 101a to 101f. A metal or
other plate or platform 102 is placed on top of the metal bars or
contactors 101a to 101f for distributing any load placed on plate
102 generally to each of contactor bars 101a to 101f. Bars 101a to
101f and plate 102, on which an object whose weight is to be sensed
are dimensioned so as to provide clearance between them and the
walls 104 and 104a of the recess in floor 15 so that plate 102 may
move downward without contacting walls 104, 104a, for instance.
When an object such as a package or a person is placed or steps on
plate 102, the weight of the package compresses the flexible layer
103 beneath each bar 101a to 101f. The consequently decreased
separation between the buttom surface of bars 101a to 101f and the
strip transmission line conductors 1 and 2 again causes the
above-discussed type of increased localized coupling between lines
1 and 2. This occurs at each of bars 101a to 101f, parlicularly if
the object is substantially centered on plate 102. To a substantial
degree, detection is independent of the exact location and
composition of the object on plate 102. The minimal weight to be
detected can, for instance, be adjusted by controlling the
thickness or density of the flexible layer 103 or the distance
separating the bars 101a to 101f.
In practice, the metal or other plate 102 of FIGS. 13 and 14 may be
replaced as in FIG. 15 by a rubber mat 110 backed by a conducting
metal foil or flexible plate 111. The mat 110 and foil 111 may be
placed directly on a foam rubber mat 103 placed, in turn, directly
on top of the strip conductors 1 and 2 of the transmission line
system.
The invention is not limited to use in a substantially horizontal
plane. For example, the strip transmission line conductors 1 and 2
of FIG. 16 are oriented vertically, being placed on the inside of a
vertical wall 123 of an inclined sluice or flume formed of walls
123 and 125 and floor 124. The surface of vertical wall 123
underlying strip lines 1 and 2 may be made of low loss dielectric
material. The presence of a material such as a dielectric or
non-conducting fluid or sand or a solid aggregate will be sensed by
the apparatus as its presence will again distort the
electromagnetic-field-pattern between conductors 1 and 2.
It is seen that the novel object presence detector employs a wide
band or wide open detector device, a detector which will respond to
any signal level in excess of the bias level which might be
dictated by the characteristics of a particular transistor detector
44. The amplitude of te received base-band pulse at the detector 44
may be, for example, about 200 millivolts in a typical operating
circumstance, a value several orders of magnitude greater than the
amplitude of the signals present in an urban environment due to
conventional radiation sources, such interfering signals normally
being at a microvolt level. Accordingly, although the presence
detecting receiver of the invention essentially accepts all signals
over a very wide pass band, it is substantially immune to
interference from conventional radiation sources, including
electrical noise signals such as internal combustion engine
ignition noise; being time gated, the receiver is sensitive only
for 1 nanosecond, for example, for each generator pulse.
The transmission line system 1 of FIG. 1 may, for instance, employ
a regular train of extremely short duration, relatively low
amplitude base-band pulses. In one typical situation, these
impulse-like signals have time durations of substantially 200
picoseconds and a pulse repitition frequency of the order of 10
kilohertz. However, the upper bound on the average power coupled
through space may be considerably less than 1 microwatt. The
spectrum of the propagating base-band signal is spread over an
extremely wide band, typically 100 megahertz to 10 gigahertz.
Accordingly, the power that may be radiated in any typical narrow
communication band is far below the thermal noise threshold of a
typical conventional communication receiver operating in that band.
The base-band pulse energy is therefore incapable of interfering
with the operation of standard radio communication equipment, while
being remarkably adapted for use with the object presence detection
apparatus of the present invention.
While the invention has been described in its preferred
embodiments, it is to be understood that the words which have been
used are words of description rather than of limitation and that
changes within the purview of the appended claims may be made
without departing from the true scope and spirit of the invention
in its broader aspects.
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