U.S. patent number 3,742,492 [Application Number 05/105,583] was granted by the patent office on 1973-06-26 for transducer drive circuit and signal generator.
Invention is credited to Darryl Frederic Proctor.
United States Patent |
3,742,492 |
Proctor |
June 26, 1973 |
TRANSDUCER DRIVE CIRCUIT AND SIGNAL GENERATOR
Abstract
A transducer such as a piezoelectric element forms part of the
diaphragm of a speaker in a sonic signal generator. A timing
circuit and the piezoelectric transducer element are coupled to a
level detector and voltage comparing circuit. This circuit monitors
the phase and voltage of the piezoelectric transducer and compares
the same with the signal from the timing circuit. When a selected
condition is reached a controlled switch connected between the
transducer and the power supply is operated to cause a small signal
to be applied to the transducer at the appropriate time to maintain
the transducer in an oscillatory state corresponding to its
resonant frequency with the expenditure of a very small amount of
energy from the power supply.
Inventors: |
Proctor; Darryl Frederic
(Bellevue, WA) |
Family
ID: |
22306648 |
Appl.
No.: |
05/105,583 |
Filed: |
January 11, 1971 |
Current U.S.
Class: |
340/384.6;
331/116R; 331/155; 331/173; 310/316.01 |
Current CPC
Class: |
H03B
5/36 (20130101); H04M 19/04 (20130101) |
Current International
Class: |
H03B
5/36 (20060101); H04M 19/04 (20060101); H04M
19/00 (20060101); H01v 007/00 (); G08b
003/00 () |
Field of
Search: |
;340/384E
;331/116R,116M,154,155,172-174 ;310/8,8.1 ;317/262 ;332/26 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Caldwell; John W.
Assistant Examiner: Wannisky; William M.
Claims
What is claimed is:
1. An audio signal generator for operation from a power supply,
comprising in combination: a transducer operative to provide a
damped output signal alternating between successively decreasing
maximum values thereof when electrically energized; a switching
means connected to said transducer for applying an in-phase,
boosting signal to said transducer; means actuating said switching
means when said output signal approaches a maximum value, said
actuating means including means providing a threshold signal whose
voltage is less than that of said maximum value of said transducer
output signal, and wherein said switching means includes a
comparison means operable to provide said in-phase boosting signal
when the voltage on said transducer substantially equals the
voltage of said threshold signal; and means connecting the power
supply to said transducer, said switching means and said actuating
means.
2. An audio signal generator as recited in claim 1, wherein said
transducer comprises a piezoelectric element.
3. An audio signal generator as recited in claim 1, wherein said
threshold signal means includes a timing circuit which produces an
output voltage which increases with respect to time in synchronism
with said output signal, and said comparison means in said
switching means includes at least one semi-conductor element having
first and second electrodes respectively connected to said timing
circuit and to said transducer, said semi-conductor element
remaining non-conductive until the voltages on said two electrodes
become substantially equal.
4. An audio signal generator as recited in claim 3, wherein said
semiconductor element comprises a programmable unijunction
transistor having a gate electrode connected to said transducer
element and an anode electrode connected to said timing means.
5. An audio signal generator as recited in claim 3, wherein said
semiconductor element comprises a silicon controlled switch having
a gate electrode connected to said transducer element and an anode
electrode connected to said timing means.
6. A signal generator comprising in combination: an electrically
sensitive transducer means including a piezoelectric element;
timing circuit means; power supply means connected to said
transducer means and timing circuit means; and signal comparison
and switch means connected to said transducer means, said timing
circuit means and said power supply means, said timing circuit
means including means providing a signal having a voltage which
rises to the voltage on said transducer means as the voltage on
said transducer means is approaching a maximum value, and said
comparison and switch means includes means operative when the
voltage on said transducer means substantially equals the voltage
of said timing signal to apply an in-phase, boosting signal to said
transducer means.
7. A signal generator as recited in claim 6, wherein said signal
comparison and switch means includes at least one semiconductor
element having first and second electrodes respectively connected
to the timing circuit means and to the transducer means, said
element remaining non-conductive until the voltages on said two
electrodes become substantially equal.
8. A signal generator as recited in claim 6, wherein said
semiconductor element is maintained non-conductive during at least
50 percent of each cycle of said transducer means.
9. A signal generator as recited in claim 6, wherein said
transducer means forms part of a sonic signal generator.
10. A sonic signal generator comprising in combination: power
supply means having first and second terminals; a transducer
element including a piezoelectric crystal having first and second
electrodes; first and second impedance elements connecting said
first and second electrodes to said first and second terminals of
said power supply means; first circuit means including a capacitor
having a first side connected to said first electrode, said first
circuit means further including means connecting a second side of
said capacitor to said first terminal of said power supply means;
and second circuit means including a semiconductor element having a
first electrode connected to said second terminal of said power
supply means and second and third electrodes respectively connected
to said second side of said capacitor and to said second electrode
of said transducer element, said semiconductor element thereby
being maintained non-conductive until the voltages on its said
second and third electrodes are substantially equal.
11. A sonic signal generator as recited in claim 10, wherein said
connecting means in said first circuit means further comprises a
third impedance element connecting said capacitor to said power
supply means so that the rate of charge of said capacitor is less
than the rate of voltage increase on said transducer element.
12. A sonic signal generator as recited in claim 10, wherein said
semiconductor element comprises a programmable unijunction
transistor having an anode electrode connected to said
semiconductor's second electrode and a gate electrode connected as
said semiconductor's third electrode.
13. A sonic signal generator as recited in claim 10, wherein said
semiconductor element comprises a silicon control switch having an
anode electrode connected as said semiconductor's second electrode
and a gate electrode connected as said semiconductor's third
electrode.
Description
BACKGROUND OF THE INVENTION
Audio signal generators are widely used at the present time, as for
example in the telephone art. In such applications it is of
importance to be able to operate a substantial number of the
telephone ringing circuits without imposing an undue drain on the
power supply. Various attempts have been made to provide these and
other electrically operated audio generators using as little energy
as possible while obtaining substantial audio energy output. Thus
sonic transducers such as disclosed in U.S. Pat. No. 3,331,970 have
been devised wherein a transducer such as a piezoelectric crystal
is connected to a thin metallic diaphragm forming part of an audio
speaker. In such an arrangement audio signals corresponding to the
resonant frequency of the piezoelectric element are generated.
Various other uses of transducer elements such as piezoelectric
devices are well known, particularly those wherein the transducer
is driven at its resonant frequency.
An oscillator carefully designed to have exactly the same frequency
as the piezoelectric transducer has been typically used as the
driving circuit in applications such as mentioned above. U. S. Pat.
No. 3,277,465 to Potter suggests such an approach. While a
carefully tuned oscillator can be used to drive a transducer, I
have found that the energy required to drive the transducer and the
oscillator itself is excessive, and in fact will severely limit the
number of ringing devices which can be driven by a single
source.
It is therefore an object of the present invention to provide an
efficient transducer drive circuit. Another object of the invention
is to provide a driving circuit for a piezoelectric transducer
which circuit requires an extremely small amount of electrical
operating energy.
Another object of the present invention is to provide an audio
signal generator utilizing a piezoelectric element in combination
with a controlled power switch which provides a small boost to the
piezoelectric element at a selected point in the physical movement
of the piezoelectric element.
SUMMARY OF THE INVENTION
In accordance with the teachings of the present invention a
piezoelectric transducer is connected to a power supply so that
when power is applied to the element the element will be distorted
in the manner well known in the art and attempt to vibrate at its
resonant frequency. At the time of applying energy to the
piezoelectric element a timing circuit is also provided with power.
The timing circuit and the piezoelectric element are connected to a
level detecting and comparing circuit which compares the voltage
level of the piezoelectric element with the level of the signal
from the timing circuit. The timing circuit is adjusted such that
its voltage level achieves a selected amplitude at a point in time
corresponding to the signal of the piezoelectric element
approaching a maximum. At this point in time a controlled switch
circuit connected to the piezoelectric element and to the power
supply is actuated so that a very small signal is applied to the
piezoelectric element. The applied signal is of the proper polarity
and accurately timed so that only a small boost signal is applied
to the piezoelectric element, causing it to swing through its
maximum signal condition. The controlled switch then turns off and
the transducer continues on through another cycle, the timing
circuit being reset for another cycle of operation.
By thus monitoring the voltage of the piezoelectric element and
accurately timing the application of a small "boosting" signal, the
piezoelectric element is maintained in a vibrational mode
corresponding to its inherent resonant frequency. The system is
such that the amount of energy applied to the piezoelectric element
is maintained at a minimum.
BRIEF DESCRIPTION OF THE DRAWINGS
The above and additional advantages and objects of the invention
will be more clearly understood from the following description when
read with reference to the accompanying drawings.
FIG. 1 is a block diagram illustrating the principles of a
preferred embodiment of the present invention.
FIGS. 2, 3, 4, 5 and 6 are schematic circuit diagrams illustrating
preferred embodiments of the present invention.
FIG. 2A is a waveform diagram illustrating voltages appearing at
selected points in the circuit of FIG. 2.
DESCRIPTION OF A PREFERRED EMBODIMENT
Referring now to the drawings there is illustrated in FIG. 1 a
piezoelectric transducer 10 which is provided with energy from the
power supply 11 whenever the main switch 12 is closed. The power
supply 11 also applies power to the timing circuit 13 and to the
controlled switch 14 when the main switch 12 is closed. A level
detector and comparison circuit 15 is connected to the timing
circuit 13 and to the transducer 10 and serves to compare the
voltage level appearing on the transducer 10 with the voltage of a
signal from the timing circuit 13. When the voltage levels are
substantially equal, the controlled switch 14 connected to the
detector and comparator 15 is closed. The controlled switch 14 is
connected by circuit 16 to the piezoelectric transducer 10 with the
arrangement being such that closure of the switch 14 causes a
signal to be applied to the transducer 10 at the appropriate time
in the cycle of movement thereof to assure continued vibration of
the transducer 10. The transducer 10 is preferably a part of a
sonic signal generator such as disclosed in U. S. Pat. No.
3,331,970 and thus the system of FIG. 1 provides an intense audio
signal when switch 12 is closed.
Referring now to FIG. 2 a preferred embodiment of the invention
following the concepts of FIG. 1 will be described. In the
arrangement of FIG. 2 the power supply is connected via lead 21 to
resistors 22 and 23. Resistor 23 is connected in series circuit
with resistor 24 across the power supply so that the mid-point 25
thereof is at a voltage dependent on the relative values of
resistors 23 and 24. A programmable unijunction transistor (PUT) 26
has its control electrode 27 connected to the point 25. The anode
28 is connected by lead 29 and resistor 22 to the positive terminal
of power supply 11.
Capacitor 30 is connected between resistors 22 and 31 and forms
part of the timing circuit referred to in FIG. 1. The piezoelectric
transducer 10 which also forms part of the diaphragm of an audio
signal generator is connected between points 25 and 32. It will be
seen that when switch 12 is closed current is provided to the
piezoelectric transducer via resistors 23 and 31. Thus it is
stressed and moves in the manner well known in the art. When the
switch 12 is closed the capacitor 30 also starts to charge at a
rate controlled by resistor 22. Thus the voltage on the anode of
the PUT 26 rises in a substantially linear fashion. When the
voltage on the anode 28 exceeds that on the gate 27 the PUT
conducts causing capacitor 30 to discharge and also discharging the
voltage across the transducer 10. The transducer is thus excited
and starts a positive excursion of point 25. Two complete cycles
are shown in FIG. 2A, with the time T.sub.1 corresponding to point
25 starting to go positive. The voltage at gate electrode 27 is
shown by waveform 27A and the voltage on anode 28 shown by waveform
28A. The voltages are shown relative to the negative voltage of
supply 11. As is well known in the art the PUT will remain
nonconductive when the gate is positive relative to the anode and
will start to conduct when the gate is negative with respect to the
anode.
Since the gate 27 is connected to the transducer 10 the gate
voltage follows the generally sinusoidal waveform indicated with
the PUT non-conductive till time T.sub.2. Between times T.sub.1 and
T.sub.2 the excited transducer undergoes a positive excursion and
then starts taking point 25 negative. At time T.sub.2 the
piezoelectric transducer is nearing the completion of a cycle of
oscillation, but due to friction and losses due to driving the
diaphragm the excursion amplitude is diminishing. When the voltage
at point 25 becomes less than the voltage on the anode 28 (at time
T.sub.2), the PUT 26 conducts. Capacitor 30 therefore discharges to
the negative voltage of battery 11, and point 25 is also lowered to
that voltage via the PUT gate circuit. Thus resistor 24 is shunted
and the negative excursion of the transducer receives an in-phase
signal which accelerates the excursion. This small in-phase signal
brings the excursion to full amplitude so that oscillation is
sustained.
After the transducer achieves its maximum negative excursion and
starts in the opposite direction, the voltage at point 25 again
rises above the voltage of the anode 25 at time T.sub.3 and hence
the PUT 26 is held non-conductive during the major portion of the
next cycle of the transducer. The operation is then repeated with
the voltage at point 25 again falling below the voltage of the
anode 28 at time T.sub.4. It will be seen that the oscillation of
the transducer is thereafter sustained by the repeated application
of the boosting signals.
Since the switch element 26 conducts for only a small portion of
each cycle of the transducer, and the remaining portion of the time
the switch appears as a very high impedance, the circuit
illustrated has been found to draw very little current and permits
the use of a large number of such systems on a single telephone
bell ringing circuit.
During conduction of the PUT anode 28 and gate 25 are both switched
negative at the same time. The capacitor 30 thus drives point 32
negative. However, resistor 31 performs somewhat of a cushioning
effect for the transducer from the fast wave-shape of the switch,
and thus in practice is has been found that the voltage across the
transducer is substantially simusoidal.
FIG. 3 is a schematic circuit diagram of an arrangement similar to
that of FIG. 2 and also making use of a programmable unijunction
transistor as the controlled switch. In the circuit of FIG. 3
resistors 43, 44 and 45 are connected in series circuit across the
power supply 11 with the piezoelectric transducer 10 being
connected in parallel with resistor 45. Resistor 42 and capacitor
50 are connected in series circuit from the positive terminal of
power supply 11 to one side of the transducer 10. The other side of
the transducer 10 is connected to the gate 47 of the PUT 46. The
anode 48 is connected to the junction of resistor 42 with capacitor
50.
The operation of the circuit shown in FIG. 3 is substantially the
same as the operation of the circuit of FIG. 2 with resistor 45
acting as part of the discharge circuit for the crystal 10. As in
the case of the circuit of FIG. 2, when the piezoelectric element
10 starts its positive excursion, the voltage on the piezoelectric
element holds the gate 47 positive with respect to the voltage on
the anode 48 and hence the PUT is held against conduction until the
crystal is on the negative portion of its excursion. Then in the
manner previously described, the PUT becomes conductive so that the
"boosting" signal is applied to the crystal in the manner described
above.
FIG. 4 shows a circuit substantially the same as the circuit of
FIG. 3 with the exception that the controlled switch in the circuit
of FIG. 4 is a silicon controlled switch (SCS). With the circuit
arrangements of FIGS. 3 and 4 the impedance of the power source is
typically lower in the case of FIG. 2, which is adapted for use
with a high impedance power supply.
In the circuit of FIG. 5 resistors 64 and 65 are connected across
the power supply and provide the bias voltage for the base of
transistor 63. The emitter of the NPN transistor 63 is connected to
the gate of the PUT 66 and to one side of the piezoelectric
transducer 10. The capacitor 70 is connected in series circuit with
resistors 61 and 62 across the power supply and is also connected
to the other side of the piezoelectric transducer 10. The anode of
the PUT 66 is connected to the capacitor 70 and to resistor 62. A
second capacitor 67 connects the emitter of the transistor 63 with
its base. It will be seen that the circuit of FIG. 5 corresponds in
principle to the circuit of FIG. 2 with the transistor 63
essentially taking the place of resistor 23 in FIG. 2. The
transistor 63 looks like a few ohms on the positive cycles of the
transducer 10, since during that time the transistor conducts.
However, during the negative cycles the transistor looks like
several megohms. As in the case of FIG. 2 will be seen that the PUT
compares the signal from the timing circuit (which includes
capacitor 70) with the signal from the transducer and controls the
application of the small boosting signal in the small manner as
previously described.
In the circuit arrangement of FIG. 6 a PNP transistor 75 serves as
the level detector and the NPN transistor 76 serves as the
controlled switch. As an aid to understanding the invention the
various circuit components are contained within the functional
blocks formed by the dashed lines. It will be seen that the base of
transistor 75 and the collector of transistor 76 are connected to
the junction of resistors 73 and 74. The emitter of transistor 75
is connected to the positive power supply terminal by the resistor
72. Resistor 71 connects one side of the transducer to the negative
power supply terminal and resistor 74 connects the other side of
the transducer as well as the base of transistor 75 to the negative
power supply. Capacitor 80 connects one side of the transducer to
the emitter of the level detecting transistor 75. The operation of
the circuit of FIG. 6 corresponds in general to the operation of
the circuit of FIG. 2. That is, when power is applied to the
circuit, current momentarily flows through resistors 71 and 73,
exciting the transducer 10. At the same time the capacitor 80
starts to charge via resistor 72. When the voltage on the emitter
of transistor 75 exceeds the voltage on the base, transistor 75
starts to conduct current through resistor 72 and also from
capacitor 80. Current is thus supplied to the base of transistor 76
so that transistor 76 conducts drawing current from the base
circuit of transistor 75 and hence insuring complete conduction of
both transistors. Resistor 74 is thus shunted by transistor 76, and
the piezoelectric transducer 10 is therefore discharged, causing
its complete excitation. It will be seen that capacitor 80 will
also be completely discharged through the emitter-collector
junction of transistor 75 and the base-emitter junction of
transistor 76. Resistor 72 does not provide sufficient current to
hold transistors 75 and 76 conductive, and therefore the circuit
reverts to its original nonconducting mode. When this occurs, the
now excited transducer begins a positive excursion on the side
connected to the base of transistor 75, assuring non-conduction of
transistor 75. At the same time, the capacitor 80 starts charging
toward the positive voltage of the power supply through resistor
72. The rate at which capacitor 80 is permitted to charge is
adjusted so that the voltage on the base of transistor 75 runs
ahead of the voltage on the emitter of transistor 75 (in the manner
indicated in the wave diagrams of FIG. 2A) and hence the transistor
75 remains non-conductive until the negative excursion of the
transducer occurs. During the negative excursion of the transducer,
the base of transistor 75 goes slightly negative with respect to
the rising voltage on the emitter, and hence the transistor 75 acts
as a level detecting circuit and voltage comparator, causing
transistor 76 to become conductive at the appropriate point in the
negative excursion of the transducer. Thus the small "boosting"
signal is applied to the transducer in the manner previously
described.
While the values of the circuit components will vary in accordance
with a particular circuit, the following values were used in the
circuit of FIG. 2: resistors 22 and 24 were each 1 megohm, resistor
23 was 100,000 ohms, resistor 31 was 1,000 ohms, and capacitor 30
was 0.002 microfarads. The power supply was 26 volts, although it
has been found that the circuits described herein will operate over
a wide variation of voltage ranges. For example, the circuit of
FIG. 5 has been found to work with voltages ranging from 1.5 volts
to 160 volts.
It will be recognized, of course, that while the circuits disclosed
in detail are shown for applying a small "booting" signal to the
transducer on one side of each cycle, the concept can be utilized
to apply a boosting signal to each side of the cycle. However, in
practice I have found that with the circuit arrangements
illustrated, a very small current drain on the power supply
results, even through a substantial volume of audio energy is being
generated.
While the invention has been described by reference to presently
preferred embodiments, it is intended that the following claims
will encompass those changes and modifications which become obvious
to a person skilled in the art as a result of teachings hereof.
* * * * *