U.S. patent number 3,737,906 [Application Number 05/199,900] was granted by the patent office on 1973-06-05 for electrically steerable aircraft mounted antenna.
Invention is credited to Lawrence A. Maynard.
United States Patent |
3,737,906 |
Maynard |
June 5, 1973 |
ELECTRICALLY STEERABLE AIRCRAFT MOUNTED ANTENNA
Abstract
The application discloses an electronically steerable
aircraft-to-satellite antenna system using a linear series of
parallel dipoles fed through phase-shifting controls. By variation
of the phase-shift to the various dipoles, different cones of
radiation (or preferred reception) are provided. The cone axes are
parallel to or coincident with the longitudinal axis of the
aircraft, so that aircraft roll has little effect on the
orientation of the cone.
Inventors: |
Maynard; Lawrence A. (Almonte,
Ontario, CA) |
Family
ID: |
22739477 |
Appl.
No.: |
05/199,900 |
Filed: |
November 18, 1971 |
Current U.S.
Class: |
343/705; 343/814;
342/371 |
Current CPC
Class: |
H01Q
3/30 (20130101) |
Current International
Class: |
H01Q
3/30 (20060101); H01q 001/28 () |
Field of
Search: |
;343/705,708,854,814 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Lieberman; Eli
Claims
What is claimed is:
1. An electrically steerable antenna system for use in an airborne
communications system to provide communications between an aircraft
and an orbiting satellite comprising:
an antenna comprising a fixed linear array of dipole elements
mounted on the upper parts of the aircraft on a common axis
parallel to the longitudinal axis of the aircraft;
phase shifting means connected to the array of dipole elements for
introducing into a signal to be communicated a predetermined phase
shift between adjacent dipole elements to produce an annular lobe
of maximum radiation in the form of a hollow cone with its apex at
the array and its axis collinear with the axis of the array;
means for applying the signal to be communicated to the phase
shifting means; and,
means for varying the apex angle of the cone of radiation to
include the orbiting satellite within the lobe of maximum radiation
regardless of the relative orientations of the aircraft and
satellite.
2. The antenna system of claim 1 wherein the means for varying the
apex angle of the cone of radiation comprises means for varying the
phase shift introduced between adjacent dipole elements.
3. The antenna system of claim 2 wherein said array of dipole
elements comprises at least three elements.
4. An antenna system as claimed in claim 1 wherein the number of
elements in the array is nine.
5. A method of communication between an in-flight aircraft having a
fixed linear dipole array antenna mounted on the upper parts of the
aircraft on a common axis parallel to the logitudinal axis of the
aircraft and an orbiting satellite which comprises:
radiating from the antenna the signal to be communicated as an
annular lobe of maximum radiation in the form of a hollow cone with
its apex at the array and its axis parallel to the longitudinal
axis of the aircraft; and
adjusting the apex angle of the cone to include the orbiting
satellite within the lobe of maximum radiation.
6. The method of claim 5 wherein the step of radiating the signal
comprises:
applying the signal to one end of the linear array; and,
shifting the phase of the signal between adjacent dipoles as it
passes to the other end of the array.
7. The method of claim 6 wherein the step of adjusting the apex
angle of the cone comprises varying the phase shift between
adjacent dipoles.
Description
STATEMENT OF GOVERNMENT INTEREST
The invention described herein may be manufactured and used by or
for The Government of the United States of America for governmental
purposes without the payment of any royalties thereon or
therefor.
BACKGROUND OF THE INVENTION
1. Field of the Invention
This invention relates to electrically steerable antenna systems,
and finds particular application in airborne mobile communications
system intended for communication with an orbiting satellite.
Use of an omni-directional antenna on a mobile platform enables
communication between the mobile platform and a satellite whatever
the bearing and elevation of the satellite (as long as it is radio
range) but on the other hand such an antenna is inefficient as
regards the transmission of energy towards the satellite and
provides no rejection of signals from noise sources during
reception. In order to provide an acceptable level of
effectiveness, some form of directional antenna in combination with
some form of steering of the antenna is necessary.
2. Description of the Prior Art
It is known to utilize for communication purposes antennas which
are directional and which are physically steerable, and these are
used both for UHF systems, in which arrays of dipoles are used as
the antenna, and for systems for frequencies above UHF, in which
latter systems sheet metal antennas are usually used. It is also
known, for UHF systems, to use fixed antenna arrays of dipoles
having radiation patterns which can be modified by varying the
relative phases of the energizing signals applied to the different
dipoles. To utilize such a system, of electronically steerable
dipole arrays, for an aircraft communication system, is of great
interest since the mechanical steering of antennas in this
environment is difficult and sometimes impossible. In considering
the airborne antenna system, a two-dimensional angular steering of
a conventional phased dipole array is necessary, and the associated
control circuitry is complex.
SUMMARY OF THE INVENTION
According to one aspect of the present invention, an antenna system
comprises at least three doublet elements arranged coaxially and
spaced apart, together with means adapted to apply a common signal
to all the elements but with a progressive change in the phase of
the signal as received by the elements in one sense along the
length of the array, the means adapted to apply the common signal
being adjustable to permit a change in the rate of the progressive
change in the phase, whereby by operating the antenna system at
different rates of change of the progressive change in phase,
different annular conical lobes of radiation, or of selective
sensitivity to radiation, are produced centered on the common axis
of the elements.
According to another aspect of the invention, a method of producing
an annular conical, or a part-annular-conical lobe of radiation or
of selective sensitivity to radiation, comprises effecting a
variable pattern of phase shifts to signals passing between an
input/output lead and a coaxial array of at least three doublet
elements, the pattern being such that the phase shifts associated
with the doublet elements vary in a progressive manner in one sense
along the length of the array in such a manner as to produce the
annular conical, or the part-annular-conical lobe, and the pattern
being varied so as to change the half-angle of the lobe cone.
OBJECT OF THE INVENTION
An object of the present invention is the provision of an
electronically steerable antenna system suitable for particular
applications and for those applications providing a system which
offers a marked reduction in both cost and complexity.
Other objects, advantages and novel features of the invention will
become apparent from the following detailed description of the
invention when considered in conjunction with the accompanying
drawing.
BRIEF DESCRIPTION OF THE DRAWINGS
The invention will now be described, by way of example, with
reference to the accompanying drawings, in which:
FIG. 1 is a plan view of an antenna system according to the present
invention;
FIG. 2 is a side elevation of the effective radiation produced by
the antenna system of FIG. 1 in free space;
FIG. 3 is a diagram showing the different zones of effective
radiation produced at the plane III--III of FIG. 2 under different
conditions of operation;
FIG. 4 is a diagram of the typical lobing structure of an array
such as that shown in FIG. 1;
FIG. 5 is a graph showing the relationship between launch angle and
beam width (in degrees) of antenna such as those shown in FIG. 1
but with varying numbers of dipole elements; and
FIG. 6 is a perspective drawing of an aircraft carrying an antenna
array such as that shown in FIG. 2, and also shows schematically
the effective lobes produced by that antenna system when operating
under different conditions.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
Referring first to FIG. 1, the antenna system illustrated comprises
nine dipoles 1A to 1I, the nine dipoles being arranged parallel and
linearly on an axis 2. The spacing between adjacent dipoles is not
critical, but the spacing will affect the radiation pattern
obtained when the various dipoles are energized with signals from
the same source but at different phases. In the example shown, the
spacing between adjacent dipoles is one-half (wavelength), and each
dipole has an overall length of one-half (wavelength).
All nine dipoles are fed from a common input/output lead 3 through
a phasing unit 5. This unit introduces different delays to a common
signal as it passes to leads 7 leading respectively to the various
dipoles.
As will be appreciated by those skilled in the art, the lengths of
at least most of the leads 7 will exceed one wavelength, and the
lengths of the various leads will thus affect the phase of the
signals actually reaching the dipoles. For any given channel, the
relative phase shifts introduced by the leads must be taken into
account. For an antenna system intended to operate on several
channels, it may be simpler to ensure that all the leads 7 have the
same length, so that phase shift in the leads 7 will be equal for
all dipoles at all frequencies.
Bearing the above points in mind, the phasing unit 5 is arranged to
enable the relative phases of the signals applied to the different
dipoles to be varied. When the signals applied to all the different
dipoles have the same phase, the overall radiation pattern of the
array will have a lobe of maximum radiation extending normally from
the array axis 2. According to the present invention, the signals
applied to the dipoles vary progressively in phase from one end of
the array to the other end, in the same sense, i.e., either with
progressively increasing amounts of phase lag or with progressively
increasing amounts of phase advance. In these circumstances, a lobe
of maximum radiation will be produced in the form of a hollow cone
with its apex at the array and with its axis colinear with the axis
of the array, as indicated in FIG. 2 by the hollow cone 11.
By using the phasing unit 5 to vary the amount of phase lag or
phase advance along the array from dipole to dipole, the cone
half-angled (see FIG. 4) can be varied. Thus, by changing the phase
shifts involved, it is possible to obtain different hollow cones of
effective coverage by the antenna system. FIG. 3 indicates this
point, and shows the annular form of three different lobes
designated 11A, 11B and 11C, obtained in this manner.
A partial set of beams generated by a linear array of .lambda./4
dipoles mounted on the surface of an aircraft 21 may look somewhat
like that shown in FIG. 6. In this case, only the upper half-cones
23, 25, 27, 29, 31, 33, 35 and 37 and the central disc 39 are
present because of the shadowing effect of the aircraft.
The power gain G.sub.A of such an array will be approximated by
G.sub.A = N G.sub.R (1)
where N = the number of elements in the array and G.sub.R is the
gain of a single element. This only holds, of course, provided that
the effective apertures of the array elements are not overlapping
and no serious interaction is occuring.
It is interesting to note that such an array is capable of scanning
a complete hemisphere by varying the single parameter 0, the
half-angle of the cone apex, (see FIG. 4).
The approximate power gain of an array of isotropic radiators
G.sub.i is given by ##SPC1##
when the beamwidths are measured at the -3 db points. The angular
area A.sub.x of cone with apex half-angle .theta. - .phi./2 is
given by
A.sub.x = .pi. [.theta. - (.phi./2)] 2
The angular area A.sub.y of cone with apex half-angle .theta. +
(.phi./ 2) is given by A.sub.A.sub.y = .pi. [.theta. + (.phi./2)]
2
The angular area A.sub.1 of radiated beam A.sub.1 is given by
A.sub.1 = A.sub.y - A.sub.x
= .pi. [.theta. + (.phi./2)] 2 - .pi. [.theta. - (.phi./2)] 2
A.sub.1 = 2 .pi. .theta. .phi.
So for the case of a single conical beam
G = (4 .pi.)/ A.sub.1 = 2/(.theta. .phi.)
and for several equal amplitude conical beams
G = 4 .pi./(A.sub.1 + A.sub.2 + ...) = 2/(.theta..sub.1 .phi..sub.1
+ .theta..sub.2 .phi..sub.2 + ...)
EXAMPLE
Consider the case where N = 9
n = 1
.theta. = 60.degree. = 0.954 rad.
G = N = 9
.thrfore. G = 9 = 2/(.theta. .phi.) = 2/(0.954 .phi.)
.phi. = 2/(0.954 .times. 9) = 0.233 rad. = 13.33.degree.
The measured -eamwidth from a synthesized pattern was 10.5.degree.
at -3dB. For an end-launched beam, .theta. = .phi./2 and
therefore
G = 9 = 2/(.theta. .phi.) = 4/(.phi..sup.2)
.phi..sup.2 = 4/9
.phi. = 2/3 = 38.2.degree.
FIG. 5 shows curves relating beamwidth to launch angle for arrays
with 3, 5, 7, 9 and 18 elements. A single quadrant is plotted since
quadrant symmetry exists.
In the U.H.F. band, fairly large effective apertures can be
achieved using only a few elements. For example, an array of nine
.lambda./4 dipoles will provide an effective aperture of about 1.5
square meters and a gain of about 13 db/iso at 250 MHz.
The minimum azimuthal beamwidth for such an array occurs broadside
i.e., at 39 and equals about 8.degree..
Only a few (.apprxeq.12) sets of lobes generated by such an array
will suffice to complete hemispherical coverage, and therefore the
technique is well suited to a switched-array antenna system.
It is common practice to utilize a single antenna array both to
transmit a signal and to receive a signal. The above description
has, for the sake of simplicity, dealt basically with the
transmission of a signal, the antenna array being effective to
produce an annular conical radiation lobe, or a
part-annular-conical radiation lobe. When such an antenna array is
used to receive a signal, all the dipoles will receive the signal
and the signal will be transmitted through the leads 7 to the
phasing unit 5, where the signals from the various leads 7 will be
phase shifted by varying amounts before being fed to the
input/output lead 3. The net result is that for a phase shift
arrangement which would give the radiation lobe 11 of FIG. 2 during
transmission, the lobe 11 will be a lobe of selective sensitivity
to radiation coming to the antenna array.
In the specific embodiment of the invention described above, the
elements of the antenna system have been described as dipoles. It
will be appreciated that a variety of radiating elements, including
doublets, may be used, the distinction being that a dipole is a
doublet which has a length so related to the frequency at which it
is used that the overall length of the doublet is a half-wavelength
at that frequency.
Although it will usually be simpler to effect the change, in the
rate of change in phase along the array, in a step like manner to
produce in sequence a number of different annular conical, or
different part-annular-conical, lobes of radiation, or of selective
sensitivity to radiation, the different lobes overlapping one
another, the present invention includes in its scope the concept of
changing the rate of change in phase along the array in a
progressive manner. The effect then produced will be of the nature
of a radiation lobe which has a progressively changing cone
half-angle.
It will be seen that in the arrangement shown in FIG. 6 two sets of
half-cones are shown, one extending forwardly of the aircraft and
one extending rearwardly from the aircraft. This change in
direction is effected by changing the sense in which the signal
phases change along the length of the array. Thus, during
transmission in one instance the signals on the forward elements of
the array will lag the signals on the rearward elements of the
array; while in the other instance the signals on the rearward
elements of the array will lag the signals on the forward elements
of the array. The exact manner in which this will be done is
largely a matter of design. If it is desired to make use only of
devices which introduce a lagging phase shift in the phasing unit
5, this is readily achieved by the use of such devices in
conjunction with each of the leads 7. When it is desired to produce
a forwardly directed lobe, then these devices can be adjusted to
produce zero phase lag at one end of the antenna array and a
progressively increasing phase lag along the series of elements,
while when it is desired to produce a rearwardly directed lobe,
then these devices can be adjusted to produce zero phase lag at the
other end of the antenna array, and a progressively increasing
phase lag along the series of elements.
It will be appreciated that the antenna array described above has
many advantages, the most important of which may be summarized as
follows:
1. Such an array is capable of complete hemispherical coverage by
varying a single array parameter, i.e., the cone angle. In the
conventional 2-dimensional arrays, two angular parameters must be
varied to allow complete hemispherical coverage.
2. The simple steering technique results in drastically simplified
phase control networks.
3. The most rapid angular maneuver, in large, transport type
aircraft, is that of bank or roll. If the linear array is spaced
along, or parallel to the roll axis of the aircraft, no beam change
or little beam change is required to maintain communication with a
satellite.
4. This technique is particularly appropriate at UHF, where the
angular thickness of the conical beam structure is several
degrees.
With the arrangement of doublets shown in FIG. 1, a radiation
pattern "hole" exists in that no effective radiation can be
produced vertically (assuming the aircraft is flying horizontally).
In the unusual case of the aircraft flying under the satellite,
this could create a problem. If such conditions are anticipated,
the elements used can be so-called "bent-monopole" elements. These
elements are commercially available.
* * * * *