U.S. patent number 3,732,465 [Application Number 05/181,865] was granted by the patent office on 1973-05-08 for electronic sensing and actuator system.
This patent grant is currently assigned to Charles A. Walton. Invention is credited to Ronald S. Palmer.
United States Patent |
3,732,465 |
Palmer |
May 8, 1973 |
ELECTRONIC SENSING AND ACTUATOR SYSTEM
Abstract
An electronic sensing and actuator control system for sensing an
energy change dependant on the proximity of a coded member to a
sensor mechanism, the mechanism including an electric field
producing means operative over a range of continuously varying
frequencies; the coded member including a passive energy absorbing
circuit responsive to a predetermined frequency range and adapted
for placement in proximity to said mechanism to create a variation
in the energy level of said electric field producing means;
detecting means for detecting variations in the energy level of
said electric field; and control-actuator means adapted to respond
to the detecting means.
Inventors: |
Palmer; Ronald S. (San Jose,
CA) |
Assignee: |
Walton; Charles A. (Los Gatos,
CA)
|
Family
ID: |
22666131 |
Appl.
No.: |
05/181,865 |
Filed: |
September 20, 1971 |
Current U.S.
Class: |
340/5.61;
361/182; 340/10.3; 331/177V; 361/203 |
Current CPC
Class: |
G06K
7/086 (20130101); G07C 9/28 (20200101); G07C
9/00714 (20130101) |
Current International
Class: |
G06K
7/08 (20060101); G07C 9/00 (20060101); E05b
049/00 () |
Field of
Search: |
;317/134,146 ;340/147F
;331/177V |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Hix; L. T.
Claims
I claim:
1. An electronic sensing and actuator control system for
controlling an actuator, the system comprising, in combination:
a variable frequency oscillator means adapted to repeatedly sweep
through a range of operating frequencies and generate a field at
said operating frequencies within a sensing zone, the oscillator
being adapted to generate an energy level signal representative of
the energy level of the output field;
a key unit means adapted to be transported to said sensing zone,
the key unit comprising a field sensitive circuit having at least
one selected resonant frequency, said resonant frequency being of a
value within the range of frequencies of said oscillator;
an energy level detector means for receiving said energy level
signal, detecting variations in the energy level of the oscillator
means and generating a responsive detection output signal
responsive to the energy level of the oscillator means;
a controller network adapted to be responsive to the detector
output signal to generate responsive control signals for
controlling an actuator mechanism; and
means for interconnecting the controller network to an actuator
mechanism.
2. The system of claim 1 in which
the variable frequency oscillator means is adapted to repeatedly
sweep through a range of operating frequencies and generate an
electrical field at said operating frequencies within a sensing
zone, the oscillator being adapted to generate an energy level
signal representative of the energy level of the output field;
and
the key unit means adapted to be transported to said sensing zone,
the key unit comprising an electrical field sensitive circuit
having at least one selected resonant frequency, said resonant
frequency being of a value within the range of frequencies of said
oscillator.
3. The system of claim 2 further including
a comparator network for comparing the actual frequency of the
oscillator means to at least one preselect frequency, the
comparator network adapted to generate a responsive comparator
control signal responsive to the relationship of said actual
frequency and said preselected frequency.
4. The system of claim 3 in which the controller means is adapted
to respond to said detector output signal and said comparator
control signal.
5. The system of claim 4 in which
the detector means is adapted to generate a first detector output
signal state responsive to variations in energy level of the
oscillator means and a second detector output signal state
responsive to the steady state energy level of the oscillator
means;
the comparator network is adapted to generate a first comparator
output signal state responsive to coincidence of the actual
frequency of the oscillator and said selected resonant frequency
and a second comparator output signal state responsive to the
absence of coincidence of the actual frequency of the oscillator
and said selected frequency; and
the controller network is adapted to respond in at least two
different modes, one of said modes being in response to receiving
the first detector output signal state and the first comparator
output signal state and another of said modes being in response to
receiving the first detector output signal state and the second
detector output signal state.
6. The system of claim 5 in which
the key unit means includes passive electronic components joined in
a circuit of said selected resonant frequency.
7. The system of claim 6 in which
the oscillator means is in the form of a voltage frequency
oscillator adapted to sweep through a range of frequencies
responsive to a sweep reference voltage; and including
a sweep voltage source adapted to generate a sweep reference
voltage and engaged to the oscillator means to control the
frequency of the oscillator.
8. The system of claim 7 in which
the comparator network is in the form of a voltage comparator, the
comparator being engaged to the sweep voltage source to receive
said sweep reference voltage, the comparator network further
adapted to receive at least one preset reference voltage of a fixed
value, each of said preset reference voltages being adapted to be
preset of a value corresponding to one of said selected resonant
frequencies.
9. The system of claim 8 in which
the energy level detector means includes an input means for
receiving said energy level signal and first differentiating means
for differentiating said energy level signal and producing a signal
representative of the rate of change of the peak amplitude of said
energy level signal.
10. The system of claim 9 in which
the energy level detector means further includes a second
differentiating means for differentiating the signal of said first
differentiating means for producing a signal representative of the
peak of said energy level signal.
11. The system of claim 10 in which
the controller network includes a logic AND gate extending to the
comparator network and to the detector means and adapted to
generate a control signal responsive to the time relationship of
said comparator output signal state and said detector output signal
state; and
an actuator mechanism adapted to respond to the control signal of
said AND gate.
12. The system of claim 1 further including
a digital-to-analog converter for generating a frequency reference
voltage responsive to input digital signals for controlling and
converter, the counter means being responsive to a clock means
extending to the counter means through a disabling means, said
disabling means being adapted to disable the counter responsive to
a control demand of the controller network.
13. The system of claim 12 in which
the controller network is in the form of an AND gate adapted to
respond to said detector output signal and to said disabling means,
an OR gate adapted to respond to said AND gate output and said
counter such that the counter is disabled responsive to said
detector output signal.
14. The system of claim 7 in which
the key unit means includes a plurality of electrical field
sensitive circuits each having a select resonant frequency, each of
said resonant frequencies being of a value within the range of
frequencies of said oscillator.
Description
BACKGROUND OF THE INVENTION
The present invention relates to apparatus for electrically sensing
the proximity of an object and remotely controlling the actuation
of an actuator responsive to the proximity of said object.
Electronic sensing and actuator control systems have various
applications. There are applications in the processing or
manufacturing of items in which items need be processed such as
sorted, counted or tested. Other applications may include locking
systems to secure designated areas from access by unauthorized
persons or objects.
A lock system generally requires a portable code device, e.g., key
to be utilized to actuate a locking to permit access to the secured
area. The lock and key are programmed such that actuation of the
lock is dependent upon coincidence between the program of the lock
and the program of the key. In an electronic locking system the key
program controls the actuation of an electrical circuit which, in
turn controls actuation of the lock. Commonly, in electronic
locking systems, in order to actuate the lock, the "key" is in the
form of a card which need be inserted in a slot or socket or make
other physical connection.
In various installations it is desirable to have locking systems
which may be controlled by various different programs. For example,
a "master key" is commonly desirable in order to entitle different
authorized persons access to the secured area but at the same time
it is necessary that the "master key" have a different code than
other authorized "keys." Further, it is commonly desirable to have
the locking system non-conspicuous and hidden from view. It is
further commonly desirable to incorporate a locking system which
does not require alteration of the area to create a key receiving
station such as a slot, socket, etc.
The present invention teaches an improved electronic sensing and
actuator control system which operates by proximity of the coded
member to the sensor. When applied as an electronic lock the
present invention does not require the aid of slots, sockets or
physical connection for receiving the "key." It further teaches an
actuator which may be adapted to respond to a plurality of coded
programs.
SUMMARY OF THE PRESENT INVENTION
The present invention teaches an electronic sensing and actuator
control system responsive to the proximity of an object to be
sensed. The object to be sensed need not necessarily make physical
contact with any other part of the apparatus but need only be
brought into a sensing zone including the electrical field
generated by an electrical part of the apparatus. The electrical
part of the apparatus is adapted to sense the proximity and the
coded program of the object and to generate a responsive control
signal to an actuator mechanism in turn adapted to perform a
designated function. As a locking system, the object to be sensed
may be referred to as the "key." The "key" may consist of a card
composed of interconnected passive electronic components, e.g.,
inductors, capacitors, resistors and/or crystals, such that the key
may be readily transported by an individual to and from the sensing
zone. The apparatus is adapted to actuate the lock when the proper
key is sensed. The apparatus may be further adapted to sense and
actuate an alarm if an incorrectly programmed key is brought in the
sensing zone in an attempt to actuate the lock.
In an exemplary embodiment of a locking system, the key is in the
form of a portable card comprised of passive inductance-capacitance
elements establishing at least one resonant frequency. The
electrical part of the apparatus includes a variable frequency
oscillator adapted to continuously oscillate at varying frequencies
within a frequency range. The electrical part of the apparatus
creates an electrical field within a sensing zone in which zone the
key may be brought for sensing. The electrical part of the
apparatus includes a sweep voltage source extending to the
oscillator adapted for controlling the oscillator frequency
responsive to the sweep voltage. The sweep voltage source further
engages a comparator network adapted to compare the sweep voltage
to select reference voltages. The select reference voltages are
selected according to desired frequencies such that the comparator
may compare the actual sweep voltage to the reference voltages. The
comparator network is adapted to generate a first comparator signal
when the actual sweep voltage coincides with a selected reference
voltage.
A detector network extends to the oscillator to detect the energy
level of the oscillator and to detect the presence of the load on
the oscillator. The energy level of said oscillator varies with
varying load and the load varies as the key is brought into the
sensing zone and the oscillator frequency approaches the resonant
frequency of the key. The detector in turn generates a control
signal responsive to the load conditions of the oscillator.
A controller network extends to the detector and to the comparator.
The controller is adapted to control the actuator mechanism
responsive to the relationship of the detector control signals and
the comparator control signals.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a schematic illustration of an installation of an
electronic sensing apparatus and control mechanism incorporating
the teachings of the present invention and applied as an electronic
lock system;
FIG. 2 is a functional block diagram of the electronic apparatus
and control mechanism of FIG. 1;
FIG. 3 is a circuit diagram of a variable frequency oscillator of
FIG. 2;
FIG. 4 is a circuit diagram of a voltage sweep generator of FIG.
2;
FIG. 5 is a circuit diagram of a comparator network of FIG. 1;
FIG. 6 is a circuit diagram of a detector network of FIG. 1;
FIG. 7 is a graphical representation of pulse-time relationships of
the circuit networks of FIGS. 5 and 6;
FIG. 8 is an exploded illustration of a key of FIG. 1; and
FIG. 9 is a functional block diagram of an alternative embodiment
of the present invention.
DESCRIPTION OF PREFERRED EMBODIMENTS
FIG. 1 illustrates an application of an electronic sensing and
actuator control system of the present invention as utilized in an
electronic locking system for securing a door 10 in turn
controlling access to an enclosed area 11. The electronic sensing
and control system may include a sensing network referred to by the
general reference character 12 and a programmed key referred to by
the general reference character 13. The sensing network 12 in turn
may control an electro-mechanical actuator in the form of a lock 14
responsive to the proximity and the program of the key 13. The key
13 is a passive circuit adapted to include an electrical-field
sensitive circuit or circuits having a selected resonant frequency
or frequencies of a value within the range of frequencies of the
oscillator 12. The sensing network 12 may be placed on the reverse
side of the door 10 or at some other position remote from the lock
14. If desired, the door 10 may be marked by appropriate
designations such as by lines 15 to designate a sensing zone at
which location the key 13 may be presented for sensing by the
network 12. In operation, when a key of a selected resonant
frequency is within the sensing zone 15 the lock 14 may be
actuated. If the key resonant frequency does not coincide with a
select resonant frequency, the lock 14 is not actuated.
As illustrated in the block diagram of FIG. 2, the network 12 may
include a variable frequency oscillator 20 including an output coil
22 which coil is positioned adjacent to the sensing zone 15 on the
reverse side of the door 10. The oscillator 20 is engaged to a
sweep voltage source 23. The sweep voltage source 23 continuously
generates the sweep voltage v.sub.f which, in turn, continuously
varies the frequency of the oscillator 20. The frequency of the
oscillator 20 may be a direct function of v.sub.f, e.g., one
megahertz per volt. At the same time the sweep voltage source 23
extends to a comparator network, in the form of a window comparator
24 with v.sub.f continuously applied to said comparator. A second
voltage Vref., representative of a desired frequency is also
applied to the comparator. The value of Vref. is preselected
according to at least one of the programmed frequencies of the key
13. The window comparator network 24 is adapted to continuously
generate binary logic "one" and "zero" signals responsive to the
comparison of the voltage v.sub.f to the preset reference voltage
Vref. For example, the comparator 24 may generate a binary logic
"one" when v.sub.f coincides with Vref. and a binary logic "zero"
for all other values of v.sub.f. Thus, the logic "one" comparator
signal indicates coincidence of the actual frequency of the
oscillator 20 and the preselected frequency and logic "zero"
comparator signal indicates the absence of coincidence of the
actual frequency of the oscillator 20 and the preselected
frequency.
The energy level of the oscillator 20 is sensed by a detector
network 25. The detector 25 is adapted to receive a sense voltage
designated v.sub.d from the oscillator. The voltage v.sub.d remains
substantially at a steady state level in the absence of variations
of the oscillator load. The oscillator load and energy level are a
function of passive reactive elements in the sensing zone 15.
Accordingly, the detector 25 network generates binary logic signals
responsive to changes in the energy level of the oscillator 20.
During the steady state energy level of the oscillator 20 the
detector 25 generates a binary logic "zero" control signal. When a
reactive circuit is sensed with the sensing zone and the frequency
of the oscillator 20 approaches the resonant frequency of the
sensed circuit, the oscillator energy level varies and the value of
v.sub.d varies. The detector 25 responds to the change in v.sub.d
and generates a binary logic "one" control signal.
The comparator 24 and the detector 25 extend to a controller
circuit network 26. The network 26 is adapted to operate in
different modes dependent on the logic signals received from the
comparator 24 and the detector 25. The controller 26 includes a
first logic AND gate 27 having an input line 28 from the detector
25 and an input line 30 from the output of the comparator network
24. The AND gate 27 has an output line 32 which extends to an
unlock control circuit 34 to control the lock 14. The unlock
control circuit 34 may extend to a solenoid actuator 36 which is
also joined to a power source + V such that in a first mode the
actuator 36 may be actuated.
A second logic AND gate 38 is included and having a pair of input
lines 40 and 42 with the input line 40 common to the detector 25
and the input line 42 extending from the output of a logic inverter
network 44. The input of the inverter 44 is common to the output of
the comparator 24. The AND gate 38 has an output line 46 extending
to an alarm control circuit 48.
Thus in the event the energy level of the oscillator 20 varies
responsive to a key in the sensing zone 15, the sense signal
v.sub.d varies from a steady state level and the detector 25
generates a logic "one" signal. The detector "one" signal is
applied simultaneously to both AND gates 27 and 38. If the sensed
signal v.sub.d is at the programmed desired frequency as
established by Vref., the comparator network 24 simultaneously
generates a logic "one" control signal which is received by the
gate 27 such that the gate 27 is actuated and generates a logic
"one" on the line 32 to the unlock control circuit 34 and to the
actuator solenoid 36 to activate the lock actuator. In the event
that the sensed signal v.sub.d is at a frequency within the
oscillator frequency range but at a frequency other than the
desired frequency, the detector 25 generates a logic "one" signal.
However, the comparator network 24 simultaneously generates a logic
"zero" control signal. The logic "one" and "zero" signals are
received by the gate 27 but the gate 27 is not activated. The
inverter 44 receives the comparator logic "zero" and inverts it to
a logic "one" on the line 42 and to the AND gate 38. The AND gate
38 also receives the logic "one" from the detector 25. Accordingly,
the AND gate 38 is activated and generates a logic "one" on the
line 46 to the alarm circuit 48 to actuate the alarm 50 indicating
that a key having a resonant frequency other than the desired
frequency has been detected.
FIG. 3 is a circuit diagram of a variable frequency oscillator 20
which may be incorporated in the acutator 12. The variable
frequency oscillator 20 includes a common base transistor
oscillator having an NPN transistor 51 with the collector and
emitter tied across a capacitor 52. The output coil 22 which forms
a part of the tank circuit for the oscillator 20 is tied in common
to the collector and in common to a capacitor 54 in turn common to
a voltage variable capacitance in the form of a varactor 56. The
common junction of the capacitor 54 and varactor 56 is common to a
choke coil 58 extending to the sweep voltage source 23 to receive
the sweep voltage v.sub.f. The common junction of the capacitor 54
and coil 22 are common to the voltage source + V. The emitter of
the transistor 51 is common to a resistance 60 which extends to
ground. The base of the transistor 51 is common to a
resistance-capacitance filter network having a capacitor 62 and a
resistance 64 both common to ground. The base of the transistor 51
also extends through a resistance 66 to the voltage source + V. In
operation the oscillator 20 generates a continuously varying
frequency depending upon the value of the voltage v.sub.f from the
sweep voltage source 23. The capacitor 52, the varactor 56 and the
load coil 22 determine the frequency of oscillation. Variations in
v.sub.f varies the capacitance value of the varactor 56.
Accordingly, when the oscillator 20 is oscillating, an electric
field exists around the output coil 22. Viewing FIG. 1 the electric
field penetrates the door 10 within the sensing zone 15. The energy
level of the oscillator varies as the operating frequency
approaches the resonant frequency of passive reactive elements
within the sensing zone 15.
FIG. 4 is a circuit diagram of a sweep voltage source network 23
adapted to generate the constantly varying sweep voltage v.sub.f
and to vary the frequency of the oscillator within a desired range.
The sweep voltage source 23 includes a unijunction transistor 68
having one emitter tied to ground and a second emitter tied to a
first resistor 70 common to the voltage source + V. The gate of the
transistor 68 is common to an output terminal 71 which is common to
a resistor 72 extending to the voltage source + V and to a timing
capacitor 74 extending to ground reference. Referring to FIG. 2,
the output terminal 71 is common to the input of the variable
frequency oscillator 20 and to the comparator network 24 to supply
the varying sweep voltage v.sub.f. The resistor-capacitor of the
resistance 72 and capacitance 74 are such that the capacitor 74
continuously charges from + V and discharges through unijunction
transistor 68. The resistor 72 allows the timing capacitor 74 to
charge until the unijunction transistor 68 fires at a predetermined
voltage. When the unijunction transistor 68 fires the capacitor 74
discharges to the point that the unijunction transistor turns off
allowing the capacitor to recharge. The charge and discharge action
continuously repeats such that the sweep voltage v.sub.f at the
terminal 71 continuously varies and repeats according to the values
of the resistor 72 and capacitor 74.
Referring to FIG. 5, there is shown a comparator network 24 adapted
to detect a particular value of the sweep voltage v.sub.f. As shown
the reference voltage from the sweep voltage source 23 is received
at an input terminal 76. The input terminal 76 is tied to a
coupling capacitor 78 which in turn extends to a common junction 80
to a potentiometer 82. The potentiometer 82 is preset according to
the reference voltage Vref. necessary to detect the resonant
frequency of the key 13 programmed to actuate the latch 14. The
junction 80 is common to a pair of resistors 83 and 84 of which the
resistor 83 is tied to the negative terminal of an operational
amplifier 86 and the resistor 84 is common to the negative input
terminal of an operational amplifier 88. The operational amplifier
86 has an output terminal 87 tied to the anode of a diode 90
extending to the negative input terminal of the amplifier 86.
Across the negative and positive input terminals of the amplifier
86 is a diode 92 with the anode tied to the negative input terminal
and the cathode tied to ground reference and the positive input
terminal. The operational amplifier 88 has an output terminal 93
joined to the cathode of a diode 94. The anode of the diode 94 is
tied to the resistor 84 and to the negative input terminal of the
amplifier 88. Across the negative input terminal and the positive
input terminal of the amplifier 88 is a diode 96 with the cathode
tied to the negative input terminal and the anode tied to the
positive input terminal and to ground reference. The diodes 92 and
96 limit the voltage of the input of the amplifiers 96 and 88 to a
predetermined safe value. The output terminal 87 of the amplifier
86 is tied to a resistor 96 extending to the negative input of the
amplifier 88.
The sweep voltage v.sub.f as received at the terminal 76 is level
shifted by means of the coupling capacitor 78 and the potentiometer
82 so that for operational purposes the reference level at the
junction 80 is zero when the oscillator frequency of the oscillator
20 is equivalent to the resonant frequency of the programmed key
13. For illustrative purposes, a voltage-time diagram 99 is
illustrated to graphically depict the sweep voltage v.sub.f as
received at the input terminal 76 and to illustrate the shifted
reference to a trigger level V.sub.t which coincides with Vref.
Accordingly, when the voltage level at the point 80 is negative
relative to the trigger level V.sub.t, the output of the
operational amplifier 86 is positive and the diode 90 conducts.
Conduction of the diode 90 clamps the output of the amplifier 86
slightly positive. At the same time the diode 94 is reversed biased
by the negative potential at the terminal 80 and the amplifier 88
produces a full positive output at the terminal 93 as illustrated
by a pulse waveform 100 illustrated on a voltage-time diagram. When
the input sweep voltage v.sub.f exceeds the preset trigger value
V.sub.t, the voltage at the terminal 80 assumes a relative positive
value such that the output at the terminal 87 is negative and the
diode 90 is reversed biased. This insures a negative voltage at the
input of the amplifier 88 and the diode 94 is reversed biased such
that a full positive voltage of a value V.sub.1 is present at the
output terminal 93. As the value of v.sub.f crosses through the
preset trigger level V.sub.t such that the relative potential at 80
is zero, as illustrated by the time period t.sub.1 -- t.sub.2, the
voltage at the output terminal 93 of the amplifier 88 is also zero
as illustrated by the value V.sub.O of the pulse diagram 100.
Accordingly, when the sweep voltage v.sub.f is at the referenced
trigger level V.sub.f, it indicates that the sweep voltage source
23 is at the value Vref. coinciding with the select resonant
frequency of a key to actuate the loc actuator 14. Accordingly the
comparator output voltage, as illustrated by the wave form 100,
when at the V.sub.O value may be designated as a binary "one" and
at all other values as a binary "zero." These logic binary signals,
as previously discussed, are applied to the input of the controller
network 26 and to the inputs of the AND gate 27 and to the inverter
44.
Referring to FIG. 6 there is shown therein a circuit diagram of the
detector network 25 adapted to detect energy level variations in
the oscillator 20 responsive to the presence of a key in the
sensing zone 15. The detector 25 of FIG. 6 has an input terminal
101 common to the anode of an input diode 102 extending in common
to the base of a NPN transistor 104. The base of the transistor 104
is tied in common to a resistance-capacitance filter comprising a
capacitor 106 extending to ground and parallel with a resistor 108.
The emitter of the transistor 104 is tied to ground reference
through a resistance 110 and through a coupling capacitor 112 to
the base of a NPN transistor 114. The base of the transistor 114 is
also tied to a resistor 116 extending to the ground reference. The
emitter of the transistor 114 is tied to ground reference and the
collector is tied in common to a junction 117. The junction 117 is
common to a resistance 118 and a capacitor 120. The capacitor 120
joins a junction 122 common to a resistor 124. The resistors 118
and 124 extend to the source + V. The junction 122 is also tied in
common to a resistance 126 extending to an output terminal 128 in
common to the anode of a diode 130. The cathode of the diode 130 is
tied to the voltage source + V. The output terminal 128 is adapted
to extend to the controller network 26 and the AND gates 27 and 38.
In operation, the energy level change in the oscillator 20 due to
the proximity of the key 13 will manifest itself as a decrease in
the envelope voltage generated by the oscillator 20. The detector
25 is adapted to respond to level changes in the envelope voltage.
The envelope voltage v.sub.d is detected by the diode 102 and
filtered to produce a sharp decrease-increase level change in the
amplitude as shown by the time diagram A in FIG. 7. The signal A
appearing at the base of the transistor 104 passes through the
emitter-follower stage of transistor 104 and is first
differentiated by the capacitor 112 and resistor 116 as shown by
the signal B in FIG. 7. The first differentiated signal B provides
a signal representative of rater of change of the signal A. The
signal B is then amplified and shaped by the common emitter
transistor 114 and appears at terminal 117 as the signal C in FIG.
7. The signal C is then further differentiated by the capacitor 120
and resistor 124 to yield a negative going spike corresponding to
the preset desired frequency along with two positive going spikes
at two frequencies dependent on the quality of resonance as
indicated by wave form D in FIG. 7. The positive going spikes of
wave form D are clamped to the positive supply + V by the resistor
124, the resistor 126 and the diode 130 such that the output at the
terminal 128 appears as signal E of FIG. 7. The desired negative
going spike portion of the signal E represents the peak of the
envelope signal A from the detector and the logic "one" level to be
applied to the AND gates 27 and 38. For illustrative purposes the
waveform 100 of FIG. 5 from the comparator 24 is reproduced in FIG.
7. It may be noted that in comparing the signal E with the signal
100 that there is time correspondence such that the AND gate 27
received a logic "one" at both input terminals and therefore
actuate the unlock control circuit 34.
It may be noted that the output of the detector 25 is a function of
the energy change of the oscillator 20 such that in the event of an
energy change, the signal E is generated. At the same time in
viewing FIG. 7 it may be noted that the comparator 24 generates a
"one" pulse only at the voltage corresponding to the desired
resonant frequency. For all other frequency values the comparator
generates a logic "zero." The output of the comparator is tied to
the inverter 44 such that for all frequencies other than the
desired frequency the inverter 44 generates a logic "one" output.
Accordingly, in the event that the oscillator 20 generates a signal
A for frequencies other than the desired frequency a pulse similar
to that of E is generated by the detector and applied to both the
AND gates 26 and 38. With the coincidence of two logic "one"
signals being applied to the AND gate 28 at a frequency other than
the desired frequency, the AND gate 38 generates a signal to
activate the alarm circuit 48 and actuate the alarm 50 while the
AND gate 27 and latch 14 are not actuated. Actuation of the alarm
50 provides a signal that an "unauthorized key" is within the
sensing zone.
FIG. 8 illustrates an embodiment of the key 13 in the form of an
exploded card having a first face 132 and a reverse side face 134.
For illustrative purposes, the diagram of FIG. 8 illustrates the
faces 132 and 134 separated whereas in actual application the faces
132 and 134 are back-to-back in secured relationship. The key 13
unit of FIG. 8 includes a pair of resonant circuits A and B each of
a resonant frequency. The first circuit A of the key 13 and
illustrated in FIG. 2, includes a capacitor 135 and an inductor 136
tied in common to form a tank circuit. The capacitor 135 may
comprise a pair of plates 137 and 138 with the plate 137 mounted on
the surface 132 and the plate 138 mounted on the surface 134
separated by the card material comprised of a dielectric material
139. The inductor 136 comprises a strip 142 on the surface 132 and
a strip 144 on the surface 134. The strips 142 and 144 are
electrically joined in common by means of a through connection 146
extending through the card. The strip 142 is tied in common to the
plate 137 and the strip 144 is tied in common to the plate 138.
Accordingly, the resonant frequency of the circuit A of the key 13
is dependent on the values of the inductance 136 and capacitance
135. The circuit B of the key 13 is similar to the circuit A and
carries the same reference numerals distinguished by a prime
designation. The resonant frequency of the circuit B may be
different from that of the circuit A. The card 13 is adapted such
that the resonant circuits consist of only passive elements and may
be designed of any of various sizes or shapes. The potentiometer 82
of the comparator is selected to relate to one of the resonant
frequencies of the programmed key 13.
Viewing the diagram of FIG. 2, it may be noted that the present
apparatus can be utilized to be actuated by cards of various
resonant frequencies. For example, in the case of a master key 13
having a different frequency than that of a regular key 13, the
network of FIG. 2 may be modified to include a second comparator 24
receiving the sweep voltage v.sub.f. The second comparator may be
preset at a voltage level relating to the master key resonant
frequency. The second comparator would extend to a third AND gate
also extending to the detector. The third AND gate output would
extend to the unlock control circuit to actuate the lock responsive
to the master key. The third AND gate output would also extend to
the alarm circuit to deactivate the alarm circuit in the event that
the third AND gate has a logic "one" responsive to the master
key.
FIG. 9 illustrates a functional block diagram of an alternative
embodiment of the present invention referred to by the general
reference character 150, to be utilized for purposes of counting or
sorting objects carrying a programmed "key." For purposes of
clarification, those elements of the embodiment 150 similar to the
previously described elements will be referred to by the same
reference numeral distinguished by a prime designation.
In the FIG. 9 application, a "key" may be in the form of the
objects to be counted or sorted or the object with a key attached
thereto. The objects carrying the keys 13.sup.1 will be
continuously processed through the sensing zone 15.sup.1. As the
key is brought into the sensing zone 15.sup.1, the energy of the
variable frequency oscillator 20.sup.1 is changed and detected by
the detector 25.sup.1. The output of the detector 25.sup.1 is fed
to a controller network 151 having an AND gate 152. In the
embodiment of FIG. 9 the variable frequency oscillator 20.sup.1
sweeps in steps through a predetermined frequency range. The
stepping is realized by a digital-to-analog converter network 153
driven by a digital counter 154 which may carry the number
corresponding to resonant frequency of the key 13.sup.1 to be
identified in the sensing zone 15.sup.1. Once the key 13.sup.1 is
identified the detector 20.sup.1 may send out signals through the
AND gate 152 to control the desired action and destiny of the
object attached to the key 13.sup.1. The counter 154 may be stepped
by means of a clock circuit 155 which extends through the input of
an AND gate 156 which, in turn, extends to the counter 154. The
connection of the clock 155 and counter 154 may be disabled by
means of the AND gate 156 through a control demand received at the
other input of the AND gate 156. In FIG. 9 gate 156 is tied in
common through a line 158 to the output of an exclusive OR logic
gate 160 and to the input of the AND gate 152. The OR gate 160 is
also tied in common to the counter 154. Accordingly, prior to a key
13.sup.1 coming within the sensing zone 15.sup.1, the counter 154
generates a signal which is applied to the OR gate 160 such that a
signal appears on the line 158. Simultaneously the clock 155
generates a signal such that the AND gate 156 generates a signal
thereby permitting the counter 154 to function. Upon a key 13.sup.1
coming within the sensing zone 15.sup.1, the detector 25.sup.1
detects the change in energy level. Accordingly, the AND gate 152
is activated thereby disabling the output of the OR gate 160 and
the signal on the line 158. Accordingly, the counter is disabled
until the key passes through the sensing zone 15.sup.1. The OR line
158 is also common to an output terminal 162 such that an actuator
mechanism (not shown) may respond to the presence of a key 13.sup.1
in the sensing zone 15.sup.1. Once the key 13.sup.1 passes through
the sensing zone 15.sup.1 the OR gate may be reset and the
apparatus 150 reactivated for detecting purposes. A more specific
example of the application of the embodiment 150 of FIG. 9 may be
for sorting inductors, capacitors or any resonant circuit of
unknown value. For example, to sort inductors, a key in the form of
a capacitor of known value may be connected to the inductor of
unknown value to form a resonant circuit. As the formed circuit
passes the sensing zone 15.sup.1 the variable frequency oscillator
20.sup.1 will identify the resonant frequency and then control a
sorting mechanism to place the inductor in a bin representing its
particular value.
* * * * *