U.S. patent number 3,714,608 [Application Number 05/157,838] was granted by the patent office on 1973-01-30 for broadband circulator having multiple resonance modes.
This patent grant is currently assigned to Bell Telephone Laboratories, Incorporated. Invention is credited to Clare Earl Barnes, Brian Owen.
United States Patent |
3,714,608 |
Barnes , et al. |
January 30, 1973 |
BROADBAND CIRCULATOR HAVING MULTIPLE RESONANCE MODES
Abstract
A junction circulator in which the usual magnetically biased
gyromagnetic post is divided into two parts of different size so
that each part is capable of supporting a resonance mode
respectively spaced from the other in frequency within the intended
broadband of the circulator to extend the range in which the mode
phase relationship required for circulation is extended. Conductive
cores may be located in one or both of the parts or the parts may
be located in separately formed conductive cavities to introduce
other mode resonances to further extend the band.
Inventors: |
Barnes; Clare Earl (Bethlehem,
PA), Owen; Brian (Wescosville, PA) |
Assignee: |
Bell Telephone Laboratories,
Incorporated (Murray Hill, Berkeley Heights, NJ)
|
Family
ID: |
22565483 |
Appl.
No.: |
05/157,838 |
Filed: |
June 29, 1971 |
Current U.S.
Class: |
333/1.1; 333/248;
333/253; 333/251 |
Current CPC
Class: |
H01P
1/39 (20130101) |
Current International
Class: |
H01P
1/32 (20060101); H01P 1/39 (20060101); H01p
001/32 (); H01p 005/12 () |
Field of
Search: |
;333/1.1 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Gensler; Paul L.
Claims
What is claimed is:
1. A circulator operating over a broadband of electromagnetic wave
energy comprising a conductively bounded structure having a
plurality of branches symmetrically extending away from a
conductively bounded region, first and second axially aligned
bodies of magnetically polarized gyromagnetic material disposed
upon the axis of symmetry of said common region, means including
said bodies for producing a first pair of spaced resonances within
said band for each of a pair of counter-rotating electric fields
induced in said common region, and means for producing a second
pair of spaced resonances within said band for an electric field
along said axis of symmetry, one of said second pair of resonances
falling at a frequency between said first pair of resonances and
the spacing between said resonances being such that said resonances
produce a broad frequency range in which the phases between said
electric fields are maintained at substantially 120.degree..
2. A circulator operating over a broadband of electromagnetic wave
energy comprising a conductively bounded structure having a
plurality of branches symmetrically extending away from a
conductively bounded region, first and second axially aligned
cylinders of magnetically polarized gyromagnetic material disposed
upon the axis of symmetry of said common region, the sum of the
axial lengths of said cylinders being such relative to the distance
between conductive boundaries measured along said axis to leave a
dielectric gap adjacent to at least one end of each of said
cylinders, said axial lengths being significantly different from
each other and so proportioned that each body is resonant for
counter-rotating modes at a respectively different frequency
falling within said broadband.
3. The circulator of claim 2 wherein said dielectric gap is located
between opposing ends of said cylinders.
4. The circulator of claim 2 wherein said conductive boundaries are
enlarged in the area of said axis of symmetry to form cavities and
wherein said cylinders are seated in said cavities.
5. The circulator of claim 2 including a thin conductive core
within at least one of said gyromagnetic cylinders having such a
length as to produce a resonance for a third mode different from
said rotating modes at a third frequency falling between the
different frequencies of said rotating modes.
6. The circulator according to claim 5 wherein the electrical
lengths of said cylinders are one-quarter wavelength of the
frequency for which they are resonant and wherein an end of each
cylinder is terminated in a conductive discontinuity.
7. The circulator according to claim 5 wherein the electrical
lengths of said cylinders are one-half wavelength of the frequency
for which they are resonant and wherein the ends of each cylinder
are terminated in a dielectric discontinuity.
8. The circulator of claim 5 including a thin conductive core
within at least one of said gyromagnetic cylinders having such a
length as to produce a resonance for a third mode different from
said rotating modes at a third frequency falling between the
different frequencies of said rotating modes, a second thin
conductive core within the other of said gyromagnetic cylinders
having such a length as to produce a resonance for said third mode
at a frequency different from said third frequency, and a
conductive body disposed on said axis and acting as a low impedance
transformer to smooth together the characteristics of said
resonances between said frequencies.
9. The circulator of claim 5 including a thin conductive core
within the other of said gyromagnetic cylinders having such a
length as to produce a resonance for said third mode at a frequency
different from said third frequency.
10. The circulator according to claim 9 wherein the spacings
between said frequencies of resonance are such as to produce a
broad range in which the reflection coefficients of said respective
modes are different by 120.degree. at substantially every frequency
within said range.
Description
BACKGROUND OF THE INVENTION
This invention relates to symmetrical coupling devices for
electromagnetic wave energy and, more particularly, to very
broadband waveguide Y-junction circulators.
The basic Y-junction circulator comprises a conductively bounded
junction of three waveguides having a magnetically biased
gyromagnetic body extending along the axis of symmetry of the
junction. Numerous variations of this basic structure, principally
having to do with the size and shape of the gyromagnetic body and
with means for matching its impedance to the remainder of the
structure, have been proposed to improve one or another of the
operating characteristics of the circulator.
It is now clearly understood that circulator action depends upon
the relationship between the responses of the junction to three
modes supported in the junction, namely, as in-phase mode and two
counter-rotating modes, the reflection coefficients of which must
be mutually displaced in phase by 120.degree.. The differences in
bandwidth of various forms of circulators depend upon the degree to
which it is possible in a particular structure to maintain this
phase relation as frequency is changed.
In the copending application of the inventor Owen hereof, Ser. No.
7,872, filed Feb. 2, 1970, now U.S. Pat. No. 3,617,946 granted Nov.
2, 1971, there is disclosed a circulator of improved performance
wherein the usual magnetically biased gyromagnetic,
cylindrically-shaped post extending along the axis of symmetry of
the junction is foreshortened to create a dielectric discontinuity
between one conductive boundary of the junction and one end of the
post. At the same time a conductive core is extended from one
conductive boundary of the junction, part of the way along the axis
of the post. In general the dielectric gap causes counter-rotating
electric fields to be induced in the gyromagnetic cylinder normal
to the magnetic bias thereby exciting dielectric waveguide modes
for which the gyromagnetic body acts as a tuned resonant structure.
The net phase shifts for these modes with the gyromagnetic material
unmagnetized are identical and are determined by the electrical
length of the cylinder. Magnetizing the cylinder, however,
increases and decreases the path lengths of the counter-rotating
modes respectively, and by adjusting the biasing field and the
length of the cylinder, these modes can be separated by 120.degree.
from each other as required for circulator action. The conductive
core, on the other hand, tunes the in-phase mode. These three modes
can thus be tuned independently in a way which results in their
reflection coefficients being displaced by 120.degree. over a band.
The width of this band depends upon the extent over which the
reflection coefficients versus frequency for the modes can be made
to run parallel to each other, i.e., have equal and constant
slopes. Since these characteristics are, however, basically
resonant characteristics, they include steep slopes in the vicinity
of the resonance and near zero slopes at frequencies removed from
the resonant frequency so the bandwidth of circulation is
finite.
Summary of the Invention
In accordance with the present invention is has been discovered
that the bandwidth of the foregoing circulator can be extended
several times the prior bandwidth by introducing multiple
resonances so spaced in the frequency spectrum from each other that
the characteristics of reflection coefficients versus frequency
merge to form a continuum of constant slope across the broadband.
More particularly, two separate ferrite cylinders are included in
the junction, each providing a different electrical path length for
each of the counter-rotating modes that is respectively resonant at
a different one of a pair of spaced frequencies. In accordance with
a further embodiment a thin conductive pin is located axially
within each cylinder, each having a different axial length to
provide double resonances for the in-phase mode. In a further
embodiment it will be shown that the transition region between the
separate characteristics can be smoothed by use of a broadly
resonant conductive platform adjacent to one conductive
boundary.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 shows the prior art junction circulator as disclosed in the
above-mentioned copending application;
FIG. 2 is a diagram of reflection coefficients versus frequency as
found for the modes in the prior art, and for comparison, those
modes as found in several embodiments according to the
invention;
FIG. 3 is a cross section taken through the junction region and
showing the modified gyromagnetic structure and tuning pin in
accordance with the invention;
FIGS. 4 through 7 are cross sections showing arrangements of
gyromagnetic bodies and tuning pins alternative to that of FIG.
3;
FIG. 8 illustrates a further improvement of the invention including
a broadly resonant transformer structure; and
FIG. 9 is a diagram of reflection coefficients versus frequency for
the embodiment of FIG. 8.
DETAILED DESCRIPTION
Referring more particularly to FIG. 1, the prior art circulator
according to the above-mentioned copending application is shown
comprising three rectangular waveguides 20, 21 and 22 intersecting
in a Y at angles 120.degree. in an H-plane junction (the plane of
the guide broad dimension) to form a conductively bounded common
region from which the waveguide branches symmetrically extend.
Extending coaxially with the axis of symmetry of the Y within the
junction is a cylinder 25 of gyromagnetic material, such as yttrium
iron garnet or ferrite. Cylinder 25 is biased along the axis of
symmetry by being permanently magnetically polarized or polarized
by the use of external magnetics as represented schematically by
the vector HDC. Cylinder 25 has a small hole 24 drilled along its
axis. The top end of cylinder 25 is contiguous to the top
conductive boundary 23 of the common region and a gap 27 filled
either by air, or by a suitable non-magnetic dielectric material
having dielectric constant close to that of air or at least
substantially different from that of cylinder 25, forms a space
between the lower end of cylinder 25 and the lower conductive
boundary of the junction. A thin conductive pin 28 is located
axially within hole 24 and is conductively connected to the top
conductive boundary. A conductive platform 26 raises the lower
conductive boundary, shortens gap 27 and acts as an impedance
matching transformer.
Operation of such a circulator is usually explained by dividing the
excitation of one port of the junction into three excitations each
involving excitation of all three ports. The three excitations
correspond to the eigenvectors for the scattering matrix for the
junction. A first excitation excites all three ports equally and in
phase while the remaining two excitations result in equal
excitations with phases that result in counter-rotating circulator
polarizations within the junction. The requirement for circulation
in terms of these excitations is that their reflection coefficients
corresponding to the eigenvalues for the scattering matrix be
displaced in phase by 120.degree..
The significance of gap 27 can be understood when it is recalled
that in an ordinary H-plane resonant junction, the electric fields
are everywhere parallel to the axis of symmetry. The region formed
by gap 27, however, has a dielectric constant and permeability
product that is different from that of the region occupied by the
gyromagnetic material of cylinder 25 so that the phase constants of
the two regions differ. This creates an electric field in the plane
of the interface between the two regions. Thus, the
counter-rotating excitations launch waves as dielectrically
supported modes in cylinder 25, travelling up cylinder 25 to be
reflected at boundary 23 and to couple back into the junction at
gap 27. Thus, the phase of the counter-rotating modes are
determined by the length of cylinder 25 and the degree of its
magnetic polarization.
In the absence of the pin 28 the ferrite cylinder 25 does not
support an in-phase mode with transverse electric fields. With pin
28, however, such a mode is supported. Being confined to the region
of the pin, its resonances are determined by the length of pin 28.
As noted above, the counter-rotating modes have only transverse
electric fields at the axis of symmetry, and, therefore, are
essentially not affected by pin 28.
The relationships can be seen from FIG. 2 which shows typical
reflection coefficients 31, 32 and 33 in phase degrees of the three
modes in the above-described prior art structure as they vary with
frequency. Thus, the counter-rotating modes as represented by
curves 31 and 32 are resonant characteristics. A moment's
reflection will indicate that the center of the linear region
designated by point 30 corresponds to that of zero phase shift at
resonance at a frequency F.sub.1, when cylinder 25 is unmagnetized.
The low frequency end corresponds to a range of +180.degree. and
the high frequency end corresponds to a resonant phase shift of
-180.degree.. Curves 31 and 32 are phase separated above and below
point 30.degree. by 60.degree. by controlling the Faraday rotation
parameters of cylinder 25, including its length, composition and
magnetization. Pin 28 is then employed to position the in-phase
mode curve as represented by curve 33, also a resonant
characteristic, so that its most linear portion falls within the
band of intended operation in a given junction with a phase
120.degree. away from the phase of the nearest rotating mode of
curve 31. Circulation is then possible over the range designated A
in which the curves generally parallel each other as indicated.
Note that this range A is bounded on the high and low frequency
ends by regions in which the phase characteristics become
non-linear as they follow the typical pattern of phase shift in a
resonant circuit. In these high and low regions the phase spacing
between the characteristics as required for circulation no longer
exists and is responsible for the band limiting effects in the
prior art structures.
With this background in mind, the principles of the present
invention may be understood from FIG. 3. In all cases in which the
structures, materials or principles of operation are the same as
those described above, the detailed description thereof need not be
repeated.
Referring then to FIG. 3, a waveguide junction is shown only in a
cross section taken through the junction region but corresponding
in every way to the kind of junction formed by guides 20, 21 and 22
of FIG. 1 and for which the top and bottom conductive boundaries
are designated 40 and 41, respectively. Gyromagnetic cylinders 42
and 43 are included on the axis of symmetry of the junction with an
end of each adjacent respectively to the top and bottom conductive
boundaries 40 and 41. In the embodiment illustrated both cylinders
42 and 43 have equal diameters. In accordance with the invention,
however, cylinder 42 has an axial length l.sub.1 equal
.lambda..sub.1 /4, where .lambda..sub.1 is the electrical
wavelength at the frequency F.sub.1 mentioned in connection with
FIG. 2 and cylinder 43 has an axial length l.sub.2 equal
.lambda..sub.2 /4, where .lambda..sub.2 is the electrical
wavelength at the frequency F.sub.2, shown on FIG. 2 above F.sub.1.
Since the cylinders act as quarter wave shorted stubs for the
counter-rotating modes, they are resonant, respectively, at the
frequencies F.sub.1 and F.sub.2.
A conductive pin 44, similar to the one described in connection
with FIG. 1, is included in an axial hole within cylinder 42 to
tune the in-phase mode in the manner of the prior art to a
dielectric mode resonance in body 42. Considering cylinder 42 and
pin 44 as a coaxial shorted stub it will be convenient to think of
this resonance as one which occurs when the electrical length of
pin 44 is one-quarter wavelength at the in-phase mode frequency. In
accordance with the present invention this resonance should occur
at a frequency such as F.sub.3 on FIG. 2 which lies between F.sub.1
and F.sub.2. Thus, the previously described characteristic 33 is
descriptive of the reflection coefficient produced by the in-phase
resonator including pin 44. While the in-phase mode resonance will
be treated hereinafter in terms of the conductive pin, it should be
kept in mind that the in-phase mode may be tuned without a
conductive pin by proper control of the diameter of cylinders 42 or
43, exclusively, or by any resonant structure which couples
primarily or differentially the in-phase mode in the band of
interest. An example of this principle will be specifically
illustrated in connection with FIG. 7 hereinafter.
Assuming then that the previously described characteristics 31 and
32 are also descriptive of body 42, reflection coefficients of body
43 may be defined by characteristics 34 and 35 of FIG. 2. The
frequency F.sub.2 must be located so that the +180.degree. phase
shift point of curves 34 and 35 overlaps, that is, occurs at a
lower frequency, than the -180.degree. phase shift portion of
curves 31 and 32. In addition, frequency F.sub.2 must be
sufficiently far from F.sub.1 that the two resonances do not "pull"
each other and degenerate into a single resonant mode. When these
criteria are met, the reflection coefficients sum to form a
continuum between linear portions of the respective characteristics
as represented by the dotted characteristics 36 and 37. Circulator
action is, therefore, achieved over the range designated B
extending over the full linear portion of curve 33.
While cylinders 42 and 43 are illustrated as having equal diameters
and different physical lengths, it should be noted that their
electrical length is the operative parameter and may be effected by
changing diameters and/or the dielectric constants of the materials
from which they are formed either with or without different
physical lengths. It has been found that the presence or absence of
the pin-containing holes does not appreciably affect their
electrical lengths.
In FIG. 4 the region of circulation is further extended by
introducing a second conductive pin 53 into the second cylinder 54
which provides a second resonance for the in-phase mode forming a
continuum with the resonance of the first pin 44 in cylinder 52.
Note that cylinder 54 is short and fat and cylinder 52 is long and
thin. In both cases it will be assumed that these dimensions are
proportioned to produce resonances more or less like those
described in FIG. 3.
Conductive pins 53 and 44 are both similar to pin 44 of FIG. 3. Pin
44 has a length that is a quarter wavelength for the in-phase mode
at a frequency F.sub.3. Additionally pin 53 has a length that is a
quarter wavelength for this mode at a higher frequency F.sub.4 to
produce a new resonance as shown by the broken line characteristic
39 on FIG. 2. As shown on FIG. 2, the frequency F.sub.3 will in
general fall between F.sub.1 and F.sub.2 and the frequency F.sub.4
will fall above the frequency F.sub.2. Furthermore, the frequency
F.sub.3 and F.sub.4 are so spaced from each other that their
respective resonance characteristics 33 and 39 merge as shown by
the dotted characteristic 38. Circulator action is now obtained
over the band C extending from the low frequency end of the linear
portion of characteristic 33 to the high frequency end of the
linear portion of characteristic 35. Since the mode involved in the
pin resonance is the lowest order mode for a dielectric waveguide
with a central conductor, the pin length required for the resonance
for the in-phase mode is generally less than the ferrite length
required for the resonances in the rotating modes. Thus, the pins
normally do not project from the ferrite bodies.
FIG. 5 illustrates an alternative embodiment of the invention in
which the relative positions of the components are, in effect,
reversed. Specifically, a pair of gyromagnetic cylinders 55 and 56
having different lengths and being separated by a thin conductive
septum 57, are suspended between conductive boundaries 40 and 41 by
spacers of low dielectric constant material 58 and 59. Conductive
pins 60 and 61 are included within cylinders 55 and 56, both pins
extending from conductive septum 57. The dimensions of cylinders 55
and 56 and of pins 60 and 61 are chosen as described above. Thus,
the counter-rotating modes are generated at the gaps produced by
dielectric spacers 58 and 59, propagate in opposite directions to
be respectively reflected by septum 57 interposed at different
distances from the dielectric gaps to produce the round trip phases
as described above. Pins 60 and 61 act as separate quarter
wavelength shorted studs for the in-phase mode having lengths
similarly measured from the terminating septum 57.
In each of the foregoing embodiments the resonant structure for
either the in-phase mode or for the counter-rotating modes took the
form of a quarter wavelength shorted stub at the appropriate wave
frequency. It is possible, however, to obtain these resonances with
an equivalent half wavelength open stub and such may be an
advantage in a particular embodiment at extremely high frequencies
where fractional wavelengths become increasingly small. FIG. 6
shows one such illustrative embodiment. Thus, gyromagnetic
cylinders 71 and 72 are supported and separated by low dielectric
constant spacers 73 and 75 between conductive boundaries 40 and 41
and by spacer 74 between the cylinders. Cylinders 71 and 72 are
resonant for the rotating mode at the required frequency when they
are one-half wavelength long. Similarly, pins 76 and 77, included
within the bodies, are resonant for the in-phase mode when they are
one-half wavelength long.
At frequencies in the millimeter wave range even a one-half
wavelength pin causes problems because of its small dimension, the
necessity of the hole in the gyromagnetic cylinder, and the
difficulty of making good electrical contacts with the conductive
waveguide housing or septum.
FIG. 7, therefore, illustrates one further alternative for tuning
the in-phase mode. Conductive boundaries 80 and 81 are provided
with conductive enlargements forming cylindrical cavities 82 and 83
extending concentrically with the axis of symmetry of the junction.
The gyromagnetic bodies 84 and 85 are seated in cavities 82 and 83
and typically, but not necessarily, fill said cavities. The cavity
diameters must be large enough to permit transmission of the lowest
order TM mode when the cavities are treated as sections of
gyromagnetically loaded circular waveguide. In this embodiment, all
three modes couple to resonances determined by the axial dimensions
of the junction. The resonances for the in-phase mode are
determined by the lengths of the cavities 82 and 83, since the RF
field modes involved cannot be supported in the unshielded portions
of the gyromagnetic bodies. However, the rotating modes couple to
RF field modes on the unshielded portion of the gyromagnetic bodies
and these modes blend smoothly into RF field modes in the shielded
cavity portion. Thus, for example, the in-phase mode sees
resonances when the cavities 82 an 83 are one-quarter wavelength
long while the rotating modes see resonances when the gyromagnetic
bodies 84 and 85 are three-quarter wavelength long. The dimensions
of the cavities and gyromagnetic bodies are proportioned to produce
the separate spaced resonances as described hereinbefore. The
dimensions of the resonators and the gyromagnetic bodies are then
proportioned to produce the separate, spaced resonances as
described hereinbefore.
In accordance with a further feature of the invention, the separate
frequencies of resonance may be more widely spaced from each other
to further increase the band of circulation by the use of one
additional resonant circuit common to each of the previously
described resonances. Referring to FIG. 8, the junction region
includes a large diameter, conductive disk or platform 91 adjacent
conductive boundary 40. Adjacent to disk 91 is a first cylinder of
gyromagnetic material 92 including a conductive pin 93 connected to
disk 91. A second cylinder of gyromagnetic material 94 is located
adjacent conductive boundary 41 and includes a second conductive
pin 95. In general, the function of conductive disk 91 is to
produce a low Q resonance that merges with and smoothes out the
separate relatively high Q resonances of gyromagnetic cylinders 92
and 94, and of conductive pins 93 and 95. The nature of this
smoothing and the proportions of all components required therefor
may most easily be explained by reference to the reflection
coefficient versus frequency characteristics of each of the
components.
Referring to FIG. 9, it may be assumed, therefore, that the
resonances in the low frequency portions of curves 101 and 102
centered about F.sub.1 represent the counter-rotating resonant
characteristics for cylinder 94 while the high frequency portions
of curves 101 and 102 represent the corresponding resonances
centered about F.sub.2 represent the counter-rotating resonant
characteristics for cylinder 92. The low and high frequency
resonances in curve 103 at F.sub.3 and F.sub.4, respectively, may
be assumed to represent the resonances associated with pins 95 and
93. In accordance with the invention, the separations between
F.sub.1 and F.sub.2 and between F.sub.3 and F.sub.4 are
substantially equal and significantly greater than the
corresponding separations described with reference to FIG. 2. More
particularly, they are spaced so that there is little if any
overlap between the two resonances in any one of the curves 101,
102, or 103, and each resonance retains its characteristic S shape
spanning the reflection coefficient phase range of 360.degree.. A
typical spacing between F.sub.1 and F.sub.2 and between F.sub.3 and
F.sub.4 is in the order of 20 percent of the midband operating
frequency F.sub.5. Disk 91 is proportioned to provide a resonant
transformer between the gyromagnetic cylinders and the connecting
waveguides. The resonant frequency of the transformer is typically
at or near the center operating frequency F.sub.5. The disk, 91,
typically, but not necessarily, has dimensions of one-quarter
wavelength at F.sub.5 as measured from the outer edge of the
gyromagnetic cylinder 92 to the outer edge of the disk. The broken
curves 104, 105 and 106, included here for illustrative purposes,
have been generated from curves 101, 102 and 103 by a simple
impedance transformation through such a quarter wave transformer.
This transformation may be made using the well-known transmission
line equations for input impedance or it may be carried out
graphically on a Smith Chart. The procedure is to convert the
reflection coefficients of FIG. 9 to impedances, transform the
impedances through the quarter wave line, and reconvert the
impedances to reflection coefficients. The residual ripple on
curves 104, 105 and 106 is determined by both the shape of the
curves 101, 102 and 103 and the impedance and length of the
transformer. When the transformer impedance and length is optimized
for minimum ripple, the phase separation between the transformed
reflection coefficients is substantially 120.degree. from F.sub.6
to F.sub.4 or over the band D of FIG. 9.
In all cases in which quarter wavelength sections are specified it
is understood that any odd number of quarter wavelengths is
obviously intended. Likewise when half wavelength sections are
specified, it is understood that any even multiple of quarter
wavelengths is intended.
* * * * *