U.S. patent number 3,703,689 [Application Number 05/119,178] was granted by the patent office on 1972-11-21 for microwave varactor-tuned resonator for preselector.
This patent grant is currently assigned to Microdyne Corporation. Invention is credited to Jon R. McAtee.
United States Patent |
3,703,689 |
McAtee |
November 21, 1972 |
MICROWAVE VARACTOR-TUNED RESONATOR FOR PRESELECTOR
Abstract
A tunable varactor resonator has a high-Q cavity and a
concentric inner probe, with one end of the concentric probe
connected electrically to an eccentric probe of higher
characteristic impedance in series with a varactor. Minimum
insertion loss, approximately constant unloaded Q, and usability of
low-Q varactor diodes are features.
Inventors: |
McAtee; Jon R. (Rockville,
MD) |
Assignee: |
Microdyne Corporation
(N/A)
|
Family
ID: |
22382956 |
Appl.
No.: |
05/119,178 |
Filed: |
February 26, 1971 |
Current U.S.
Class: |
333/223; 333/207;
334/45 |
Current CPC
Class: |
H01P
7/06 (20130101) |
Current International
Class: |
H01P
7/00 (20060101); H01P 7/06 (20060101); H01p
007/04 () |
Field of
Search: |
;333/83R,82R,82B,73R,73W,76 ;334/45,15 |
References Cited
[Referenced By]
U.S. Patent Documents
Foreign Patent Documents
Primary Examiner: Gensler; Paul L.
Claims
What is claimed is:
1. An electronically tuned resonator comprising a microwave
resonator cavity element, a conductive probe concentrically
positioned in said cavity element and forming therewith a high-Q
shorted line resonating at somewhat higher frequency than that
desired for operation, a conductive element eccentrically
positioned in said cavity element and connected at one end to a
point on said probe at an elevated RF potential, and a varactor
diode in said cavity in series between the other end of said
conductive element and a point on said probe of low RF potential;
said conductive element forming with said cavity element a second
shorted line resonating at a somewhat lower frequency than that
desired for operation, and having a relatively lower Q, and a
source of adjustable bias voltage connected to the varactor diode
for adjusting the effective frequency of said resonator.
Description
BACKGROUND OF THE INVENTION
In the design of highly selective ultra-high-frequency radio
receivers, it is common practice to subject incoming signals to a
succession of mixing or heterodyning operations, but it is known
also that it is advantageous to provide a non-amplifying
preselector between the antenna and the first mixer stage, or any
straight radio-frequency amplifier. Interfering or spurious inputs
are thus reduced or eliminated with little attenuation of the
incoming power, and the sought-for signal can be amplified to
higher levels then when it is relatively impure. In addition, the
preselector minimizes the radiation of receiver-generated
signals.
For use at ultra-high-frequencies, it is necessary for the
preselector (which is essentially a highly selective filter, or
more usually, a series of filter sections) to present the high Q
characteristic of all sharply tuned devices. Some provision must
also be made for tuning adjustments to permit a reasonable range of
frequencies to be covered. In prior art preselectors, this
adjustment has usually been accomplished by mechanical adjustment
of transmission line length associated with the other components of
the filter. The moving parts of this type of cavity lead to the
possibility of mechanical wear, resulting noise and failure to
track accurately, and other defects, such as bulk and the shape
factors which are inimical to reasonable values of the circuit
Q's.
While it might appear obvious that some of these disadvantages
could be overcome by using the variable-capacity property of
varactors, the fact is that for use at microwave frequencies, the
inherent Q's are then altogether too low to permit the selectivity
desired. The present invention provides an arrangement in which a
readily available low-Q varactor diode component is combined with
high-Q components in a resonant cavity so that an adequate control
of the resonance (selective) frequency is achieved, while the
effect of the diode on degrading the overall Q is minimized.
SUMMARY OF THE INVENTION
Basically, the end object of the invention is to provide electronic
tuning of a microwave resonator having a relatively low insertion
loss or attenuation, such as not over 1 db, with a loaded Q in
excess of 100, which is relatively uniform over the band. The
signal frequency may be, for example, as high as 4 GHz or higher.
Two circuits are involved; one of these is the widely known
quarter-wave TEM cavity, the other, which is inductively coupled to
the same cavity, consists of a length of transmission line that is
loaded with the variable capacitance diode, or varactor. This
transmission line, with the diode at maximum reverse bias (minimum
capacitance), is self-resonant below the operating frequency of the
cavity; therefore, minimum capacitance in this circuit will be
reflected to the cavity as a minimum value of inductance and will
therefore represent the condition of maximum frequency. At minimum
reverse bias (maximum capacity) the inductive component reflected
to the cavity is maximum, and will correspond to the condition of
minimum frequency.
The total inductive reactance thus coupled to the cavity is very
high compared to the inductive component of the TEM cavity;
therefore the Q of the coupled reactance represents a relatively
small degradation in the total Q of the resonator.
Stated differently, at minimum capacitance the effect on the cavity
will be maximum because the inductive component reflected is
minimum. However, at minimum capacitance the Q of the diode is at
its highest. At the condition of maximum capacity the inductive
component is maximum and has a minimum effect on the cavity. It can
therefore be seen that due to the offsetting effects, the unloaded
Q of the cavity may be kept essentially constant across the
frequency band of interest. In still other words, the point of
minimum Q of the diode occurs at the point of minimum loading of
the cavity. The point of maximum Q of the diode occurs at the point
of maximum loading of the cavity.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a schematic diagram of one stage of a pre-selector (less
input and output coupling) denoting the basic resonator
arrangement.
FIG. 2 is a similar diagram of a four-stage pre-selector showing
iris coupling between stages and one form of input and output
coupling to and from the first and last stages.
FIG. 3 is a vertical sectional view of a varactor-tuned
pre-selector stage incorporating the present invention, and
suitable for microwave frequencies.
DETAILED DESCRIPTION
GENERAL
Lp and Cp of FIG. 1 illustrates the equivalent circuit of a
conventional resonator design as employed in the art, and described
in texts, such as "Microwave Filters, Impedance Matching Networks
and Coupling Structures" by Matthaei et al. McGraw-Hill (1964). For
tuning to a precise frequency in the microwave region, a varactor
(voltage-variable capacitor) Cj can be connected in series with
inductance Ld, and varied by adjusting the value of reverse-bias
voltage applied to its control lead. However, such a device would
be very inefficient, due to the very large attenuation (insertion
loss) in each stage of the preselector, in turn due to the
inherently low Q of the diode Cj.
The problem encountered at microwave frequencies is utilizing
readily available low Q variable capacitance diodes in such a way
as not to degrade the Q of the resonator below the point of being
usable in a microwave filter. The pre-selector in its simplest form
consists of: (1) a quarter-wave resonator that is tuned to the
desired operating frequency, (fo); (2) the varactor diode (Cj) with
its associated line, resonant at a lower frequency f1. The
frequency of the preselector is determined by: (1) the length of
the concentric center conductor, (LpCp), and (2) the resonant
frequency of the eccentric line (LdCd) and the diode capacitance
(Cj). The tuning range and the unloaded Q of the cavity are
dependent upon the ratio of the two resonant frequencies. The
greater the ratio of the frequencies the smaller the tuning range.
The smaller the tuning range the higher the unloaded Q. Basically,
the technique employed at microwave frequencies is to tune a high Q
resonant cavity (LpCp) with a lightly coupled low Q circuit, (LdCd)
containing the variable capacitance diode (Cj). The low Q resonant
circuit, by itself, is self-resonant below the operating frequency
of the cavity so that at the cavity frequency it appears as an
inductive reactance. Electronic tuning of the device is
accomplished by changing the resonant frequency of LdCd, which in
turn changes the resonant frequency of LpCp. The end object of this
device is to provide electronic tuning of a microwave resonator
having a relatively low insertion loss, 1 db or less, with loaded
Q's in excess of 100.
Basically, the resonator consists of two circuits. One circuit is
the widely known quarter-wave TEM mode cavity. The other circuit,
which is inductively coupled to the TEM cavity, consists of a
length of transmission line that is loaded with a variable
capacitance diode. The transmission line, with the diode at maximum
reverse bias (minimum capacitance), is self-resonant below the
operating frequency of the cavity; therefore, minimum capacitance
in this circuit will be reflected to the cavity as a minimum
inductance and will therefore represent the condition of f-maximum.
At minimum bias (maximum capacity) the inductive component
reflected to the cavity is maximum and will represent the condition
of f-minimum.
The total inductive reactance coupled to the cavity is very high
compared to the inductive component of the TEM cavity; therefore
the Q of the coupled reactance represents a relatively small
degradation in the total Q of the resonator.
At minimum capacitance the effect on the cavity will be maximum
because the inductive component reflected is minimum. However, at
minimum capacitance the Q of the diode is highest. At the condition
of maximum capacity the inductive component is maximum and has a
minimum effect on the cavity. It can therefore be seen that due to
the offsetting effects, the unloaded Q of the cavity is relatively
constant across the band of interest. In other words, the point of
minimum Q of the diode occurs at the point of minimum loading of
the cavity. The point of maximum Q of the diode occurs at the point
of maximum loading of the cavity.
FIG. 2 illustrates in diagram form a four-stage resonator with
input coupling loop 10, for example, feeding the incoming signal to
the first-stage can 12, and after filtering exiting at 14 by
capacitor coupling to the second stage can 16, thence by similar
coupling to the third stage can 20, and similarly at 18 into the
fourth stage can 22. The respective tuning varactors are controlled
over a common reverse-bias line 24 from outside the body of the
pre-selector, with provision for individual trimming of these
biases for alignment purposes. The output signal from the fourth
stage 22 is taken by means of coupling loop 25.
DETAILS OF THE RESONATOR OF THE INVENTION
The construction of the individual stages, as physically embodied,
is typically shown by FIG. 3, illustrating the details of first
stage 12. The "can" referred to above constitutes the outer
conductor of the quarter-wave cavity, and is a metal cylinder 26
which is closed at the top, and at the bottom by the mounting plate
28. Into this plate the metal stub 30 is secured, as by a threaded
nut 32. Since the effective length of the central conductor within
the cavity 26 tunes the cavity, provision is made for closely
adjusting its length by an external screwdriver-like blade (not
shown) inserted in the slot 35 whereby to rotate the metal probe 34
and make more or less of it project above the top of the stub.
Spring fingers 36 of beryllium copper or the like have a good
running fit over the body of the probe 34, and are soldered to the
end of the stub 30.
The stub-probe combination is the centered element within the can
of the concentric line, where mounting plate 28 performs the
"shorting" function. The length of the line is adjusted to be
greater than one-fourth wavelength at the operating frequency, for
reasons explained above. Actually, it is the inside surface 38 of
can 26 which functions as the outer conductor of the concentric
line. The ratio of the inside diameter of the cavity 26 (at 38) to
the outer diameter of the center conductor is chosen for optimum
(high) Q.
Within the annular space surrounding the probe 34 is mounted the
second major component of the resonator, a length of transmission
line 40 extending parallel to the axis of the cavity 26. Such lines
have much higher characteristic impedance than do concentric lines
such as just described, yet by positioning it in this way, i.e.,
the fact that it is within the cavity, its effect as a mere lossy
(low-Q) body on the cavity itself is minimized. The length of this
line is made such that, with the added capacitance of the varactor
diode, the resonance is below the operating frequency of the
resonator, and the distance of its upper end from the stub 30 is
fixed by the length of a small metal tab 42 soldered to the top of
stub 34 and electrically and mechanically connected to a metal cap
on socket 44. This distance controls the amount of coupling between
the cavity and the line 40. At the lower end, the "eccentric" line
is held mechanically by mounting the varactor diode 46 between two
caps in the usual way, the upper metal cap 48 for the anode being
soldered to the lower end of line 40 and the lower cap 50 being
mounted on a feed-through element 52 of known type which passes the
control conductor 24 from the varactor cathode through the mounting
plate 28 to the inverse bias source. The feed-through also secures
the lower end of line 40 in position, and provides an r-f ground at
the cathode of the varactor.
* * * * *