U.S. patent number 3,681,654 [Application Number 05/116,436] was granted by the patent office on 1972-08-01 for light-regulating power supply circuit for gaseous discharge lamp.
This patent grant is currently assigned to Wagner Electric Corporation. Invention is credited to Halsey P. Quinn.
United States Patent |
3,681,654 |
Quinn |
August 1, 1972 |
LIGHT-REGULATING POWER SUPPLY CIRCUIT FOR GASEOUS DISCHARGE
LAMP
Abstract
A power supply circuit operative to supply sinusoidal
high-frequency (28 kilohertz) electrical power which meets both the
starting and running requirements of a gaseous discharge lamp, and
further operative to regulate the light output of the lamp, all
without mechanical switching means or saturable reactors.
Inventors: |
Quinn; Halsey P. (Morris
Plains, NJ) |
Assignee: |
Wagner Electric Corporation
(N/A)
|
Family
ID: |
22367200 |
Appl.
No.: |
05/116,436 |
Filed: |
February 18, 1971 |
Current U.S.
Class: |
315/151;
315/DIG.4; 250/205; 315/158 |
Current CPC
Class: |
H05B
41/3922 (20130101); Y10S 315/04 (20130101) |
Current International
Class: |
H05B
41/392 (20060101); H05B 41/39 (20060101); H05b
041/36 () |
Field of
Search: |
;250/205
;315/DIG.4,DIG.5,DIG.7,149,151,158,159,246,291 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Heyman; John S.
Assistant Examiner: Woodbridge; R. C.
Claims
1. A voltage and current regulated power supply circuit for a
variable-impedance, light-generating load comprising:
1. first circuit means operative to convert alternating current
power to direct current power which is applied to the remainder of
said power supply circuit;
2. second circuit means operative in response to a variable bias
signal to generate high-frequency pulses of variable width and
substantially constant amplitude;
3. third circuit means which, when coupled to the
variable-impedance load, is operative in response to the output of
said second circuit means to generate high-frequency, high voltage
output power when the load impedance is high, and to generate
high-frequency, low voltage output power when the load impedance is
low; and
4. fourth circuit means operative to compare the light output of
the load with the light output of a reference source and to provide
a variable bias signal to said second circuit means to vary the
width of the output pulses of said second circuit means in response
to variations from a
2. The power supply circuit according to claim 1 wherein said first
circuit means comprises:
1. a diode bridge circuit having first and second input and output
terminals;
2. first and second inductances each having first and second
terminals, said first terminal of said first inductance being
connected to said first output terminal of said bridge circuit, and
said first terminal of said second inductance being connected to
said second output terminal of said diode bridge circuit; and
3. a filtering capacitance connected between said second terminals
of said
3. The power supply circuit according to claim 2 wherein said first
and
4. The power supply circuit according to claim 1 wherein said
second circuit means comprises:
1. high frequency oscillator means operative to generate
high-frequency rectangular pulses;
2. saw-tooth pulse generating means synchronized with said
high-frequency oscillator means;
3. first amplification circuit means connected to said saw-tooth
pulse generating circuit and operative to amplify the output of
said saw-tooth pulse generating means and said variable bias
signal;
4. threshold circuit means having a first input terminal connected
to the output of said first amplification circuit means and a
second input terminal connected to the output of said
high-frequency oscillator means, and operative to generate output
pulses of constant amplitude and of variable width corresponding to
the period of time during which both of said input pulses exceed
its threshold; and
5. second amplification circuit means operative to generate output
pulses of predetermined polarity, constant amplitude, and variable
width corresponding to the width of the output pulses of said
threshold circuit
5. The power supply circuit according to claim 4 wherein said
threshold
6. The power supply circuit according to claim 4 wherein said
second
7. The power supply circuit according to claim 6 wherein said
saw-tooth pulse generating circuit comprises:
1. a capacitance and a charging resistance connected in series
therewith to said voltage regulation means; and
2. a diode and a discharging resistance connected in series between
the junction of said capacitance and said charging resistance and
the output
8. The power supply circuit according to claim 7 wherein said
high-frequency oscillator means is operative to close a discharge
current path for said saw-tooth pulse generating means through said
second transistor switch in the periods between adjacent
high-frequency
9. The power supply circuit according to claim 1 wherein said third
circuit means comprises:
1. a transformer having primary and secondary windings, said
primary winding being connected in series between said first and
second circuit means;
2. an autotransformer having first, second and third terminals;
3. a power transistor having its base and emitter connected across
said secondary winding of said transformer, and having its
collector connected through said second and first terminals of said
autotransformer to said first circuit means; and
4. resonant circuit means connected between said first and third
terminals of said autotransformer and operative to generate a high
voltage by resonating at a first high frequency in response to
input power pulses from said auto-transformer when said load
impedance is high, and by resonating at a second high frequency in
response to input power pulses
10. The power supply circuit according to claim 1 wherein said
fourth circuit means comprises:
1. light pipe means operative to sample the light output of the
load and to channel the sample as a first input to
2. feedback signal generating means including a phototransistor and
operative to generate a variable component of said variable bias
signal; and
3. bias circuit means coupled to said feedback signal generating
means and operative to provide said variable bias signal to said
second circuit
11. The power supply circuit according to claim 10 wherein said
feedback signal generating means comprises:
1. integrating circuit means and inverter means operative in
combination to shorten and delay in phase input pulses of constant
frequency, amplitude, and width derived from said second circuit
means;
2. a light-emitting diode energized by the output of said inverter
means and operative to provide a second input to said
phototransistor;
3. synchronous detector means operative in response to said pulses
of constant frequency, amplitude, and width, said output pulses of
said inverter means, and the output of said phototransistor to
generate a reference signal and a variable signal which varies
directly with the light output of the load;
4. first and second peak-to-peak detector means including a common
capacitance and operative to vary the charge on said common
capacitance as said variable signal from said synchronous detector
means varies; and
5. transistor means having its input terminals connected across
said common capacitance and having its output terminal connected to
said bias circuit
12. The power supply circuit according to claim 11 wherein said
synchronous detector means comprises:
1. a voltage dividing network;
2. first and second normally non-conductive transistors, said first
transistor having a differentiating input circuit connected to the
output of said inverter means and said second transistor having a
differentiating input circuit connected to said source of pulses of
constant frequency, amplitude and width; and
3. a variably-conductive transistor connected into the output
current paths of said normally non-conductive transistors, and
controlled by the output of said phototransistor.
Description
BRIEF SUMMARY OF THE INVENTION
The present invention relates to a power supply circuit operative
to generate sinusoidal high-frequency voltage and current outputs
for a variable-impedance, light-generating load having widely
variable voltage and current requirements, e.g., a gaseous
discharge lamp. Such a load presents a unique problem because it
initially requires a very high starting voltage and then, after the
gaseous discharge has been initiated by the flow of current through
the lamp, high lamp current at a low voltage is required. Earlier
supply circuits have used a high-voltage starting circuit which,
when the lamp passes current, is switched off by a relay which
simultaneously connects the lamp to a low-voltage constant current
supply circuit. Saturable reactors have also commonly been employed
in such prior art circuits.
More recently developed circuits have sought to achieve a regulated
light output from the lamp load by regulating the voltage and
current supplied to that load. See, for example, copending
application Ser. No. 102,610 entitled Voltage and Current Regulated
Power Supply Circuit for Gaseous Discharge Lamp and filed on Dec.
30, 1970 by Halsey P. Quinn, the present applicant. Such circuits
do not compensate for such factors as aging of the lamp, blackening
of the lamp envelope, or variations in light output due to ambient
temperature changes.
The present invention is embodied in a single power supply circuit
which does not utilize mechanical switching means or saturable
reactors, and which compensates for the condition of the lamp load.
This power supply circuit has two modes of operation, one for
starting and one for running the lamp. The output voltage is very
high when the supply circuit is in the starting mode, and the
output current is supplied at a relatively low voltage when the
supply circuit is in the running mode. A resonant circuit builds up
a controlled high voltage only during the starting mode. To
regulate the light output of the lamp load at the lower voltage
developed in the running mode, high-frequency current pulses of
constant amplitude and variable width are supplied to the input of
a power circuit. The width of the pulses is controlled by a
variable bias voltage generated by a feedback circuit which provide
a bias voltage component proportional to the light output of the
lamp load. The variable bias voltage is combined with a series of
saw-tooth pulses, both are amplified and then fed to a NAND gate as
a first input, the second input being provided by the
high-frequency rectangular pulse output of an oscillator. The
saw-tooth pulses are generated in synchronization with the
oscillator's rectangular pulses by charging a capacitor through a
first current path during one time interval corresponding to the
duration of a rectangular pulse, and discharging that capacitor
through the oscillator during a second time interval corresponding
to the interpulse null of the oscillator.
BRIEF DESCRIPTION OF THE DRAWINGS
A better understanding of the present invention may be had by
reference to the accompanying drawings, of which:
FIG. 1 is a schematic diagram of the circuit which is the preferred
embodiment of the present invention; and
FIG. 2 is a series of graphs showing a number of pertinent wave
forms appearing at specific points in the circuit during operation,
all of said graphs having a common time base.
DETAILED DESCRIPTION OF THE INVENTION
Referring now specifically to FIG. 1, the circuit shown therein is
operable with a standard alternating current power source (117
volts RMS, 60 hertz) connected between input terminals 002 and 004.
A switch 006 connected to the high input terminal 002 enables
control of the application of power to transformer 100, which
energizes the filaments of lamp 200, and to the AC/DC conversion
circuit 300, the output of which is fed to high-frequency
oscillator 400 via switch 008 and resistance 010, to variable-width
pulse generator 500, and to power circuit 600. The high-frequency
sinusoidal output voltage and current developed by resonant circuit
700 are applied between the filaments of lamp 200, the output of
which is sampled by light pipe 800. The light sample is fed to a
photosensitive transistor in the feedback signal generating circuit
900, the variable output of which is fed to bias circuit 1,000. The
output of the bias circuit 1,000 is fed to the variable-width pulse
generator 500 to cause variations in the width of the
high-frequency, constant-amplitude pulses which comprise the input
to power circuit 600.
The AC/DC conversion circuit 300 includes a diode bridge full-wave
rectifier circuit comprising diodes 302, 304, 306 and 308, a pair
of choke coils 310 and 312 which are preferably inductively coupled
by a common core 314 to act as a low-pass filter, and a capacitor
316 to eliminate substantially all of the AC ripple in the DC
output. An output voltage of approximately 120 volts DC is
generated across capacitor 316 and is applied through switch 008
and resistance 010 to high-frequency oscillator 400, which is
operative to generate rectangular output pulses as shown in FIG.
2(a). This oscillator 400 may comprise any circuit operative to
provide the aforementioned output, but is preferably of the type
shown in copending application Ser. No. 102,610 referred to
earlier.
The DC power output of AC/DC conversion circuit 300 is applied to
the variable-width pulse generator 500 through the current-limiting
resistance 516, which is effectively in series with zener diode 524
between the output terminals of the AC/DC conversion circuit 300.
Thus, a constant DC voltage of approximately 5 volts DC is applied
to the variable-width pulse generator 500, which comprises a
charging circuit formed by resistance 502 and capacitance 520,
their junction being connected via resistance 504 to the base of
transistor 526. A discharge circuit for capacitance 520 is formed
by diode 522 and resistance 506 connected in series between the
aforementioned junction and the output terminal of high-frequency
oscillator 400. During each of the positive high-frequency
rectangular pulses which comprise the output of oscillator 400, the
discharge path is effectively blocked because the cathode of diode
522 is placed at a positive potential. Thus, during each pulse,
charging current flows through resistances 516 and 502 to
capacitance 520. Between pulses, capacitance 520 discharges through
diode 522, resistance 506, and the high-frequency oscillator 400.
In this manner, saw-tooth pulses having the same frequency as the
output of oscillator 400 appear at the junction of resistance 502
and capacitance 520, and are applied through resistance 504 to the
base of transistor 526. These saw-tooth pulses, along with the
variable negative DC bias derived from the bias circuit 1000 and
applied to the base of transistor 526, are amplified by the
two-stage DC amplifier formed by transistor 526, resistance 508,
transistor 528 and resistance 512. The combined and amplified
saw-tooth pulses and variable DC bias comprise one input to the
NAND gate 532, and the positive high-frequency rectangular output
pulses of oscillator 400 comprise the second input to the NAND gate
532. Only when both of these positive input signals are above the
threshold voltage of NAND gate 532 is a negative output signal
generated. Since the period of time during which the first input
signal is above that threshold varies according to the variable DC
component of the first input signal, the output pulses of NAND gate
532 will vary accordingly. The variable-width, constant-amplitude
negative pulses which form the output of NAND gate 532 are fed via
capacitance 518 to the base of normally-conductive amplifier
transistor 530, which is resultantly pulsed non-conductive to
provide variable-width, positive input voltage pulses to the low
terminal of winding 614 in power circuit 600.
The primary winding 614 of transformer 610 is connected in series
with resistance 604 between the positive terminal of AC/DC
conversion circuit 300 and the collector of transistor 530. Thus,
with each variable width, positive voltage pulse applied to the low
terminal of primary winding 614, the flow of current through that
winding is interrupted and a pulse of corresponding width is
induced in the secondary winding 612 and applied across the
base-emitter junction of power transistor 608. Consequently,
transistor 608 is rendered conductive for variable periods of time
corresponding to the width of each input pulse thus generated
across secondary winding 612 of transformer 610. During these
periods of conductivity of transistor 608, current flows from the
positive terminal of AC/DC conversion circuit 300, through input
winding segment 618 of auto transformer 616, and through the
collector-emitter junction of transistor 608 to ground. Thus,
high-frequency power pulses are generated across the output winding
618 + 620 of auto transformer 616. These periodic power pulses,
whose frequency corresponds to that of high-frequency oscillator
400, are applied to the resonant circuit 700.
The resonant circuit 700 comprises first capacitance 702 connected
across the output terminals of the auto transformer 616, a second
capacitance 704 of approximately one-third the magnitue of first
capacitance 702, and an inductance 706 connected between the low
terminals of capacitances 702 and 704, whose high terminals are
both connected to the positive output terminal of AC/DC conversion
circuit 300, and to the lamp filament 204 by a center-tap
connection to secondary winding 104 of transformer 100. The low
side of capacitance 704 is connected through a center-tap
connection to secondary winding 106 of transformer 100 to filament
202 of lamp 200. The high-frequency power pulses appearing across
the output terminals of autotransformer 616 are injected into the
series resonant circuit 700 and cause that circuit to resonate at
the second harmonic of the frequency of the power pulses when the
impedance of lamp 200 is high, i.e., when the lamp has not been
started. Consequently, the voltage across the smaller capacitance
704 becomes very high and effects start-up of the lamp 200. The
voltage thus developed across the relatively high impedance of
capacitance 704 has the frequency of the second harmonic of the
high frequency power pulses injected into resonant circuit 700,
i.e., 56 kilohertz. When the impedance of the lamp 200 is lowered
following the initiation of gaseous discharge therein capacitance
704 is effectively shunted and the resonant circuit which now
includes the low impedance load resonates at the fundamental
frequency of the power pulses injected into resonant circuit 700,
i.e., 28 kilohertz. Inductance 706 also serves to isolate injection
transients from the load. The leakage inductance of the auto
transformer 616 provides the necessary slow-down action on the
charging current to capacitance 702, which in turn loads the auto
transformer 616 so as to prevent large inductive kicks on power
transistor 608. By judicious selection of the characteristics of
auto transformer 616, dissipation in transistor 608 can be
minimized.
Light pipe 800 channels a sample of the light output of gaseous
discharge lamp 200 as a first input to phototransistor 956 in the
feedback signal generating circuit 900. Because this first input is
a small fraction of the output of lamp 200 shown in FIG. 2(f), it
will have the same waveform as the sampled light output. A second
input is provided to phototransistor 956 by the light-emitting
diode 944, which is pulsed on during alternate nulls in the light
output of lamp 200. Light-emitting diode 944 is preferably of
gallium arsenide, which has a half life of 75 years and therefore
makes a very stable photoelectric transducer. Each rectangular
output pulse of oscillator 400 shown in FIG. 2(a) is fed to an
integrating circuit comprising resistance 926 and capacitance 942,
from the junction of which a saw-tooth wave input as shown in FIG.
2(b) is derived and provided to inverter 966, which is biased by
resistance 919 connected between the +5 volt DC line and the
inverter input terminal. Since the inverter 966 is responsive to
generate an output only during the period of time in which the
input voltage waveform is below the threshold voltage of the
inverter, output pulses of shorter duration and delayed in phase
with respect to the input pulses from oscillator 400 will result.
Absent an input signal, the output of inverter 966 is normally a
low positive voltage. When an input signal is provided to the
inverter 966, a positive-going pulse corresponding in duration to
the below-threshold portion of the input signal results as shown in
FIG. 2(c), and is fed through fixed resistance 904 and variable
resistance 902 to the anode of light-emitting diode 944. Thus,
because of the aforementioned phase delay, the light-emitting diode
944 is pulsed on during alternate nulls in the light output of lamp
200. Because the oscillator 400 has a duty cycle of approximately
50 percent, and because of the reduced width of the output pulses
of inverter 966 as compared to those of oscillator 400, the
light-emitting diode 944 has a duty cycle of about 10 percent.
With these two input components, the net light input to
phototransistor 956 will have a waveform as shown in FIG. 2(g). The
output voltage derived at the collector of phototransistor 956 will
have a like waveform, but of inverted polarity and with a DC
component added. Since the phototransistor 956 is operated in the
AC mode, the circuit is not adversely affected by DC temperature
drift, by the light history or aging of phototransistor 956, or by
replacement thereof.
A voltage dividing network is formed by resistances 908, 910, 912
and 914 connected in series across voltage-regulating diode 524. A
DC bias voltage derived from the junction of resistances 912 and
914 is provided to the base of transistor 962, which is part of a
synchronous detector further comprising a differential amplifier
comprising transistors 958 and 960. Transistor 958 is pulsed on in
synchronization with the energization of light-emitting diode 944
by the application of each positive output pulse of inverter 966
through the differentiating circuit formed by capacitance 930 and
resistance 916. Thus, each input signal at the base of transistor
958 is as shown in FIG. 2(d). Since transistor 958 is biased
normally non-conductive, only the positive spikes of this input
signal will cause an output to be generated at the collector. This
output will be a negative-going spike, which will be fed through
capacitance 938 to a positive peak-to-peak detector comprising
diodes 954 and 952 and capacitance 940. Similarly, transistor 960
is pulsed on by the positive spike portion of the input signal
formed by the differentiation of the rectangular pulses of
oscillator 400 by the differentiating circuit formed by capacitance
932 and resistance 922. Again, the output at the collector will be
a negative-going spike, which will be fed through capacitance 936
to a negative peak-to-peak detector circuit comprising diodes 950
and 948 and common capacitance 940. Capacitance 940 is normally
charged slightly positive.
The magnitude of the pulses appearing at the collectors of
transistors 958 and 960 is controlled by the degree of conductivity
of transistor 962, which is determined by the output voltage of
phototransistor 956. When fed through blocking capacitor 928 to the
base of transistor 962, the DC component of the output voltage of
phototransistor 956 is removed. Transistor 962 is biased by an
emitter network comprising resistance 924 and capacitance 934
connected in parallel. Since transistor 958 is pulsed on in
synchronization with the constant-intensity light pulses of the
light-emitting diode 944, the negative-going spikes appearing at
its collector will be substantially constant. However, transistor
960 is pulsed on in synchronization with alternate peaks of the
light output of lamp 200, and as these peak values vary, the
conductivity of transistor 962 and consequently the magnitude of
the negative-going spikes appearing at the collector of transistor
960 will also vary. For example, if the peak value of the light
output of lamp 200 decreases below a predetermined normal level,
transistor 962 will become more conductive than normal, thus
providing larger-than-normal spikes at the collector of transistor
960, with the result that capacitance 940 becomes increasingly
negative. Consequently, transistor 964 will become less conductive
than normal resulting in a more positive DC bias being applied at
the base of transistor 526 by bias circuit 1,000. Consequently,
wider pulses are developed at the collector of transistor 530, and
more power will be applied across the filaments 202 and 204 of lamp
200 to increase the intensity of the light output.
Bias circuit 1,000 comprises resistances 1002 and 1004 connected in
series between the base of transistor 526 and the output of
feedback signal generating circuit 900, and a resistance 1006
connected from the high side of voltage-regulating zener diode 524
to the junction of resistances 1002 and 1004. The light pipe 800 in
combination with feedback signal generating circuit 900 and bias
circuit 1000 form a feedback loop from the lamp to the first stage
of the two-stage DC amplifier in the variable-width pulse generator
500. The variable feedback signal is added through resistance 1004
to the steady positive bias voltage generated across resistances
1006 and 1002 of the bias circuit 1000. Thus, if the intensity of
the light output of lamp 200 is too high, the variable DC voltage
component supplied by feedback signal generating circuit 900 will
alter the bias at the base of transistor 526 by making it less
positive. Consequently, the DC component of the signal applied as
the first input to the NAND gate 532 will be lowered so as to cause
a decrease in the width of the output pulses of the pulse generator
500, resulting in decreased width of the power pulses fed to
resonant circuit 700. On the other hand, if the intensity of the
light output of lamp 200 is too low, the opposite variation is made
upon the bias voltage at the base of transistor 528, with the
opposite effect of increased pulse width.
In the circuit which forms the preferred embodiment of the
invention and which is shown in FIG. 1, the values of the various
circuit elements are as follows:
Resistances Capacitances 010 15K ohms 316 200 microfarads 012 470
ohms 518 .068 microfarad 502 1K ohm 520 .068 microfarad 504 10K
ohms 606 .068 microfarad 506 100 ohms 702 .1 microfarad 508 10K
ohms 704 .033 microfarad 512 10K ohms 928 .1 microfarad 514 4.7K
ohms 930 .033 microfarad 516 2K ohms 932 .033 microfarad 602 1.5K
ohms 934 10 microfarads 604 2K ohms 936 .068 microfarad 902 100
ohms 938 .068 microfarad 904 220 ohms 940 1 microfarad 906 10K ohms
942 .068 microfarad 908 4.7K ohms 910 10K ohms Inductances 912 22K
ohms 914 22K ohms 310 .05 henry 916 22K ohms 312 .05 henry 918 4.7K
ohms 706 .36 millihenry 919 10K ohms 920 4.7K ohms Diodes 922 22K
ohms 924 4.7K ohms 302 Varo Part No. 926 2.2K ohms 304 VS447 1002
10K ohms 306 1004 10K ohms 308 1006 10K ohms 522 1N914 524 1N5231
Transistors 944 MV-50 946 1N914 526 2N5183 948 1N914 528 2N5183 950
1N914 530 MJE340 952 1N914 608 DTS411 954 1N914 956 L14 958
Transformers 960 Part of CA3054 962 100 Primary winding 102-1145
turns 964 2N5183 Secondary windings 104 & L06-47 turns 610
Primary winding 614-5 turns NAND Gate Secondary winding 612-150
turns 616 Winding segment 618-84 turns 532 integrated with Winding
segment 620-14 turns oscillator 400; SN7400N Inverter 966 Part of
SN7400N
the advantages of the present invention, as well as certain changes
and modifications of the disclosed embodiment thereof, will be
readily apparent to those skilled in the art. It is the applicant's
intention to cover all those changes and modifications which could
be made to the embodiment of the invention herein chosen for the
purposes of the disclosure without departing from the spirit and
scope of the invention.
* * * * *