U.S. patent number 3,675,163 [Application Number 05/067,017] was granted by the patent office on 1972-07-04 for cascaded f. m. correlators for long pulses.
Invention is credited to Clinton S. Hartmann, William S. Jones.
United States Patent |
3,675,163 |
Hartmann , et al. |
July 4, 1972 |
**Please see images for:
( Certificate of Correction ) ** |
CASCADED F. M. CORRELATORS FOR LONG PULSES
Abstract
Methods and apparatus are disclosed for producing a frequency
dispersive surface wave delay device or correlator having a large
time bandwidth product. The device comprises several sections, each
of which contributes a discrete frequency dispersive delay to the
incident signal. These sections are cascaded together and the
individual delays are additive producing a device having a large
time bandwidth product. Each section comprises at least two
interdigital surface wave transducers deposited on a piezoelectric
substrate, at least one of the transducers having electrodes of
graded periodicity. A Fourier transform computer program may be
used to optimize the overall correlator characteristics by defining
the optimum weighting pattern to be utilized on one or both of the
transducers of each cascaded section.
Inventors: |
Hartmann; Clinton S. (Dallas,
TX), Jones; William S. (Richardson, TX) |
Family
ID: |
22073190 |
Appl.
No.: |
05/067,017 |
Filed: |
August 26, 1970 |
Current U.S.
Class: |
333/150;
310/313R; 310/313B |
Current CPC
Class: |
H03H
9/44 (20130101) |
Current International
Class: |
H03H
9/44 (20060101); H03H 9/00 (20060101); H03h
007/30 (); H03h 009/30 () |
Field of
Search: |
;333/30,72,6
;310/9.7,9.8 ;343/17.2 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Lieberman; Eli
Assistant Examiner: Nussbaum; Marvin
Claims
What is claimed is:
1. A frequency dispersive correlator having a large time-bandwidth
product capability for compressing an input pulse that sweeps
through a span of frequencies in a predetermined manner from a
first preselected frequency to a second preselected frequency
comprising:
a. a piezoelectric single crystalline substrate;
b. a plurality of pairs of broadband interdigital surface wave
transducers defined on the surface of said substrate, one of said
transducers serving as the input transducer and the other as an
output transducer, each pair of transducers aligned to define a
separate acoustic channel across the surface of said substrate, the
plurality of acoustic channels so defined being essentially
parallel;
c. a plurality of frequency dispersive arrays, respective ones of
which are interposed intermediate the input and output transducers
of each of said plurality of pairs of transducers, each of said
dispersive arrays being defined by an interdigitated array of
electrodes deposited on the surface of said substrate, said
electrodes having a graded periodicity corresponding to the
wavelengths of respective portions of the frequency span of said
input pulse, the bandwidth of said pulse being divided into as many
successive segments of frequency spans as there are plurality of
pairs of transducers, the first of said plurality of dispersive
arrays having electrodes with graded periodicity corresponding to
the wavelengths of the first segment of frequency spans starting
with said second preselected frequency, successive dispersive
arrays having electrodes of graded periodicity to match the
wavelengths of successive segments of frequency spans;
d. means for electrically connecting said plurality of acoustic
channels in series; and
e. means for electrically connecting said plurality of dispersive
arrays in parallel whereby an input pulse sweeping in frequency
from said preselected first frequency to said preselected second
frequency produces an electrical signal across said correlator that
is of relatively short duration with respect to said input
pulse.
2. A frequency dispersive correlator having a large time-bandwidth
product capability for compressing an input pulse that sweeps
through a span of frequencies in a predetermined manner from a
preselected first frequency to a preselected second frequency
comprising:
a. a piezoelectric single crystalline substrate;
b. a plurality of frequency dispersive sections formed along
separate essentially parallel acoustic channels on said substrate,
each of said plurality of dispersive sections comprising input and
output interdigital surface wave transducers, the input transducer
being defined by an interdigital array of electrodes of graded
periodicity exactly corresponding to the wavelengths of the
frequency variations of said input signal, each of said output
transducers being defined by an interdigital array of electrodes of
graded periodicity corresponding to the wavelengths of a time
reversed image of said input pulse, said input and output
transducers being formed on the substrate such that electrodes
having a periodicity matching the frequency components of said
second preselected frequency are adjacent said input and output
transducers being amplitude weighted according to the square root
of the frequency response required of each of said sections;
and
c. means for cascading said plurality of frequency dispersive
sections whereby each section imparts a delay to said input pulse,
a total delay of the cascaded sections substantially equalling the
duration of said input pulse.
3. A frequency dispersive delay device having a large
time-bandwidth product capability comprising a plurality of
separate frequency dispersive delay sections respectively disposed
in separate acoustic channels on a common piezoelectric substrate,
said sections electrically connected in series, each section
respectively including a plurality of collinear interdigital
surface wave transducers at least one of which is defined by
interdigitated electrodes having a graded periodicity corresponding
to at least a portion of a selected input pulse, wherein said at
least one transducer is effective to produce a portion of the total
delay of said device.
4. A frequency dispersive correlator having a large time-bandwidth
product capability for compressing an input pulse that sweeps
through a band of frequencies in a predetermined manner from a
preselected first frequency to a preselected second frequency
comprising:
a. a piezoelectric single crystalline substrate,
b. a plurality of separate frequency dispersive delay section
respectively disposed in separate acoustic channels on said
substrate and electrically connected in series, each section
respectively including collinearlly a first relatively broad band
transducer having electrodes of constant periodicity corresponding
to the center frequency of said input pulse and a second frequency
dispersive array having electrodes with a graded periodicity
corresponding to the time reversed image of the frequency span of
said input pulse, each of said sections providing a portion of the
total frequency dispersive delay of said correlator.
5. A frequency dispersive correlator having a large time-bandwidth
product capability for compressing an input pulse that sweeps
through a span of frequencies in a predetermined manner from a
first preselected frequency to a second preselected frequency
comprising:
a. a piezoelectric single crystalline substrate,
b. a plurality of separate frequency dispersive delay sections
respectively disposed in separate acoustic channels on said
substrate and electrically connected in series, each section
respectively including collinearlly a first relatively broad band
transducer having electrodes of constant periodicity corresponding
to the center frequency of said input pulse and a second frequency
dispersive array having electrodes with a graded periodicity
corresponding to the time reversed image of the frequency span of
said input pulse, each of said sections providing a portion of the
total frequency dispersive delay of said correlator.
6. A frequency dispersive correlator having a large time-bandwidth
product capability for compressing an input pulse that sweeps
through a span of frequencies in a predetermined manner from a
first preselected frequency to a second preselected frequency
comprising:
a. a piezoelectric single crystalline substrate,
b. a plurality of separate frequency dispersive delay sections
respectively disposed in separate acoustic channels on said
substrate and electrically connected in series, each section
respectively including collinearlly first and second interdigitated
surface wave transducers, at least one of said transducers being
defined by electrodes having a graded periodicity and wherein the
interaction length of respective electrode pairs of said at least
one transducer is selectively defined to provide amplitude
weighting thereby to enhance the characteristics of said
correlator, each of said sections providing a portion of the total
frequency dispersive delay of said correlator.
7. A frequency dispersive correlator as set forth in claim 6
wherein said first transducer is a broad-band transducer defined by
interdigitated electrodes having a constant periodicity
corresponding to the center frequency of said input pulse.
8. A frequency dispersive correlator as set forth in claim 6
wherein said first transducer is defined by electrodes having a
graded periodicity corresponding to the frequency span of said
input pulse.
9. A frequency dispersive correlator as set forth in claim 6
wherein said second transducer has a periodicity and amplitude
weighting which is defined by the inverse Fourier Transform of the
desired frequency response.
Description
This invention relates to surface wave delay devices, and more
specifically to surface wave frequency dispersive sections and
methods for cascading same to produce a preselected delay vs.
frequency characteristic.
There are many purposes, for example, in certain radar systems, in
which it is required to convert a relatively long pulse or train of
pulses which sweep in frequency in a predetermined manner, for
example, linearly, between two limiting values of frequency, into a
shorter pulse containing most of the incident energy. There are
various known ways of satisfying such a requirement, such as using
a dispersive electrical delay line composed of lumped circuit
elements. Such electrical delay lines, however, are expensive,
difficult to design and due to inevitable losses in the coils in
the lumped circuits do not operate satisfactorily. Further, as a
result of the large number of reactive elements employed in such
lines, it is difficult to avoid the generation of false pulses due
to periodic error in the line. Additionally, bulk grating
dispersive delay lines, meandering lines, etc., have been used to
achieve the required pulse compression. Such systems, however, have
extremely high insertion loss, are unduly large, are very expensive
and are sensitive to temperature variations.
It has also been proposed to use surface wave devices to produce
frequency dispersive correlators. To date, however, it has not been
possible to achieve large time bandwidth products with surface wave
correlators because such devices have conventionally required a
substrate of single-crystal piezoelectric material of a continuous
length sufficient to delay the signal an amount equal to the
duration of the original pulse which it is desired to compress.
This large pulse length required for large time bandwidth products
has required long sections of single-crystal material.
Piezoelectric crystalline materials, such as lithium niobate, are
very fragile and long lengths are exceedingly difficult to handle,
making it impractical to use lengths of crystals greater than about
three to four inches in length, which would correspond roughly to
about a 20 to 30 microsecond delay. It is desirable, however, to
use surface wave frequency dispersive correlators because of the
advantages obtained relative to size, cost, lower insertion loss,
etc.
Accordingly, it is an object of the present invention to produce a
surface wave frequency dispersive correlator having a large time
bandwidth product.
It is another object of the present invention to produce a surface
wave frequency dispersive correlator for long pulses by cascading a
plurality of relatively short delay sections.
Briefly and in accordance with the present invention, a frequency
dispersive device for large time bandwidth products is produced by
cascading a plurality of frequency dispersive sections, each of
which comprises a plurality of surface wave interdigitated
transducer arrays, at least one of which is frequency dispersive,
deposited colinearly on a piezoelectric substrate. Each section
contributes a portion of the total desired delay such that when all
of the sections are cascaded together, a total delay equal to the
pulse duration of the incident pulse is produced. In one embodiment
the frequency span of the input pulse, which sweeps from a
preselected low frequency to a preselected high frequency, or vice
versa, is divided into a plurality of frequency segments, each
segment covering a different region of the bandwidth from the low
frequency point of the input pulse to the high frequency point of
the input pulse. Each individual section, then, is designed to
match respective frequency segments of the input pulse. In a
different embodiment of the invention, each dispersive array covers
the entire bandwidth of the input pulse and contributes a portion
of the total delay desired. In the preferred embodiment of the
invention, a Fourier transform computer program is utilized to
define the optimum weighting pattern of one or both of the
transducers of each of the sections to optimize the output
characteristics of the overall correlator.
The novel features believed to be characteristic of this invention
are set forth in the appended claims. The invention itself,
however, as well as other objects and advantages thereof may best
be understood by reference to the following detailed description of
illustrative embodiments when read in conjunction with the
accompanying drawings in which:
FIG. 1 pictorially depicts apparatus in accordance with one
embodiment of the present invention wherein a plurality of sections
have been cascaded;
FIG. 2 graphically depicts a typical pulse to be compressed in
accordance with the methods and apparatus of the present
invention;
FIG. 3 graphically depicts the pulse of FIG. 2 compressed in
accordance with the present invention;
FIG. 4 depicts a graph of the delay vs. frequency characteristics
of the embodiment of FIG. 1;
FIG. 5 pictorially depicts a different embodiment of the present
invention;
FIG. 6 depicts a graph of the delay vs. frequency of the embodiment
of FIG. 5;
FIG. 7 pictorially depicts a modification of the device of FIG.
5;
FIG. 8 is a graph of amplitude vs. frequency, depicting the Fresnel
ripples produced by one section and by a plurality of identical
cascaded sections; and
FIG. 9 pictorially depicts an embodiment of the present invention
wherein one of the transducers of each cascaded section is
amplitude weighted.
With reference to the drawings, a plurality of frequency dispersive
sections, each individually effecting a relatively short frequency
dispersive delay, are cascaded to produce a delay device with a
large time bandwidth product. The invention may better be
understood by reference to FIG. 1 wherein one illustrative
embodiment is depicted.
With reference to FIG. 1, a single crystalline piezoelectric
substrate is indicated at 14. The substrate may comprise, for
example, convenient lengths of lithium niobate, quartz, zinc oxide,
cadmium sulfide, or other piezoelectric materials known to those
skilled in the art. A plurality of frequency dispersive sections
10, 11 and 12 are defined on the surface of the substrate 14 to
define thereon separate, essentially parallel acoustic channels or
sections. Each of sections 10, 11 and 12 comprises an input
transducer 15, 19 and 23, respectively, a frequency dispersive
array 16, 20 and 24, respectively, and an output transducer 17, 21
and 25 respectively. Input transducers 15, 19 and 23, and output
transducers 17, 21 and 25 are preferably identical broadband
surface wave interdigital transducers, each defined by an
interdigitated array of electrodes deposited on the surface of
substrate 14. The bandwidth of these transducers is chosen such
that they pass the entire bandwidth of the input pulse without
significant distortion. A first plurality of electrodes 26 are
commonly connected to a conductive bar 27. Adjacent electrodes 26
are spaced apart by one wavelength of the center frequency of the
input pulse. A second plurality of electrodes 28 are commonly
connected to a second conductive bar 29, the second plurality of
electrodes 28 being interlaced with the first plurality of
electrodes 26 to form an interdigitated pattern. Adjacent
electrodes 26 and 28 are spaced apart by one half of a wavelength
of the center frequency of the input pulse. The electrodes 26 and
28 may comprise aluminum, gold, or other appropriate metals and may
be formed on the substrate 14 by conventional masking and etching
metallization techniques, or other techniques of defining a metal
pattern on a surface. Conventionally, a layer of metal is formed on
the surface of the substrate 14. A photoresist layer is formed to
overlie the metal layer, and selected areas of the photoresist
layer are exposed through a mask. This mask may be formed by
techniques known in the art. As described hereinafter, the mask may
be designed using a Fourier transform to define the desired
electrode pattern. The metal underlying the exposed areas is
selectively etched using etchants known in the art to thereby form
the required electrode pattern.
As an example of a train of signals that may be utilized as the
input pulse, reference is made to FIG. 2 wherein a typical pulse is
depicted at 30. Pulse 30, shown for illustrative purposes only as
being of 50 microseconds duration, may be used, for example, in a
radar system wherein it is desirable that the pulse be for as great
a duration as possible. Typical pulse lengths desired are from 30
to 100 microseconds. As understood by those skilled in the art, a
long pulse is required in order to increase the range of radar
systems, but some means for compressing the pulse to, for example,
0.2 microseconds duration, are required to obtain the necessary
resolution. Such a pulse is depicted at 32 in FIG. 3. In order to
obtain pulse compression, it is necessary to code the pulse 30 in
some manner. One method for coding the pulse is to very accurately
sweep the pulse through a range of frequencies from a minimum
frequency to a maximum frequency. For example, in FIG. 2 the
minimum frequency of the incident pulse is shown as being 8997.5
megacycles and the maximum frequency 9002.5 megacycles, defining a
bandwidth of 5 megacycles. It is to be understood, of course, that
the frequency bandwidth, the center frequency, pulse duration,
etc., will vary from system to system, depending upon the design
and specification requirements.
As mentioned previously, the incident pulse 30 in the example given
is in effect coded by having the pulse begin at a certain minimum
frequency and end at a certain maximum frequency. In general, the
pulse is swept from the minimum to the maximum frequency in a
linear manner during the duration of the pulse, but this is not a
restriction, and non-linear F.M. coding may also be used. Thus,
when the pulse 30 depicted in FIG. 2 initially begins, only the low
frequency components are transmitted. As the pulse is defined, the
frequency will increase until, at the end of the pulse, only the
high frequency components are transmitted. This pulse may be
detected and compressed by a correlator which is precisely matched
to the pulse phase and amplitude characteristics. For example, the
dispersive arrays 16, 20 and 24 shown in FIG. 1 are designed to
detect a pulse having a preselected phase and amplitude. As
described in more detail hereinafter, when a signal having the
exact frequency variations of the incident pulse is precisely
matched to the correlator, a short pulse of relatively large
amplitude will be produced across the correlator output
terminals.
Again, with reference to FIG. 1, each of the dispersive arrays 16,
20 and 24 is respectively comprised of a first plurality of
electrodes designated generally at 18, commonly connected to a
first conductive bar 31 and a second plurality of electrodes 22
commonly connected to a second conductive bar 33. Electrodes 18 and
22 are defined on the surface of the substrate in an interdigitated
array using conventional masking and etching metallization
techniques. The spacing between adjacent electrodes of the
dispersive arrays, that is, the periodicity of the electrodes,
varies in a predetermined manner from one end of the array to the
other. For example, with respect to array 16, the electrodes at the
end facing the input transducer 15 are defined so that the space
between the electrodes corresponds to one half the wavelength of
the high frequency components of the input pulse. That is, if the
input pulse 30 has a high frequency limit of 9002.5 megacycles, as
shown in FIG. 2, the spacing between adjacent electrodes 36 and 37
would correspond to one half of a wavelength of that frequency.
Progressing along the dispersive array 16 in a direction away from
the input transducer 15, the spacing of electrodes varies to match
the frequency variations defined by the input pulse; e.g., starting
at the high frequency limit thereof and decreasing toward the low
frequency limit.
For the embodiment depicted in FIG. 1, the correlator has been
divided into three separate sections respectively including
dispersive arrays 16, 20 and 24. Each dispersive array is
responsive to a different span of frequency variations of the input
pulse. In other words, the frequency span of the incident pulse 30
is divided into three parts, each part having a frequency span of
.DELTA.F. Dispersive array 16 is defined such that the spacing
between electrodes varies in a predetermined manner to match the
upper one third of the frequency span of the input pulse 30. The
end of the dispersive array 16 facing the input transducer 15 has
electrodes with a periodicity matching the maximum frequency of the
input pulse, the periodicity of the electrodes varying to match the
wavelengths of the input pulse such that the electrodes at the end
of the dispersive array facing the output transducer 17 have a
periodicity matching the maximum frequency F.sub.max of the input
pulse minus .DELTA.F. Similarly, dispersive array 20 has electrodes
with a periodicity at the end facing input transducer 19
corresponding with F.sub.max - .DELTA.F while the electrodes at the
end of dispersive array 20 facing the output transducer 21 have a
periodicity corresponding to F.sub.max - 2.DELTA.F. With respect to
the dispersive array 24, the end thereof facing the input
transducer 23 has electrodes with a periodicity corresponding with
F.sub.max - 2.DELTA.F while the opposite end thereof corresponds to
the minimum frequency of the input pulse. The frequency variations
defined along the length of each dispersive array exactly
corresponds with the frequency variations of a respective portion
of the input pulse.
While the example shown in FIG. 1 depicts the input pulse frequency
span being divided into three sections, each section being matched
by a frequency dispersive array, it should be appreciated that any
number of sections could be utilized in accordance with the
teachings of the present invention.
In operation, the correlator depicted in FIG. 1 is electrically
connected such that the respective acoustic sections are cascaded
in series and the dispersive arrays are electrically cascaded in
parallel. The output signal from the first acoustic section is
generated across output transducer 17. Since input transducer 15
and output transducer 17 are both broadband, all of the frequency
components of the input signal are preserved. Only a small portion
of the energy of the surface wave is extracted by the dispersive
array 16 between F.sub.max and F.sub.max -.DELTA.F since the
periodicity of the electrodes of dispersive array 16 is not matched
to those frequencies. The signal from output transducer 17 is
electrically connected to the input transducer of the second
acoustic section 19 by leads 40 and 41. Similarly, the signal from
the second acoustic section generated across output transducer 21
is electrically connected to the input transducer 27 of the third
acoustic section by leads 42 and 43. Dispersive arrays 16, 20 and
24 are electrically connected in parallel by leads 44-44'-44" and
45-45'-45". The overall electrical output terminals A-A' of the
correlator are connected across the parallel combination of
dispersive arrays 16, 20 and 24.
An input source 46 generates a pulse 30 which is applied to the
input transducer 15 by leads 47 and 48. Input transducer 15
generates an acoustic surface wave in the surface of substrate 14
in accordance with techniques understood to those skilled in the
art. The frequency of the acoustic wave so generated corresponds to
the input signal 30. The low frequency components of the input
signal 30 are the frequency components first generated by the
transducer 15 since they are the components first received,
assuming that the input signal sweeps from the low frequency to the
high frequency. If, instead, the input sweeps from the high
frequency to the low frequency, the signal would be applied across
transducer 25 rather than transducer 15. It should be noted that
either bidirectional or unidirectional transducers may be utilized
for the input and output transducers.
The low frequency components of the signal propagate along the
surface of the substrate 14 and pass under the dispersive array 16.
When the low frequency components of the input signal 30 have
reached the end of the dispersive array 16, the lower one third of
the frequency span of the input signal 30 will underlie the
dispersive array 16. The periodicity of the electrodes of the
dispersive array 16, however, does not correspond with the
wavelengths of any of the frequency components of the lower one
third of the frequency span of the input signal, and therefore the
signal is very low in amplitude, consisting of the leading
sidelobes of the compressed pulse generated across the output A-A'
corresponding to the correlator parameters and weighting used. This
portion of the output across A-A' is shown in FIG. 3 at 50.
As the input signal continues to propagate along the surface of the
substrate 14, it is detected by the output transducer 17 and
converted into an electrical signal. This electrical signal is
coupled to input transducer 19 by leads 40, 41. The input
transducer 19 generates an acoustic surface wave in the second
acoustic section of the substrate 14. Again considering the low
frequency components of the input signal 30, these components
travel under the dispersive array 20. Since the periodicity of the
electrodes in the array 20 does not precisely correspond with the
wavelengths of any of the low frequency components of the input
signal 30, the output across A-A' consists only of low amplitude
sidelobes. Similarly, output transducer 21 detects the acoustic
wave and generates an electrical output which is coupled
electrically by leads 42 and 43 to input transducer 23 in the third
acoustic section. Input transducer 23 generates an acoustic surface
wave in the piezoelectric substrate which propagates under
dispersive array 24. At the instant that the low frequency
components of the incident pulse 30 exactly underlie electrodes
49-51, an output is generated across A-A' since the electrodes
49-51 have been defined to exactly correspond to the wavelength of
the low frequency components of the incident pulse. Similarly, at
the instant the low frequency components of the incident pulse
exactly underlie electrodes 49-51, the high frequency components of
the incident pulse exactly underlie electrodes 36 and 37 of
dispersive array 16. These electrodes have a periodicity exactly
corresponding to the high frequency components of the input signal
and therefore generate an output across A-A'. In addition, all of
the frequency components of the input signal intermediate the high
frequency portions which underlie electrodes 36 and 37, and the low
frequency components which underlie electrodes 49 and 51 underlie
adjacent electrodes of the dispersive arrays 16, 20 and 24 which
exactly correspond to the wavelength of the respective frequencies.
Thus, a large pulse such as shown at 32 in FIG. 3 is produced
across output A-A'. This pulse is of very short duration since the
acoustic wave propagates continuously along the surface of the
substrate 14 and exactly underlies electrodes having a matching
periodicity at only one instant in time.
A graph of the delay vs. frequency of the output across A-A' is
shown in FIG. 4. As may be seen, the low frequency components of
the output are delayed more than the high frequency components
since they have had to travel a substantially greater distance
along the surface of the substrate 14 than have the higher
frequency components. The output contributed by dispersive array 24
is shown by the portion of the curve depicted at 53 in FIG. 4,
while the output contributed by dispersive arrays 20 and 16 is
shown respectively on the portions of the curve in FIG. 4 marked at
55 and 57. It may be seen that the frequency dispersive delay
characteristics of the curve in FIG. 4 resemble a stepped function,
there being certain areas wherein there is a delay that is not
frequency dependent, such areas being depicted at 59. These
undesirable non frequency dispersive delays are caused by the
presence of the acoustic non-interaction spaces B of FIG. 1 wherein
the acoustic wave travels along the substrate 14 without
interaction with a dispersive array and thus an equal delay is
imparted to all frequency components of the incident pulse 30.
These spaces within the correlator cause certain portions of the
input pulse to be lost, unless the input pulse is generated in
three portions (for the situation where three segments are
cascaded) to exactly match the three dispersive arrays including
the non-dispersive delays; that is, to exactly match the time delay
vs. frequency characteristic shown in FIG. 4.
With reference to FIG. 5, there is depicted a modification of the
circuit of FIG. 1 wherein the non-acoustic interaction areas are
eliminated. As in FIG. 1, for clarity of description, only three
acoustic sections are depicted. It is to be understood, of course,
that the number of acoustic sections will be determined by design
consideration considering the substrate material, the total delay
required, etc.
In FIG. 5, input transducers are indicated at 60, 62 and 64. These
transducers may be identical broadband interdigital transducers
having a uniform periodicity corresponding to the center frequency
of the input signal that the correlator is designed to compress.
Again, the input transducer must have sufficient bandwidth to
encompass the bandwidth of the input pulse. Frequency dispersive
arrays are indicated generally at 66, 68 and 70. These dispersive
arrays may be identical interdigitated arrays of electrodes defined
on the surface of the substrate 14 in such a manner that the
overall time delay vs. frequency of the correlator operates to
compress the input signal as desired. For example, the electrodes
may be defined on the substrate to have a graded periodicity
exactly corresponding to a mirror image of the input signal. It is
to be appreciated of courSe that other electrode patterns may be
utilized in accordance with the present invention.
Dispersive arrays 66, 68 and 70, and input transducers 60, 62 and
64 may be comprised of aluminum, gold, or other acceptable metals,
and may be defined on the surface of the substrate 14 by
conventional metallization techniques.
In operation, the output across dispersive array 66 is electrically
connected to the input transducer 62 by leads 65, 67; dispersive
array 68 is electrically connected to the input transducer 64 by
leads 69, 71; and the output is obtained across dispersive array 70
by leads 72, 73. It is to be noted that each of the disperSive
arrays 66, 68 and 70 has electrodes with a periodicity matched to
the entire frequency span of the input signal.
A signal source 46 generates a linear F.M. coded input signal which
is applied to the input transducer 60 by leads 75, 76. The input
transducer 60 generates an acoustic surface wave which propagates
along the surface of substrate 14. As the frequency components of
the input signal propagate to points underlying electrodes having a
periodicity that corresponds to that frequency, a signal is
generated across the dispersive array 66. This signal is
electrically coupled to the input transducer 62 by leads 65 and 67.
The input transducer 62 in turn generates an acoustic surface wave
in the surface of substrate 14 which propagates along the surface
of substrate 14 underlying dispersive array 68. Similarly, an
electrical signal is generated across dispersive array 68 and this
signal is electrically connected to input transducer 64 by leads
69, 71. Input transducer 64 generates an acoustic surface wave
which propagates along the surface of the substrate 14 under the
dispersive array 70. Each dispersive array 66, 68 and 70
contributes a frequency dispersive delay to the input signal, the
total delay corresponding to the summation of the individual delays
of the respective sections. With reference to FIG. 6, there is a
plot of the delay vs. frequency of the arrangement shown in FIG. 5.
Cross-hatched areas 80, 82 and 84 pictorially depict, respectively,
the delays contributed by dispersive arrays 66, 68 and 70. The
total delay is obtained by adding the individual delays of the
respective sections. This is shown by the dashed line 86. As may be
seen, the total delay is extremely linear and does not exhibit the
stepped response caused by acoustic non-interaction areas as shown
in FIG. 4.
While the individual dispersive arrays have been shown to be formed
in separate acoustic channels on the same substrate, it is to be
understood that they could be formed on separate substrates or even
on opposite sides of the same substrate, as may be desired.
FIG. 7 depicts a modification of a circuit shown in FIG. 5. In FIG.
7 input transducers are indicated generally at 87, 88 and 89,
respectively defining separate acoustic channels. These transducers
may be identical interdigitated arrays of electrodes defined on the
surface of the substrate 14 to effect an overall time delay vs.
frequency response of the correlator operable to compress the input
signal as required. In one embodiment, for example, the electrodes
may be defined to have a periodicity exactly corresponding to the
frequency span of the input pulse. Output transducers 90, 91 and 92
may also be identical and may, for example, correspond to a mirror
image of the input transducers 87, 88 and 89. It may be required,
however, to form the output transducers to have electrodes with a
periodicity different from the periodicity of electrodes of the
corresponding input transducer in order to obtain the desired
correlator characteristics. Each pair of input and output
transducers such as 87, 90 operates to form a frequency dispersive
section of the correlator, each section having electrodes with a
periodicity corresponding to the entire bandwidth of the input
signal.
In operation, a linear F.M. coded input signal is generated by
source 46 and is applied to the input transducer 87 of the first
acoustic channel by leads 99 and 100. The input transducer 87
generates an acoustic surface wave in the substrate 14, the low
frequency components being generated at the lefthand side of the
input transducer 87 where the electrode spacing corresponds to the
low frequency components of the input signal, and the high
frequency components being generated by the electrodes at the
righthand side of input transducer 87, where the electrode spacing
corresponds to the high frequency wavelengths. A signal is
generated across the output transducer 90 when the surface wave has
propagated to a point underlying electrodes of transducer 90 having
the appropriate periodicity. The high frequency components of the
input signal need travel only a short distance along the surface of
the substrate before being detected by electrodes at the lefthand
side of the output transducer 90, wherein the electrode spacing
corresponds to the high frequency wavelength of the input signal,
while the low frequency components of the generated acoustic wave
must travel along the surface of the substrate the combined length
of the input transducer and the output transducer before being
detected by the electrodes at the righthand side of the output
transducer 90. In this manner, a frequency dispersive delay is
imparted to the input signal. The electrical output generated
across the output transducer 90 is connected in series to the input
transducer 88 of the second acoustic channel by the leads 93 and
94. A further delay is imparted by the second acoustic channel and
the output from transducer 91 is electrically connected to the
input transducer 89 of the third acoustic channel by leads 95 and
96. The output from the device is obtained from across the last
serially cascaded transducer 92. Thus, each section imparts a
discrete frequency dispersive delay across the bandwidth of the
input signal producing a delay vs. frequency curve similar to that
shown in FIG. 6. The advantage of this method is the wide bandwidth
obtained by using graded input and output transducers without the
disadvantages of using a broadband input/output transducer which
generally exhibits a very high input impedance.
In certain applications it may be desired to cascade more than
about two or three frequency dispersive sections to obtain an
extremely large pulse time duration capability. Certain
difficulties, however, are encountered when sections are cascaded.
These difficulties are caused by the fact that the frequency
response (that is, amplitude and phase vs. frequency) of a
frequency dispersive array inherently contains Fresnel ripples
since each dispersive array has a finite time duration. These
ripples are depicted at 102 in the output response 104 shown in
FIG. 8. Theoretically for a perfect correlator the number of
Fresnel ripples increases as a larger time bandwidth product is
obtained. When identical sections are cascaded, however, the number
of Fresnel ripples does not increase but rather remains the same
and the Fresnel ripples produced by each section add in amplitude,
as shown in FIG. 8 by the dotted curve 105. Even if only one
frequency dispersive section is used, such as the section comprised
of arrays 87 and 90 of FIG. 7, incorrect correlation results making
it unfeasible to obtain accurate sidelobes, etc., in the compressed
pulse.
To overcome this incorrect correlation and deleterious Fresnel
ripple effects, a detailed design must be undertaken using
sophisticated techniques such as a Fast Fourier Transform (FFT) to
transform from the time domain--corresponding to the actual
geometry of the device--to the frequency domain or vice versa using
an inverse transform. The FFT determines the weighting of the
dispersive arrays required to produce the desired frequency
response.
There are several methods of implementing weighting of the
individual interdigital transducers to produce the required
amplitude and phase vs. frequency characteristics. Specifically it
is desired to obtain very low side-lobe levels. For instance the
sidelobe level of an unweighted correlator is only about 13 dB
whereas 30-40 dB is often required. Such sidelobe levels may be
obtained by appropriate weighting of the transducer.
Weighting can be implemented by varying the interdigital electrode
width effecting approximately a 2:1 weighting ratio, or by removing
selected interdigital electrodes altogether, or by amplitude
weighting. By amplitude weighting is meant varying the interaction
length or the amount of overlapping between adjacent electrodes of
the interdigital transducers. Since the signal produced when the
surface wave interacts with adjacent electrodes is proportional to
the amount of interaction length or overlap of the electrodes, the
amplitude vs. frequency characteristics of the output signal may be
varied by amplitude weighting of the electrodes.
The method of determining the weighting pattern is critical to
successful operation. The first step is to determine the required
impulse response to be produced by the convolutions of the cascaded
sections in order to obtain the desired frequency vs. amplitude
response characteristics. This is determined from the
specifications of the specific application; for example, certain
radar requirements would require a certain level of sidelobes, a
certain pulse bandwidth, compression ratio, etc. Knowing these
requirements it is known in the art to define a suitable impulse
response. Substrate material limitations and required
time-bandwidth define the number of sections that must be cascaded.
Consider for example that N sections are required to provide the
required overall time duration capability. The overall impulse
response F(t) of the overall correlator comprises the summation of
the delay characteristics of the individual sections. In the
frequency domain, the total frequency response G(.omega.) of the
correlator is found from F(t) using the FFT. The total frequency
response is obtained from the product of the frequency responses of
the individual sections. That is, G.sub.T (.omega.) = G.sub.1
(.omega.) .times. G.sub.2 (.omega.) .times. . . . G.sub.N
(.omega.). If it is desired to have identical sections such that
G.sub.1 (.omega.) = G.sub.2 (.omega.), etc., then the required
frequency response of each section is defined as the Nth root of
G.sub.T (.omega.). This gives the total frequency response required
for each section, each section comprising two arrays of electrodes
for the embodiment of FIG. 7, or the input and dispersive arrays
for the embodiment shown in FIG. 5. The frequency response of each
section G.sub.s (.omega.) is defined by G.sub.s (.omega.) = G.sub.o
(.omega.) .times. G.sub.w (.omega.) where G.sub.o (.omega.)
represents the frequency response of one array of electrodes of the
frequency dispersive section and where G.sub.w (.omega.) represents
the frequency response of the other array of electrodes. If, for
instance, the array having a response G.sub.o (.omega.) is
unweighted, the frequency response of the weighted transducer
G.sub.w (.omega.) may be determined by dividing G.sub.s (.omega.)
by G.sub.o (.omega.). The mathematical expression for an unweighted
transducer is known to those skilled in the art. Alternatively, the
square root of G.sub.s (.omega.) may be taken to give two identical
arrays for each section. Also, it may be convenient to assume some
arbitrary response for one array of the section and to use the FFT
to design the second array. After the frequency response of a given
array has been determined (using the FFT), the inverse Fourier
transform is accomplished by a Fourier transform computer program
to define the impulse response required for that array of
electrodes. As known to those skilled in the art, the impulse
response in the time domain defines the physical weighting pattern
of the transducer. Using the weighting pattern so produced, a mask
may be formed and the weighted transducer formed by conventional
metallization techniques.
In the embodiment shown in FIG. 1, it is not necessary to carry out
the design technique above described as the overall correlator
geometry is simply divided into N sections, each section covering
successive spans of the frequency spread of F.sub. max - F.sub.min
/ N.
As understood by those skilled in the art, the required weighting
of the frequency dispersive sections may not conform precisely to
the conventional convolution predicted by the FFT; i.e., with
amplitude weighting two colinear arrays do not convolve in an ideal
manner. This incorrect convolution may be avoided by using one
unweighted array, or a more complicated model of the actual
convolution, or by using electrode width weighting which convolves
conventionally.
With reference to FIG. 9, there are three frequency dispersive
sections or channels depicted generally at 106, 108 and 110,
cascaded in series wherein the transducers 112, 114 and 116 are
unweighted while the respective transducers 118, 120 and 122 are
weighted in accordance with the results of the Fourier transform as
above described. Amplitude weighting of the output transducer is
diagrammatically depicted by the curved lines such as 119 and 121.
These lines enclose the interaction area of the electrodes making
up the output transducer. It is to be appreciated that the precise
shape of curves 119 and 121 are determined from the Fourier
transform as above described and will vary depending upon the
specific design parameters. The input transducers for the
respective sections are shown diagrammatically in block form as
112, 114 and 116. These transducers are defined by an interdigital
array of electrodes having a graded periodicity which matches the
frequency variations of the input pulse desired to be
compressed.
The weighted transducers 118, 120 and 122 are also identical, the
weighting of the interdigitated electrodes being determined by the
Fourier transform in order to give the desired overall phase and
amplitude characteristics.
In operation, the transducer 118 is electrically connected in
series to transducer 114 by leads 107 and 109, and transducer 120
is electrically connected to transducer 116 by leads 111 and 113.
The output A-A' is obtained across transducer 122. Each channel is
reciprocal and the input and output of the correlator may be
interchanged with no change in characteristics.
Although specific embodiments of this invention may have been
described herein, it will be apparent to a person skilled in the
art that various modifications to the details of construction shown
and described may be made without departing from the scope of this
invention. Specifically, it is noted that an input signal which is
itself amplitude weighted may be used with the present
invention.
* * * * *