U.S. patent number 3,660,787 [Application Number 05/064,955] was granted by the patent office on 1972-05-02 for low frequency paper transient filters.
This patent grant is currently assigned to The United States of America as represented by the Secretary of the Navy. Invention is credited to Aly A. Mahmoud.
United States Patent |
3,660,787 |
Mahmoud |
May 2, 1972 |
LOW FREQUENCY PAPER TRANSIENT FILTERS
Abstract
Transients in electrical power systems are capable of causing
operational lfunctions in, and possible damage to, delicate
equipment such as computers and data processing apparatus. The
present disclosure is directed to the design of an
inductance-capacitance filter which effectively suppresses
externally-produced transients as well as those generated within
the load itself.
Inventors: |
Mahmoud; Aly A. (Oxnard,
CA) |
Assignee: |
The United States of America as
represented by the Secretary of the Navy (N/A)
|
Family
ID: |
22059366 |
Appl.
No.: |
05/064,955 |
Filed: |
August 19, 1970 |
Current U.S.
Class: |
333/181;
333/12 |
Current CPC
Class: |
H02H
9/005 (20130101); H02M 1/14 (20130101) |
Current International
Class: |
H02M
1/14 (20060101); H02H 9/00 (20060101); H03h
007/04 (); H04b 015/00 () |
Field of
Search: |
;333/76,70,12 |
Foreign Patent Documents
Primary Examiner: Lieberman; Eli
Assistant Examiner: Nussbaum; Marvin
Claims
I claim:
1. Apparatus for suppressing power line transients in the frequency
range extending from several kilocycles to approximately 400 Hertz,
said apparatus being effective to attenuate transients propagating
toward a load as well as those originating on the load side and
propagating back toward the power line source, said apparatus
comprising:
a filter network connected between said power line source and said
load, said network including a series inductor L and a shunt
capacitor C.sub.2 ;
a further shunt capacitor C.sub.1 interposed between said filter
network and said power line source;
the forward voltage attenuation characteristic .alpha..sub.1 of
said apparatus being given as ##SPC2##
the respective values of inductor L and capacitor C.sub.2 being
selected to yield optimum suppression of power line transients as
indicated by the voltage attenuation curve plotted for the
particular values of inductance and capacitance so selected.
2. Apparatus according to claim 1 in which said inductor is of the
high-permeability laminated iron core type.
3. Apparatus according to claim 1 in which inductor L has a value
of approximately 10 millihenries and capacitor C.sub.2 has a value
of between 25 and 50 microfarads, yielding a filter cut-off
frequency of approximately 220 Hertz.
4. Apparatus according to claim 1 in which the shunt capacitor
C.sub.2 is connected to a point on inductor L intermediate the ends
thereof, the voltage developed on that portion of the inductor
between such point and the end nearest the load being in effect
injected into the output of the filter network to compensate for
changes in the voltage developed on capacitor C.sub.2 in response
to variations in said load.
5. Apparatus according to claim 4 in which the two portions of said
inductor lying on opposite sides of said capacitor connection point
have a ratio of approximately 3:1, the smallest portion lying on
the load side of such point.
Description
STATEMENT OF GOVERNMENT INTEREST
The invention described herein may be manufactured and used by or
for the Government of the United States of America for governmental
purposes without the payment of any royalties thereon or
therefor.
BACKGROUND OF THE INVENTION
Oscilloscope recordings show conclusively that transients in
electrical power systems consist of voltage spikes and dips varying
in both magnitude and duration. They are usually characterized by a
very fast rise time of between 10 and 100 .mu. sec., and ordinarily
are in the form of an oscillatory voltage superimposed on the basic
60-Hertz sine wave. The frequency of these disturbances customarily
varies from a few kilocycles down to about 300 Hertz. Those from
external sources are a primary cause of computer operational
problems, while those generated internally can result in the
malfunctioning of synchronous communications equipment.
Power filters which are employed to suppress such transients must
satisfy a number of requirements. Not only must they attenuate the
disturbances to a level harmless to the load without at the same
time appreciably reducing the 60-Hertz line voltage, but they must
also produce a minimal rise or drop in the output voltage as the
load varies from light to full. In addition, they should not
overheat under full-load operation, and should be economical,
simple, compact and rugged with a high reliability factor and long
operating life.
SUMMARY OF THE INVENTION
The present concept is directed to the provision of a basically
two-element inductance-capacitance filter capable of protecting
electronic equipment against commonly-occurring harmful power
transients. With the addition of a capacitor across the filter
input, load-originated disturbances are effectively precluded from
being fed back onto the input power lines.
STATEMENT OF THE OBJECTS OF THE INVENTION
One object of the invention, therefore, is to provide means for
suppressing low-frequency transients in power lines.
Another object of the invention is to provide a two-element
inductance-capacitance filter capable of protecting electronic
equipment against externally-produced transients as well as those
generated within the load itself.
An additional object of the invention is to provide a filter of the
type described that is capable of yielding effective no-load to
full-load voltage regulation.
A further object of the invention is to provide a filter of the
type described which is not only simple and rugged but which
possesses high reliability and a long operating life.
Other objects, advantages and novel features of the invention will
become apparent from the following detailed description of the
invention when considered in conjunction with the accompanying
drawings wherein:
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a circuit diagram of a filter network designed in
accordance with a preferred embodiment of the present
invention;
FIG. 2 is a set of voltage attenuation curves for the circuit of
FIG. 1;
FIGS. 3(a), 3(b), 4(a), 4(b), 5(a) and 5(b) are waveforms of
voltages appearing at the input and output terminals, respectively,
of the filter network of FIG. 1;
FIG. 6 is a chart illustrating the effect of load variations on the
attenuation characteristics of the filter network of FIG. 1;
and
FIG. 7 is a modification of the circuit of FIG. 1 to achieve
voltage regulation during changes in load impedance.
DESCRIPTION OF THE PREFERRED EMBODIMENT
In designing an inductance-capacitance filter in accordance with
the principles of the present invention, it is necessary, in order
to obtain maximum transient attenuation, to select a cut-off
frequency substantially below the lowest frequency component of the
transients to be suppressed. However, the requirement for
non-amplification and non-attenuation of the 60 Hertz line voltage
places a limit on the selection of the lowest possible cut-off
frequency. Also, to prevent overheating, proper choice of wire size
for the inductor is essential, and, moreover, a capacitor with low
dielectric loss is called for. The economy, simplicity, compactness
and ruggedness requirements dictate a passive component design
having a minimum number of elements.
The inability of resistance-capacitance filters to provide a low
cut-off frequency rules out their use for the purposes herein set
forth. However, the two-element L-filter network disclosed
possesses the necessary simplicity, economy and compactness to
satisfy the demands imposed by the widely-different types of
installations where delicate equipment is operated.
A preferred form of filter network, together with its terminal
impedances, is illustrated in FIG. 1 of the drawings. The
impedances Rs and RL represent the internal source impedance and
the load impedance, respectively. This L filter is capable of
suppressing transients propagating towards the load designated as
forward filtering action. The capacitance C.sub.1 is added to the
filter network to suppress transients that may originate on the
load side and propagate back onto the critical bus, designated as
reverse filtering action. By this network arrangement, forward and
reverse filtering action is achieved.
The forward voltage attenuation characteristics of the filter
network of FIG. 1 are given by Equation 1: ##SPC1##
where .alpha..sub.1 = forward voltage attenuation
E.sub.S = input voltage
E.sub.L = load voltage
X.sub.C = 1/j.omega.C.sub.1 = capacitive reactance
X.sub.C = 1/j.omega.C.sub.2 = capacitive reactance
X.sub.L = j.omega.L = inductor reactance
R = inductor resistance
With R.sub.S and R.sub.L as known parameters, and by varying L and
C.sub.2 in Equation 1, a set of voltage attenuation curves is
obtained. From this set the best attenuation curve that satisfies
the filter requirements is selected. The proper values of
inductance L and capacitance C.sub.2 are then determined.
Since the internal power source impedance R.sub.S is usually much
less than unity, Equation 1 may be reduced to Equation 2 and
X.sub.C vanishes:
X.sub.C is essential only for reverse filter action; capacitor
C.sub.1 can be eliminated if reverse filter action is not
needed.
where R.sub.t = internal transient source impedance.
The dominant factor in Equation 3 is X.sub.c . The value of C.sub.1
depends on the frequency of the fundamental component of the
transients, f.sub.t, created by the load. The value of the
capacitance C.sub.1 is not critical and it may be selected by
choosing the resonant frequency of the LC.sub.1 circuit to be equal
to 1/2f.sub.t. C.sub.1 is given by Equation 4:
FIG. 2 shows a set of voltage attenuation curves obtained by
solving Equation 1 for a 10-ampere, 120-volt filter. Each curve
represents a possible design value for L and C.sub.2. In solving
Equation 1, R.sub.S is assumed to be constant and is given the
realistic value of 0.01 ohm. R.sub.L is taken to be 10.4 ohms and
the inductor resistance R is taken as 0.01 .omega./mh.
It can be seen from the voltage attenuation curves of FIG. 2 that
the cutoff frequency is decreased by increasing the values of
either L or C.sub. 2. In addition the choice of values for L and
C.sub.2, and thus the cutoff frequency, is greatly limited by the
requirement of nonappreciable voltage loss of gain at 60 Hertz. The
attenuation performance of this filter in the frequency range of
interest is typically 40 db per decade slope.
FIG. 3(a) of the drawings shows an oscilloscope recording of the
transients produced by a utility company switching on 100-kva power
factor correction capacitors. FIG. 3(b) illustrates the manner in
which the filter network of FIG. 1 effectively suppresses such
transients.
FIGS. 4(a) and 4(b) illustrate the effective suppression by the
circuit of FIG. 1 of low-frequency transients which cause
considerable distortion of the input waveform. FIGS. 5(a) and 5(b)
present a similar comparison of filter input and output waves when
the former contains a high-voltage pulse associated with a
low-frequency oscillation.
The two-element L-filter of FIG. 1 acts to maintain the output
voltage relatively constant as long as R.sub.L does not vary.
However, if the load does undergo variations for any reason, the
attenuation characteristics of the filter of FIG. 1 will be as
shown in FIG. 6 of the drawings for representative conditions.
However, since the load voltage is a function of the load current
passing through the inductor L, it is possible to achieve a
constant load voltage E.sub.L by use of the circuit illustrated in
FIG. 7 of the drawings.
In such Figure, the inductor L is effectively divided into two
portions a-c and a-b by connecting the capacitor C.sub.2 to a tap
at point a. Thus only portion a-c lies within the L-C network. For
an inductor of 80 turns, the portion a-c should consist of
approximately 60 turns and the portion a-b of approximately 20
turns.
The voltage V.sub.ab developed across that portion a-b of inductor
L lying outside the L-C network varies in both magnitude and
direction as the load changes. For example, when the load R.sub.L
increases, V.sub.ab also increases. This voltage V.sub.ab is
injected into the filter output to compensate for the voltage drop
V.sub.ad on capacitor C.sub.2. Consequently, the load voltage
(which is the vectorial summation of V.sub.ab and V.sub.ad) remains
constant within about 1 percent.
The attenuation performance for a 10-ampere, 120-volt filter is
shown in FIG. 2. Each attenuation curve Y and Z represents a
possible design value for L and C.sub.2. The design attenuation
curve must be selected to satisfy the filter requirements described
previously. The selection criteria may be summarized as
follows:
1. The attenuation curve should not have any voltage gain at any
frequency. This guarantees the suppression of all transient
harmonics as well as avoiding the amplification of any harmonics
that may exist in the power supplied.
2. There should not be any appreciable voltage loss or gain at 60
Hertz.
3. The cutoff frequency should be lower than the fundamental
component frequency of the incoming transients.
Attenuation curves Y and Z satisfy all design criteria. They
establish an inductance L of about 10 mh and a capacitance C.sub.2
between 25 and 50 .mu.f. The cut-off frequency of the filter is 220
Hertz, which is far below the lowest transient normally
present.
In order to lower the cut-off frequency of the filter and thus
suppress harmful transients in this region, it was found necessary
to employ a specially-designed inductor together with a high-value
capacitor. In contrast to the usual powdered iron inductors
utilized in filters of this type, it was discovered that one with a
laminated iron core would yield a larger value of inductance.
However, the presence of both high capacitance and high inductance
caused the no-load to full-load regulation to be less than
completely satisfactory.
To overcome this condition, the circuit of FIG. 7 was devised,
incorporating a "split" inductor one part of which is employed to
inject a voltage into the basic L-C filter output. The magnitude
and direction of this injected voltage depends on the load current,
on the mutual inductance between the two portions of the inductor,
and on the ratio therebetween. When such factors are properly
related, the circuit of FIG. 7 acts not only as a low cut-off
frequency filter but also as a voltage regulator.
In choosing an inductor, the following factors must be
considered:
1. The inductor should be as linear as possible. 2. It should not
saturate at full load. 3. It should carry the full load on a
continuous basis without appreciable heating.
Inductor linearity is usually obtained so that the inductance value
is relatively independent of the property of the core material. In
the basic inductance design formula, Equation 5, if 1.sub.g. is
chosen much larger than 1.sub.c /.mu. , the inductance L is
determined primarily by the air gap, and the effect of the
where A.sub.c = core cross-sectional area
N = number of turns of inductor
1.sub.c = iron core length, in.
1.sub.g = length of inductor air gap
.mu. = incremental permeability of the iron core
To prevent iron core saturation, the flux density at full load,
B.sub.ac, must not exceed the saturation value. The full-load flux
density is computed from Equation 6.
where E = I.omega.L
I = the full load current
.omega. = 2.pi.f radian frequency
B.sub.ac = full load flux density in gauss
The heating problem can be eliminated by minimizing the copper
losses. This is achieved by selecting the proper wire size to
obtain a low-resistance coil. For the 10-mh, 10-ampere inductor a
12-AWG wire should be chosen. The resistance for this wire is
0.00162 .omega./ft. It was determined from conventional inductor
design procedures that a 78-turn coil should be wound on a 1.5-inch
stack of standard 150 EI seiectron laminations. The resistance of
this coil is calculated as 0.1 ohm. The air gap of the inductor is
calculated as 0.030 inch to obtain 10 mh and assure linearity. With
10 amperes flowing at 60 Hertz, the voltage across the 10-mh
inductor is 37.7 volts. Substituting into Equation 6, the full load
flux density is 14,500 gauss, which is below the saturation value
of 16,000 gauss.
Obviously many modifications and variations of the present
invention are possible in the light of the above teachings. It is
therefore to be understood that within the scope of the appended
claims the invention may be practiced otherwise than as
specifically described.
* * * * *