U.S. patent number 3,633,109 [Application Number 04/769,144] was granted by the patent office on 1972-01-04 for negative resistance antenna amplifier arrangement.
This patent grant is currently assigned to Saba Schwarzwalder Apparati Bau-Anstalt August Schwer Sohne GmbH. Invention is credited to Hansrichard Schulz.
United States Patent |
3,633,109 |
Schulz |
January 4, 1972 |
NEGATIVE RESISTANCE ANTENNA AMPLIFIER ARRANGEMENT
Abstract
An oscillator circuit is kept at a predetermined
stable-operating point below the onset of oscillations by
high-resistance feedback in the emitter circuit. The tuned circuit
of the oscillator has one winding of a transformer whose second
winding is connected either in series between the antenna and the
receiver, or in parallel with the receiver. The impedance seen
looking into the second winding is a negative resistance.
Inventors: |
Schulz; Hansrichard
(Villingen/Schwarzwald, DT) |
Assignee: |
Saba Schwarzwalder Apparati
Bau-Anstalt August Schwer Sohne GmbH (Villingen-Schwarzwald,
DT)
|
Family
ID: |
7531826 |
Appl.
No.: |
04/769,144 |
Filed: |
October 21, 1968 |
Foreign Application Priority Data
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|
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Oct 21, 1967 [DT] |
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S 112511 |
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Current U.S.
Class: |
455/151.3;
455/291 |
Current CPC
Class: |
H03F
3/191 (20130101); H03F 1/34 (20130101); H03F
3/19 (20130101) |
Current International
Class: |
H03F
1/34 (20060101); H03F 3/19 (20060101); H03F
3/189 (20060101); H03F 3/191 (20060101); H04b
001/18 () |
Field of
Search: |
;179/17T,17HF,17U
;325/373,374,375,384,318,365 ;330/4.5,4.9,61A ;331/132,3,4 |
References Cited
[Referenced By]
U.S. Patent Documents
Other References
Transmission Systems for Communications, Bell Telephone
Laboratories, Inc., th Ed., 1970 pp. 85-87.
|
Primary Examiner: Griffin; Robert L.
Assistant Examiner: Leibowitz; Barry
Claims
What is claimed as new and desired to be protected by Letters
Patent is set
1. Receiving arrangement, comprising, in combination, antenna
means; a negative-resistance circuit means connected to said
antenna means, said negative-resistance circuit means comprising
oscillator circuit means having an amplifier element, said
amplifier element having a first and second output electrode and a
control electrode; high-resistance passive feedback means connected
to said first output electrode for maintaining the operating point
of said amplifier element at a predetermined stable point below
onset of oscillations; and high-frequency voltage divider means
connected to said amplifier element for furnishing additional
feedback in such a manner that the operating point of said
amplifier element lies in a region of relatively small changes in
amplification; and
2. An antenna arrangement as set forth in claim 1, further
comprising four-terminal amplifier circuit means having a pair of
input terminals connected to said interconnected antenna and
negative-resistance circuit means, said four-terminal amplifier
circuit means further having a pair of output terminals; and
receiver means connected to said pair of output
3. An antenna arrangement as set forth in claim 1, further
comprising receiver means connected to said interconnected antenna
means and
4. Antenna arrangement as set forth in claim 3 wherein said circuit
means is connected in series between said antenna means and said
receiver means.
5. Antenna arrangement as set forth in claim 3 wherein said antenna
means, said negative-resistance circuit means and said receiver
means are
6. Antenna arrangement as set forth in claim 1 wherein said
voltage-divider means comprise a first and second capacitor, each
of said capacitor having a leakage resistance, the value of said
leakage resistance in parallel to said control electrode of said
amplifier element being small compared to
7. An antenna arrangement as set forth in claim 1, wherein said
amplifier element is a transistor and wherein said first output
electrode is the
8. Receiving arrangement, comprising, in combination, antenna
means; a negative-resistance circuit means connected to said
antenna means, said negative-resistance circuit means comprising
oscillator circuit means having an amplifier element, said
amplifier element having a first and second output electrode and a
control electrode; high-resistance feedback means connected to said
first output electrode for maintaining the operating point of said
amplifier element at a predetermined stable point below onset of
oscillations, said oscillator circuit further comprising tuning
means for the remote tuning thereof and receiver means connected
to
9. An antenna arrangement as set forth in claim 8, wherein said
oscillator circuit further comprises transformer means having a
first winding connected in parallel with said tuning means and a
second winding, inductively coupled to said first winding,
connected to said antenna means
10. Antenna arrangement as set forth in claim 8 wherein said tuning
means
11. Antenna arrangement as set forth in claim 10 wherein said
capacitive tuning means comprise capacitive diodes.
Description
BACKGROUND OF THE INVENTION
This invention relates to antenna amplifiers. In particular, it
relates to antenna amplifiers wherein an equivalent negative
resistance is connected in series with said antenna by coupling an
amplifier element in an oscillator-type circuit to said
antenna.
The basic advantage of an antenna amplifier which presents an
equivalent negative resistance and is connected in a two terminal
configuration between the antenna and the receiver as compared to
the conventional antenna amplifiers connected in a four-terminal
connection is, that the antenna current and therefore the
equivalent antenna absorption surface are increased, thus greatly
increasing the signal-to-noise ratio. The negative resistance
increases the figure of merit (Q) of the circuit and thus decreases
the bandwidth of the antenna. The only limitation on the advantage
to be gained by the arrangement set forth in the present invention
is that a minimum bandwidth is prescribed for each transmission
channel. However, it will be demonstrated below that an increase in
gain of 29 db. for a frequency of 480 MHz. and 39 db. in the UHF
region may be obtained even considering the regulations for minimum
bandwidth mentioned above. Thus the increase in antenna gain by an
antenna amplifier in accordance with the present invention is of
great value when the fact is considered that an additional gain of
20 db. is sufficient to solve the reception problem in most fringe
areas.
Antenna amplifiers using a tunnel diode as a negative resistance
are known. However, the stability problems associated with these
circuits are such that they cannot be used in a series or two
terminal connection as is the amplifier of the present
invention.
SUMMARY OF THE INVENTION
It is an object of this invention to furnish a negative resistance
antenna amplifier which is sufficiently stable for use in a series
connection.
This invention comprises an antenna receiving arrangement
comprising antenna means and receiver means and circuit means
series connected between said antenna means and said receiver
means. Said circuit means are designed to provide an equivalent
negative resistance between said antenna means and said receiver
means, thus increasing the gain of the arrangement.
The circuit means for creating said above-mentioned equivalent
negative resistance comprise an amplifier element and feedback
means interconnected with said amplifier element in such a manner
that the operating point of said amplifier element is kept just
below onset of oscillations. These negative feedback means may for
example comprise a very high resistance in the emitter circuit of
the amplifier element. The circuit means also comprise coupling
means, which may for example be a tank circuit, for coupling the
interconnected amplifier element and its feedback means serially
between the antenna means and the receiver means.
The circuit of the amplifier element may be further stabilized by
providing high-frequency feedback by means of a voltage divider,
said high-frequency feedback being designed to keep the operating
point of the amplifier element in a region of relatively small
variation in amplification.
Phase shift in the feedback circuit, and thus a lack of symmetry
relative to the center frequency of the receiving arrangement is
avoided by causing the voltage divider used for the high-frequency
feedback to have a low leakage resistance compared to the input
resistance of the control electrode of the amplifier element which
is in parallel with said leakage resistance.
Capacitive diodes may be used as tuning elements. In a particularly
advantageous embodiment of the present invention, the tuning
elements and the operating point of the amplifier element are
chosen in such a combination that the feedback remains the same
over the whole tuning range.
A further improvement in stability of the receiving arrangement may
be achieved by inserting a conventional antenna amplifier in a four
pole arrangement between the antenna with the series connected
antenna amplifier with negative resistance on the one hand, and the
receiver means on the other hand. The distance between the antenna
and said second, four-pole amplifier should be small relative to
the wavelength of the receiving channel or alternatively a multiple
of half of said wave length, so that a definite terminal resistance
is formed at the input of this four-terminal network for the
antenna circuit.
The output of the second antenna amplifier is matched to the wave
impedance of the high-frequency cable leading to the receiver input
in the conventional fashion. This matching eliminates reflections
between the second amplifier and the receiver input. Furthermore,
the second amplifier serves as a decoupling element and thus
prevents the high-frequency cable and the input impedance of the
receiver from being reflected into the antenna circuit. Thus any
receiver may be connected to the output of the second amplifier
without requiring a change in the feedback arrangement of the
series connected antenna amplifier.
The high stability achieved by the above means permit the series
connection of the new antenna amplifier. The coupling elements
coupling the amplifier element with its associated feedback means
to the antenna and the receiver means may for example comprise tank
circuits.
Conventional highpass filters may be used for protecting the
amplifier elements against overvoltages caused by lightning.
The novel features which are considered as characteristic for the
invention are set forth in particular in the appended claims. The
invention itself, however, both as to its construction and its
method of operation, together with additional objects and
advantages thereof, will be best understood from the following
description of specific embodiments when read in connection with
the accompanying drawing.
BRIEF DESCRIPTION OF THE DRAWING
FIG. 1 is a first embodiment of a circuit in accordance with the
present invention;
FIG. 2 is a second embodiment of a circuit in accordance with the
present invention;
FIG. 3 is an equivalent circuit for the circuits shown in FIGS. 1
and 2; and
FIG. 4 is a plot of antenna gain as a function of the resistance
elements in said circuits.
DESCRIPTION OF THE PREFERRED EMBODIMENT
A preferred embodiment of the present invention will now be
discussed with reference to FIG. 1. The circuit of FIG. 1 has
antenna means denoted by 8, receiver means denoted by reference
numerals 11 and 12, where 12 denotes the high-frequency cable
leading into the receiver proper which is denoted by 11, a
four-terminal amplifier circuit denoted by reference numeral 9, and
two-terminal circuit means which comprise the remainder of the
circuitry shown in FIG. 1 and will be discussed in detail
below.
The transistor denoted by reference numeral 1 serves as an
amplifier element. This transistor 1 together with the primary
winding of transformer 2 which furnishes an inductivity and the
tuning capacitor 3, in addition to the capacitive voltage divider
comprising capacitors 4 and 5, form an oscillator circuit which is
maintained below the onset of oscillation. The high-stability
requirements of the arrangement are satisfied by the
high-resistance value of the emitter resistors 6 and 7, as well as
by the value chosen for the voltage-divider means comprising
capacitors 4 and 5. The reasonant frequency of the oscillator
circuit corresponds to the carrier frequency of the complete
receiving channel, thus causing the circuit means embodied in this
so-called oscillator circuit to present an equivalent negative
resistance of value -R.sub.T at the secondary winding of
transformer 2. As shown in FIG. 1, this negative resistance is
connected in series to the radiation resistance R.sub.S and the
resistance R.sub.V representing the antenna losses on the one hand,
and to a conventional four-terminal amplifier circuit, circuit 9,
on the other hand. Under these conditions, the equivalent circuit
for the arrangement is that shown in FIG. 3 which will be used as
the basis for the theory to be presented below. A half-wave dipole
is assumed to be the embodiment of antenna 8. For the chosen
coupling at peak current, this may be considered as a series
resonant circuit for the carrier frequency in the received
signal.
Other antennas as for example multiple dipole antennas, dipole with
reflecting mirrors in half-wave or full wave configurations, or
short dipoles (1<<.lambda./4) may be substituted with
whatever additional matching elements may then be required.
The only difference between the circuit shown in FIG. 2 and the
circuit shown in FIG. 1 is that the negative resistance -R.sub.T is
in parallel to the input resistance R.sub.E for FIG. 2, while it is
in series with said resistance in FIG. 1. The winding ratio of
transformer 2 must in general have a different value for the
circuit configuration shown in FIG. 2 as that for the circuit
configuration shown in FIG. 1. However, either circuit will lead to
the same antenna gain for a proper choice of components.
In accordance with the present invention, four-terminal amplifier
circuit, 9, decouples the antenna circuit comprising resistors
R.sub.S +R.sub.V +R.sub.E -R.sub.T from the high-frequency cable
and the receiver input so that a perfect match between the
amplifier output 10 having a positive resistance to the wave
resistance of the high-frequency cable 12 leading to the input
receiver 11 is achieved. Any mismatch at the receiver input does
not cause any back coupling to the antenna circuit and thus cannot
influence the stability of said antenna circuit.
An analysis of the negative-resistance circuit and the antenna
arrangement as a whole now follows.
Let it be assumed that the received carrier frequency is denoted by
f. A series resonant circuit resulting from a half-wave dipole
antenna is assumed. It is assumed that this antenna has radiation
resistance R.sub.S, a resistance R.sub.V representing the antenna
losses. The input resistance of the receiver means is denoted by
R.sub.E, while the equivalent negative series resistance coupled
into the circuit in a two-terminal arrangement is denoted by
-R.sub.T. Thus the equivalent circuit of FIG. 3 is derived. Below
onset of oscillations, the magnitude of R.sub.T must be less than
R.sub.S +R.sub.V +R.sub.E. This results in an efficiency:
.eta.=R.sub.E /(R.sub.S +R.sub.V +R.sub.E -R.sub.T)
It will be noted that this is greater than 1 when R.sub.T is
greater than R.sub.S +R.sub.V.
Let the gain G of the antenna amplifier be defined as the ratio of
the efficiency of .eta.(R.sub.T) for any given negative resistance
-R.sub.T to the efficiency .eta.(R.sub.T) for R.sub.T =0.
Then the following equation results:
The curve denoting this equation is shown in FIG. 4.
For a (.lambda./2) of dipole of length 2H and radius r.sub.o, the
following equations result:
a. the inductivity L:
L=(.mu.=.sub.0 /2.pi.).sup. . 1n (2H/r.sub.o) per kilometer
b. the capacitance C:
c. the wave impedance Z:
z=60.sup.. 1n (2H/r.sub.o).OMEGA.
d. the equivalent inductivity L*:
L*=L.sup.. 2/.pi..sup.. H; H=.lambda./4
e. the equivalent capacitance C*:
C*=C.sup.. 2/.pi..sup.. H; H=.lambda./4
f. the figure of merit of Q of the antenna then is:
g. If the value Q.sub.O for the figure of merit without an antenna
negative resistance amplifier (R.sub.T =0) and the gain G as
defined above are introduced into this expression for the figure of
merit Q, the following results are obtained: ##SPC1##
h. For a .lambda./2 dipole having a reflector R.sub.S +R.sub.V may
be assumed to be 60.OMEGA.. Furthermore R.sub.E is also
60.OMEGA..
For these values:
i. For R.sub.T =0, that is without the two terminal negative
resistance amplifier of the present invention:
Q.sub.0 =0.5.sup.. 1n (2H/r.sub.o)
j. If now f.sub.1 =480 MHz., 2H=0.9.sup.. 62=56 cm., and r.sub.o
=0.5 cm.:
Q.sub.01 =o.5.sup.. 1n 112=0.5.sup.. 4.72=2.35
k. For f.sub.2 =90 MHz., 2H=0.95.sup.. 333=317 cm. r.sub.o =0.6
cm:
Q.sub.02 =0.5.sup.. 1n 528=0.5.sup.. 6.27=3.13
1. For f.sub.1 =480 MHz., and a bandwidth .DELTA.f.sub.1 =7 MHz.
the required figure of merit:
Q.sub.1 =f.sub.1 /.DELTA.f.sub.1 =480/7=68.6
m. The maximum resulting gain then is:
G.sub.max .sup.(1) =Q.sub.1 /Q.sub.o1 =68.6/2.36=29.1=29.2 db.
n. For f.sub.2 =90 MHz., and a bandwidth .DELTA.f.sub.2 =0.3 MHz.
the following figure of merit results:
Q.sub.2 =f.sub.2 /.DELTA.f.sub.2 =90/0.3=300
o. This results in a maximum gain of:
G.sub.max .sup.(2) =Q.sub.2 /Q.sub.02 =300/3.13 =95.8=39.8 db.
p. The above-mentioned gains are theoretically obtainable if the
optimal value of R.sub.T is used. If these values are denoted
-R.sub.T .sup.(1) and -R.sub.T .sup.(2), the respective values may
be computed as follows: ##SPC2##
q. The effective surface of the antenna having a height H, a wave
impedance Z.sub.0 (=377.OMEGA.), resistances R.sub.S, R.sub.V,
R.sub.E, and -R.sub.T in the presence of the receiver may be
computed as follows:
r. Since the maximum gain equals:
both the effective surface area F.sub.a of the antenna as well as
the figure of merit Q are proportional to the maximum gain.
Thus it will be seen that the effective absorption surface of the
antenna, the gain G, and the figure of merit all are considerably
increased because of the effective negative resistance -R.sub.T
introduced by the two-terminal amplifier of the present
invention.
Physically this increase in the effective absorption surface of the
antenna may be explained as follows. For a constant antenna voltage
determined by the product of the transmitted field strength and the
effective antenna height, the negative resistance of the antenna
amplifier of the present invention results in an increase in
antenna current corresponding to the above-defined gain. Thus the
field established in the vicinity of the receiving antenna is
increased correspondingly, thus weakening the transmitted
field.
The power required for establishing the receiving antenna field is
furnished by the negative resistance. This intercoupling of the
amplifier of the present invention with the antenna field is the
basic assumption underlying the generation of a true gain as
compared with conventional antenna amplifiers.
Thus with conventional antenna amplifiers having a R.sub.T =0, an
increase in the effective absorption surface area of the antenna
may only be obtained by the use of multiple dipole antennas or
dipoles having reflectors. However, with use of a
negative-resistance amplifier as proposed by the present invention,
it is possible to effectively increase the surface area of the
antenna and thus the gain of the receiving system electrically,
without requiring additional antennas. Of course the arrangement
according to the present invention may also be used to increase the
gain of the multiple dipole arrangement, or dipoles with reflectors
which should then have an arrangement which has as broad a
bandwidth as possible so that the phase characteristic of the
antenna impedance within the transmission channel is relatively
flat and the figure of merit Q.sub.0 without amplifier (R.sub.T =0)
is low, that is that the maximum gain obtainable by the antenna
amplifier of the present invention is as great as possible.
In practice, the obtainable gains G depend first on the stability
of the circuit means used to generate the equivalent negative
resistance and further on the minimum bandwidth required.
While the invention has been illustrated and described as embodied
in a negative resistance amplifier using a transistor, it is not
intended to be limited to the details shown, since various
modifications, structural and circuit changes may be made without
departing in any way from the spirit of the present invention.
Without further analysis, the foregoing will so fully reveal the
gist of the present invention that others can by applying current
knowledge readily adapt it for various applications without
omitting features that, from the standpoint of prior art, fairly
constitute essential characteristics of the generic or specific
aspects of this invention and, therefore, such adaptations should
and are intended to be comprehended within the meaning and range of
equivalence of the following claims.
* * * * *