U.S. patent number 3,611,199 [Application Number 04/862,382] was granted by the patent office on 1971-10-05 for digital electromagnetic wave phase shifter comprising switchable reflectively terminated power-dividing means.
This patent grant is currently assigned to Emerson Electric Co.. Invention is credited to Paul Safran.
United States Patent |
3,611,199 |
Safran |
October 5, 1971 |
**Please see images for:
( Certificate of Correction ) ** |
DIGITAL ELECTROMAGNETIC WAVE PHASE SHIFTER COMPRISING SWITCHABLE
REFLECTIVELY TERMINATED POWER-DIVIDING MEANS
Abstract
A digital phase shifter of the reflection type is disclosed
which includes a directional coupler, hybrid network or other power
division network with switchable load means coupled to ports of the
coupler for effecting changes in reflection coefficients of the
network to provide incremental phase shifts or delays in the output
wave relative to the input wave. A four-port hybrid network is
provided with switchable loads, such as diodes, at some of the
ports, and the diodes are controlled by control signals. In one
arrangement switchable loads are connected to three of the four
ports to provide eight states of phase shift spaced 45.degree.
apart. Some other arrangements include more than one hybrid network
to provide a greater number of incremental phase shifts.
Inventors: |
Safran; Paul (Chesterfield,
MO) |
Assignee: |
Emerson Electric Co. (St.
Louis, MO)
|
Family
ID: |
25338370 |
Appl.
No.: |
04/862,382 |
Filed: |
September 30, 1969 |
Current U.S.
Class: |
333/109 |
Current CPC
Class: |
H01P
1/185 (20130101) |
Current International
Class: |
H01P
1/18 (20060101); H01P 1/185 (20060101); H01p
001/18 (); H01p 005/14 () |
Field of
Search: |
;333/10,11,31,31A |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Saalbach; Herman Karl
Assistant Examiner: Gensler; Paul L.
Claims
What is claimed is:
1. Electromagnetic wave phase shifting means comprising a
directional coupler having first port means for passing input and
output electromagnetic waves, and at least three other ports, and
electromagnetic wave reflective means coupled to each of said other
ports, said reflective means each being selectively changeable to
effect at least two different reflection coefficients thereby
providing any of at least eight output wave phase states.
2. The phase-shifting means according to claim 1 wherein one of
said wave-reflective means comprises power-dividing means having a
plurality of ports, and other switchable reflective means
respectively coupled to said last-named ports.
3. The phase-shifting means according to claim 1 wherein each of
said reflective means includes switchable load means to effect
either of two different reflection coefficient angles at their
respective ports.
4. The phase-shifting means according to claim 3 wherein each of
said reflective means includes switch means and predetermined
impedance means.
5. The phase-shifting means according to claim 3 wherein each of
said reflective means includes transmission line means, switch
means coupled to said line means to provide a predetermined length
of said line at the associated port when the switch means is closed
and to provide another predetermined length of said line when said
switch means is open, and means for selectively switching said
switch means between its closed and open states.
6. The phase-shifting means according to claim 5 wherein each of
said switch means comprises a diode.
7. Electromagnetic wave phase shifting means of the reflection type
comprising power-dividing means including first-port means for
passing input and output electromagnetic waves, and exactly three
other ports, three wave-reflective means including respectively
three impedance means coupled respectively to said three ports,
each of said impedance means having exactly two impedance values,
three switch means respectively connected to said impedance means
for switching its associated impedance means from one of its values
to the other, said wave-reflective means being individually
selectively operable to provide any one of eight phase shifts of
said output wave.
8. The phase-shifting means according to claim 7 wherein each of
said switch means comprises a solid-state diode, and control signal
means for controlling the conductivity of the diode.
9. The phase-shifting means according to claim 7 wherein said
power-dividing means comprises directional coupler means, each of
said reflective means including switchable load means to effect
either of two different reflection coefficient angles at its
respective port.
10. An electromagnetic wave phase shifting means of the reflection
type comprising a directional coupler having at least four ports
including first-port means for passing input-incident and
output-reflective waves, and second, third and fourth ports, said
second port being directly connected to said first port, said third
port being isolated with respect to said first port, and said
fourth port being coupled with respect to said first port, whereby
incident power flowing into said first port flows directly to said
second and fourth ports, and said third port receives power
substantially only from said second and fourth ports; first, second
and third switchable wave-reflective means coupled to said second,
third and fourth ports, respectively, each of said reflective means
having at least two states providing at least two reflection
coefficient angles at the port coupled thereto, and means for
individually selectively switching said reflective means to
selectively provide at least five different combinations of
reflection coefficient angles at said second, third and fourth
ports to selectively permit any one of at least five phase shifts
of the output-reflective wave at said first port, the ratio of the
power division between said second and fourth ports and the
relative values of said reflection coefficients being chosen to
provide output wave phase shifts in substantially angularly equal
incremental steps.
11. The phase-shifting means according to claim 10 wherein each of
said reflective means includes reactance means switchable between
two reactance values.
12. The phase-shifting means according to claim 10 wherein each of
said reflective means includes a diode and two different lengths of
transmission line.
13. The phase-shifting means according to claim 10 wherein the
ratio of the power division between said second and fourth ports is
chosen to provide a coupling ratio substantially less than 3db.
14. The phase-shifting means according to claim 13 wherein each of
said reflective means has exactly two states providing exactly two
reflection coefficient angles at the port coupled thereto and
wherein the ratio of the power division between said second and
fourth ports and the relative values of said reflection
coefficients are chosen to provide output wave phase shifts in
eight substantially angularly equal incremental steps.
Description
BACKGROUND OF THE INVENTION
This invention relates to electromagnetic wave phase shifters and
more particularly to phase shifters of the reflection type.
Electromagnetic wave phase shifters are useful in many types of
circuits. In one application, for example, a plurality of digital
phase shifters are used to control the direction of radiation of
electromagnetic energy in a phased-array antenna application or to
control the beam shape. It is, of course, desirable to make
shifters that are relatively small, lightweight, require relatively
small control power, and are relatively inexpensive, especially
where a number of phase shifters are used together, such as in the
above-mentioned application. Some phase shifters of prior art
required a number of hybrid couplers even where only a relatively
few increments of phase shift were required, and this resulted in
apparatus which was relatively expensive, great in size and weight,
and required relatively large control power.
SUMMARY OF THE INVENTION
Accordingly, it is a general object of the present invention to
provide a novel electromagnetic wave phase shifter of the
reflection type.
Another object of the invention is to provide an improved
electromagnetic wave phase shifter of the reflection type wherein
the above-mentioned undesirable features are substantially
obviated.
Another object is to provide a novel phase-shifting network of the
reflection type which requires relatively few coefficient of
reflection changing means while obtaining a relatively large number
of phase shift changes.
Still another object is to provide a phase shifter of the
reflection type which utilizes hybrid coupler or other power
division means and switchable coefficient of reflection means and
which is relatively inexpensive and requires relatively low control
power while providing a relatively large number of phase shift
changes.
In accordance with one aspect of the present invention, an
electromagnetic wave phase shifter is provided which includes a
directional coupler having a port for passing input and output
waves, and means for effecting a changeable coefficient of
reflection at at least some of the other coupler ports to provide
at least four different states of phase shift.
These and other objects and advantages of the present invention
will be apparent from the foregoing.
BRIEF DESCRIPTION OF THE DRAWING
FIG. 1 is a schematic diagram of a phase shifter in accordance with
an embodiment of the present invention.
FIG. 2 is a schematic diagram illustrating an embodiment of the
invention utilizing diodes; and
FIG. 3 is another embodiment of the invention.
DESCRIPTION OF THE PREFERRED EMBODIMENTS
Referring now to the drawings, and more particularly to FIG. 1, a
phase shifter 10 of the reflection type is shown including a hybrid
junction or directional coupler or other power division means 12
having four ports, P.sub.1, P.sub.2, P.sub.3 and P.sub.4. The port
P.sub.1 is shown as the input-output port and is connected to a
transmission line 14 for accepting an input wave to the phase
shifter 10 and accepting the reflected wave from the phase shifter.
Ports P.sub.2, P.sub.4 and P.sub.3 may be referred to as the
directly-connected port, coupled port, and isolated ports,
respectively. Power flow between the ports is in accordance with
the flow arrows shown on the coupler 12.
Connected respectively to the ports P.sub.2, P.sub.3 and P.sub.4
are wave reflection means 24, 26 and 28 for selectively effecting
two different coefficients of reflection at each of the ports. This
arrangement provides a total of eight different combinations of
reflection coefficients so that an output wave on line 14 will have
any one of eight phase values relative to the input wave on line
14, the phase values being separated by 45.degree..
The reflection means 24, 26 and 28 are illustrated as variable or
switchable admittance or impedance networks each shown including a
pair of admittances and a switch for selectively connecting the
associated port to the admittances. In FIG. 1, the reflection means
24 is shown including a switch S.sub.2 and admittances Y.sub.2 and
Y.sub.2 '; the reflection means 26 includes a switch S.sub.3 and
admittances Y.sub.3 and Y.sub.3 "; and the reflection means 28
includes a switch S.sub.4 and admittances Y.sub.4 and Y.sub.4
'.
While the reflection means 24, 26 and 28 are shown in FIG. 1 as
including mechanical switches and admittances, the loading of the
ports P.sub.2, P.sub.3 and P.sub.4 can, of course, take on a
variety of physical characteristics to yield desired switchable or
changeable reflection coefficients. In FIG. 2, for example, the
reflection means 24, 26 and 28 connected respectively to the ports
P.sub.2, P.sub.3 and P.sub.4 of coupler 12 are shown including
semiconductor diodes D.sub.2, D.sub.3 and D.sub.4 connected to
provide, respectively, two different lengths of line, l.sub.2 and
l.sub.2 ', l.sub.3 and 1.sub.3 ' and l.sub.4 and l.sub.4 ' to
provide different effective impedance values and reflection
coefficient phase angles when switched between "on" and "off"
states. The diodes, which may be PIN diodes, may be controlled by
suitable control signals or bias voltages applied thereto using
well-known isolating means between the control signal source and RF
circuit. As is well known by those skilled in the art, various
other forms of reflection means are possible, such as ferrites and
mechanical or electromechanical switches or shutters, the
particular form used being dependent, for example, on the frequency
under consideration, as well as other criteria.
The desired relative incremental phase shifts (.phi.) between the
input wave on line 14 and the output wave on line 14 utilizing the
four-port directional coupler 12 are obtained by suitably choosing
reflection means so as to obtain predetermined reflection
coefficients (.GAMMA.) and corresponding reflection coefficient
angles (.theta.) at the ports P.sub.2, P.sub.3 and P.sub.4 along
with a suitable coupling ratio for the coupler 12.
In the discussions which follow, numerical subscripts to the
various symbols relate respectively to the coupler ports having the
same numerical subscripts. Thus, .GAMMA..sub.2, .GAMMA..sub.3 and
.GAMMA..sub.4 represent the reflection coefficients at ports
P.sub.2, P.sub.3 and P.sub.4, respectively. Since there are two
different reflection coefficients at each of the ports P.sub.2,
P.sub.3 and P.sub.4, they will be distinguished from each other by
using prime symbols; thus, .GAMMA..sub.2 represents herein either
of two different reflection coefficients .GAMMA..sub.2 ' and
.GAMMA..sub.2 " at port P.sub.2 ; .GAMMA..sub.3 represents either
of the reflection coefficients .GAMMA..sub.3 ' and .GAMMA..sub.3 "
at P.sub.3 ; and .GAMMA..sub.4 represents either of the reflection
coefficients .GAMMA..sub.4 ' and .GAMMA..sub.4 " at P.sub.4.
Similarly, the reflection coefficient angle .theta..sub.2
represents .theta..sub.2 ' or .theta..sub.2 " at port P.sub.2 ; the
reflection coefficient angle .theta..sub.3 represents .theta..sub.3
' or .theta..sub.3 " at P.sub.3 ; and reflection coefficient angle
.theta..sub.4 represents .theta..sub.4 ' or .theta..sub.4 ".
In defining the values for the six reflection coefficient angles at
the coupler ports and the coupling ratio of the coupler 12 to
provide the eight possible combinations necessary to obtain the
desired eight output phase angles, a scattering matrix approach is
used. The scattering matrix for a four-port directional coupler is
well known and a detailed discussion of such may be found, for
example, in "Microwave Circuit Theory and Analysis," by R. N.
Ghose, McGraw-Hill, New York, 1963.
The scattering matrix [S] relates the reflected waves, b, to the
incident waves, a, at each of the coupler ports and may be
indicated as:
where p and q represent the fraction of the incident voltage at the
directly connected and coupled ports and where p.sup.2 +q.sup.2 =1
with p and q being positive real numbers and .times.ab.=20
log.sub.10 q is the coupling ratio in db.
Hence, in the present case:
a and b, with their respective subscripts, being indicated in FIG.
1.
With power incident at port P.sub.1, each of the other three ports
P.sub.2, P.sub.3 and P.sub.4 are loaded with reflection coefficient
means so that .GAMMA..sub.2 b.sub.2 =a.sub.2, .GAMMA..sub.3 b.sub.3
=a.sub.3 and .GAMMA..sub.4 b.sub.4 =a.sub.4, therefore:
This matrix equation can readily be solved to obtain a relation
between the input wave a.sub.1 and the output wave b.sub.1 by
algebraic methods whereby:
The ratio b.sub.1 /a.sub.1 is a complex number, the phase of which
is a total phase shift of the device for a particular set of
reflection states, .GAMMA..sub.2, .GAMMA..sub.3, and .GAMMA..sub.4.
Eight related equations for b.sub.1 /a.sub.1 can be written for the
phase of the output wave, one corresponding to each of the eight
possible combinations of the six reflection coefficient states,
.GAMMA..sub.2 ', .GAMMA..sub.2 ", .GAMMA..sub.3 ', .GAMMA..sub.4 '
and .GAMMA..sub.4 ".
The device is assumed, for purpose of analysis, to be lossless so
that the magnitude of the output wave b.sub.1 is equal to the
magnitude of the input wave a.sub.1 and the magnitudes of the
reflection coefficients are all equal to one. Thus, the ratio of
the output wave to the input wave b.sub.1 /a.sub.1 can be rewritten
in phaser notation as follows:
where .phi. is the total phase shift of the device and,
(6) .phi.=.phi..sub.s +.phi..sub.i
where .phi..sub.s is some arbitrary constant starting angle which
adds only to the absolute phase shift of the device and .phi..sub.i
is the incremental phase shift which is a function of the states of
the reflection coefficients.
The reflection coefficients can be written in complex number
notation as:
where i=2, 3, or 4 throughout the equation.
The relation between the input and output, equation (4), can now be
rewritten in a form which more readily gives a solvable relation
for the total phase shift.
Since the magnitudes of the reflection coefficients are one, the
complex conjugates can be written as
where .GAMMA..sub.i * is the complex conjugate of
.GAMMA..sub.i.
Factoring the produce -.GAMMA..sub.2 .GAMMA..sub.3 .GAMMA..sub.4
out of the relation for b.sub.1 /a.sub.1 in equation (4) results
in
Now factoring .GAMMA..sub.3 * from the numerator and .GAMMA..sub.3
from the denominator one obtains
Using the complex notation of equation (7) in the equation (10) and
then rationalizing the resulting complex expression, one skilled in
the art can arrive at the following equations (11) and (12) and
(13) for the phase shift of the device in terms of the phase angles
of the reflection coefficients.
Therefore, the incremental phase shift is defined as follows:
(13) .phi..sub.i
=f(x,.theta..sub.2,.theta..sub.3,.theta..sub.4)-.phi..sub.s
There is, of course, a total of eight equal incremental phase
shifts .phi..sub.i spaced 45.degree. apart. The general equation
(11), in other words, can be rewritten eight times, each for a
different combination of the reflection coefficient angles, the
equation (12) defining one of the terms of equations (11), (13). A
solution to these eight equations is obtained by choosing values of
X,.phi..sub.s,.theta..sub.2 ',.theta..sub.2 ", .theta..sub.3
',.theta..sub.3 ",.theta..sub.4 ' and .theta..sub.4 ", such that
the eight equations are simultaneously satisfied, as is shown
hereinafter.
By eliminating the arctangent term in equation (12), the desired
phase states can be obtained by stepping one reflection coefficient
angle 45.degree., a second 90.degree., and a third 180.degree.. The
arctangent term may be eliminated by forcing the numerator or
denominator to zero for all combinations of the reflection
coefficient states or by forcing the ratio of the numerator and
denominator to retain some constant value for the different
reflection coefficient combinations of states.
The way in which this may be accomplished is demonstrated by the
following example:
Force the numerator of the arctangent term in the equation (12) to
zero.
(14) i.e., sin.theta..sub.3 -(q.sup.2 sin.theta. .sub.2 -p.sup.2
sin.theta. .sub.4)=0.
Then if the denominator is positive the resulting angle is
0.degree., and if the denominator is negative, the resulting angle
is 2.pi. or, in effect, again 0.degree.,
(15) i.e., 2 tan.sup.-1 (0/+Den)=0.degree. and
(16) 2 tan.sup.-1 (0/-Den)=2x180.degree.=360.degree.
Therefore, the equations for the incremental phase shift can be
written:
(17) .phi..sub.i =.pi.+.theta..sub.2 +.theta..sub.4 -.theta..sub.3
-.phi..sub.s
Now the choice can be made of which reflection coefficient will
switch the phase 45.degree., which will switch it 90.degree., and
which will switch it 180.degree.. This choice determines the order
in which the incremental phase switches states and also the way in
which the numerator is set equal to zero.
To obtain one solution, for example, force .theta..sub.3 to switch
the phase in 180.degree. steps, .theta..sub.2 to switch the phase
in 45.degree. steps, and .theta..sub.4 to switch the phase in
90.degree. steps.
Therefore:
(18) .theta..sub.2 "-.theta..sub.2 '=45.degree.
(19) .theta..sub.3 "-.theta..sub.3 '=-180.degree.
(20) .theta..sub.4 "-.theta..sub.4 '=90.degree.
Now to make the numerator of the arctangent term zero for all
states, the following conditions are imposed:
(21) sin .theta..sub.3 '=0
(22) sin .theta..sub.3 "=0
(23) g.sup.2 sin .theta..sub.2 '-p.sup.2 sin .theta..sub.4 '=0
(24) g sin .theta..sub.2 "-p.sup.2 sin .theta..sub.4 '=0
(25) g.sup.2 sin .theta..sub.2 '-p.sup.2 sin .theta..sub.4 "=0
(26) g.sup.2 sin .theta..sub.2 "-p.sup.2 sin .theta..sub.4 "=0
The eight equations for the incremental phase shifts, therefore,
become:
(27) .theta..sub.i =.pi.+.theta..sub.2 '+.theta..sub.4
'-.theta..sub.3 '-.phi..sub.s =0.degree.
(28) .theta..sub.i =.pi.+.theta..sub.2 "+.theta..sub.4
'-.theta..sub.3 '-.phi..sub.s =45.degree.
(29) .theta..sub.i =.pi.+.theta..sub.2 '+.theta..sub.4
"-.theta..sub.3 '-.phi..sub.s =90.degree.
(30) .theta..sub.i = .pi.+.theta..sub.2 "+.theta..sub.4
"-.theta..sub.3 '-.phi..sub.s =135.degree.
(31) .theta..sub.i =.pi.+.theta..sub.2 '+.theta..sub.4
'-.theta..sub.3 "-.phi..sub.s =180.degree.
(32) .theta..sub.i =.pi.+.theta..sub.2 "+.theta..sub.4
"-.theta..sub.3 "-.phi..sub.s =225.degree.
(33) .theta..sub.i =.pi.+.theta..sub.2 '+.theta..sub.4
"-.theta..sub.3 "-.phi..sub.s =270.degree.
(34) .theta..sub.i =.pi.+.theta..sub.2 "+.theta..sub.4
"-.theta..sub.3 "-.phi..sub.s =315.degree.
The first equation fixes the value of .phi..sub.s to its desired
value and the remaining equations follow from the switching
conditions imposed above.
The specific switching angles and coupling coefficients are now
determined using the equations (18), (19) and (20) and the imposed
conditions which force the numerator of the arctangent phase term
to zero for all states. Hence, (35) sin .theta..sub.3 ' = sin
.theta..sub.3 " = 0
(36) .theta..sub.3 " -.theta..sub.3 '= -180.degree..
(37) Therefore, .theta..sub.3 ' = 0
(38) .theta..sub.3 " = - 180.degree..
Also, (39) q.sup.2 sin .theta..sub.2 ' - p.sup.2 sin .theta..sub.4
' = 0
(40 ) q.sup.2 sin .theta..sub.2 " - p.sub.2 sin .theta..sub.4 '
=0
(41) q.sup.2 sin .theta..sub.2 ' -p.sup.2 sin .theta..sub.4 " =
0
(42) q.sup.2 sin .theta..sub.2 " - p.sup.2 sin .theta..sub.4 " =
0
(43) .theta..sub.2 " - .theta..sub.2 ' = 45.degree.
(44) .theta..sub.4 " - .theta..sub.4 ' = 90.degree.
Subtracting equation (39) from (40) results in
Subtracting equation (39) from (41)
(50) p.sup.2 sin .theta..sub.4 ' - p.sup.2 sin .theta..sub.4 " = 0
on
(51) 0 = sin .theta..sub.4 ' - sin (.theta. .sub.4 '+90) But
(52) (.theta..sub.4 '+90.degree.) = sin .theta..sub.4 'cos
90.degree. + cos .theta..sub.4 ' sin 90.degree. = cos .theta..sub.4
'
(53) so sin .theta..sub.4 ' = cos .theta..sub.4 ' therefore
(54) tan .theta..sub.4 '= 1
Values of .theta..sub.2 ' and .theta..sub.4 ' which satisfy the
above tangent equations are: (55) .theta..sub.2 '= 67.5.degree.
(56) .theta..sub.4 '= 45.degree.
Using these values, the coupling ratio x can be determined from
equation (39)
(57) q.sup.2 sin 67.5.degree. - p.sup.2 sin 45.degree. = 0 or
(58) q.sup.2 (0.924)- p.sup.2 (0.707)= 0
Recalling that q.sup.2 + p.sup.2 = 1
(59) q.sup.2 (0.924)- (1-q.sup.2) (0.707)= 0 So
(60) q.sup.2 = 0.433
(61) p.sup.2 = 0.567
(62) Xdb. = -10 log.sub.10 q.sup.2 = -10 log.sub.10 0.433
(63) Xdb.= 3.63db. and
(55) .theta..sub.2 " = 67.5.degree.
(64) .theta..sub.2 " = 112.5.degree.
(56 .theta..sub.4 ' = 45.degree.
(65) .theta..sub.4 " = 135.degree.
The value of s is then obtained from the first of the eight
equations for the incremental phase. (66) .phi..sub.i = 0.degree. =
.pi.+.theta..sub.2 ' .theta..sub.4 '-.theta..sub.3 '-.phi..sub.s
so
(67) .phi..sub.s
=-0.degree.+180.degree.+67.5.degree.+45.degree.-0.degree. or
(68) .phi..sub.s =292.5.degree.
In conclusion, therefore, the desired parameters for this
particular design are:
The values for .phi. i as indicated above are readily verified by
substituting the eight possible combinations of the reflection
coefficients into the design equation (4) and rationalizing the
resulting complex expression.
In the illustrated embodiments of FIGS. 1 and 2, three-bit phase
shifter arrangements are shown in which the output wave can be
switched to provide as many as eight incremental steps or phase
states as indicated by equations (27) through (34). However, phase
shifters can be provided that afford other than eight steps of
phase shift. In FIG. 3, for example, there is illustrated a phase
shifter arrangement wherein a directional coupler 12a has its
directly connected port connected to an input port of another
directional coupler 12b. Any of the ports of coupler 12a can be
used for this configuration. By switchable choices of coupling
coefficients and reflection means, the phase shifter arrangement of
FIG. 3 can provide up to a total of 32 phase states of equal
increments, it being shown as a five-bit arrangement having a total
of five switchable reflection means, each having two states. This
arrangement can be extended to more than two couplers with
additional cascading to increase the number of phase states
possible. This technique can be applied to stripline, microstrip,
waveguide, coaxial line or any other transmission media.
As various changes could be made in the above construction without
departing from the scope of the invention, it is intended that all
matter contained in the above description or shown in the
accompanying drawings shall be interpreted as illustrative and not
in a limiting sense.
* * * * *