U.S. patent number 3,602,799 [Application Number 05/049,131] was granted by the patent office on 1971-08-31 for temperature stable constant current source.
This patent grant is currently assigned to Westinghouse Electric Corporation. Invention is credited to Francisco J. Guillen.
United States Patent |
3,602,799 |
Guillen |
August 31, 1971 |
TEMPERATURE STABLE CONSTANT CURRENT SOURCE
Abstract
An ultrastable high-speed constant DC current source for
generating a precise reference voltage in other apparatus such as a
high-speed analogue to digital converter. A continuous constant
load current is selectively switched between two current paths, one
of which comprises an output load across which said reference
voltage is developed. A high-speed digitally controlled driver
circuit including a differential amplifier configuration controls
the flow of the constant current selectively through one of two hot
carrier diodes. The diodes serve as electronic switches from the
constant current source which comprises an operational amplifier
connected in a feedback loop including a Darlington transistor
configuration and controlled by an externally applied input
reference voltage and an error signal developed by the flow of said
load current across a temperature compensated resistor.
Inventors: |
Guillen; Francisco J. (Ellicott
City, MD) |
Assignee: |
Westinghouse Electric
Corporation (Pittsburgh, PA)
|
Family
ID: |
21958202 |
Appl.
No.: |
05/049,131 |
Filed: |
June 24, 1970 |
Current U.S.
Class: |
323/283; 307/60;
323/351; 327/535 |
Current CPC
Class: |
G05F
3/225 (20130101); G05F 1/56 (20130101) |
Current International
Class: |
G05F
1/56 (20060101); G05F 3/22 (20060101); G05F
1/10 (20060101); G05F 3/08 (20060101); G05f
003/14 (); H02j 001/04 () |
Field of
Search: |
;323/1,4,8,9,22T,22SC,23,25 ;307/296,297,59,60 |
References Cited
[Referenced By]
U.S. Patent Documents
Other References
IBM Techn. Disclosure, Vol. 10; No. 7, Dec. 1967, Pg. 1045, 1046
Copy in 323/4.
|
Primary Examiner: Goldberg; Gerald
Claims
Having thus described the present invention with respect to its
preferred embodiment, I claim as my invention:
1. Apparatus for delivering a constant current to a load from a
source of supply voltage over a relatively wide temperature range
of operation, comprising in combination:
electronic switch means having a first and a second current switch
including circuit means coupling said first current switch to one
side of said load, said load having its opposite side coupled to
said source of supply voltage;
driver circuit means operated in accordance with at least one
control signal applied thereto and including an electronic circuit
coupled to said second current switch, said electronic circuit
being operated by said control signal to cause said second current
switch to become selectively nonconductive and conductive while
causing said first current switch to become conductive and
nonconductive and thereby switch substantially all of said constant
current respectively to said first or second current switch;
a reference voltage source providing an output of reference
voltage; and
a constant current source coupled in series between said electronic
switch means and said source of supply voltage and additionally
including circuit means coupled to said reference voltage source
and being responsive to said reference voltage to generate said
constant current of a predetermined magnitude in response to the
magnitude of said reference voltage, said constant current thereby
being adapted to flow continuously either through said first or
said second current switch.
2. The invention as defined by claim 1 wherein said first and
second current switch comprises a first and a second semiconductive
diode.
3. The invention as defined by claim 2 wherein said first and
second semiconductor diodes are comprised of Schottky barrier
diodes.
4. The invention as defined by claim 1 wherein said constant
current source comprises:
Dc amplifier means including a feedback control loop and having
first and second input terminals and an output terminal, being
operable to provide an output signal which is a function of the
signal difference between signals respectively applied to said
first and second input terminal;
first circuit means coupling said first input terminal to said
reference voltage;
second circuit means coupling said source of supply voltage to said
first input terminal;
first feedback means comprising at least one transistor having an
input electrode and a first and second output electrode, including
circuit means coupling said output terminal of said DC amplifier
means to said input electrode, said first output electrode to said
electronic switch means, and said second output terminal to said
second input terminal; and
second feedback means coupling said second output electrode of said
at least one transistor and said second input terminal of said DC
amplifier means to said source of supply voltage, whereby said
first and second feedback means defines said feedback control loop
whereby a voltage is produced across said second feedback means and
is applied to said second input terminal for causing a
substantially constant current flow between said switch means and
said second output electrode of said at least one transistor.
5. The invention as defined by claim 4 wherein said first feedback
means additionally comprises a second transistor coupled to said at
least one transistor in a Darlington circuit configuration.
6. The invention as defined by claim 5 wherein said first and
second current switch comprises a first and a second Schottky
barrier diode.
7. The invention as defined by claim 4 wherein said first feedback
means comprises a first and a second transistor each having an
input electrode and a first and second output electrode and
including circuit means commonly coupling said first output
electrodes together to said switch means, said input electrode of
said first transistor to said output terminal of said DC amplifier
means, said second output electrode of said first transistor to
said input electrode of said second transistor, and said second
output electrode of said second transistor to said third circuit
means providing thereby a Darlington circuit configuration.
8. The invention as defined by claim 7 wherein said switch means
comprises a pair of hot carrier diodes and wherein one of said pair
of diodes is directly connected between said load and said common
coupling of said first output electrodes of said first and second
transistor.
9. The invention as defined by claim 8 wherein said first and
second circuit means and said second feedback means each comprises
resistor means.
10. The invention as defined by claim 1 wherein said reference
voltage source comprises a DC voltage regulator circuit including
means for selectively adjusting the magnitude of said reference
voltage thereby controlling said substantially constant current
supplied to said load.
11. The invention as defined by claim 1 wherein said driver means
comprises a differential amplifier having a first and a second
input circuit adapted to be coupled respectively to and operated by
a binary input signal and the complement thereof and an output
circuit coupled to said second current switch of said switch means,
said output circuit being rendered selectively operative to control
current flow in said second current switch.
Description
BACKGROUND OF THE INVENTION
1. Field of the Invention
The present invention relates to a constant or otherwise regulated
electric current from a voltage source to a load. The magnitude of
the current is unaffected by changes in load or device parameters
as a result of temperature change or operating point.
2. Description of the Prior Art
Circuits for supplying a controlled magnitude of electrical current
flow from a voltage source to a load are well known to those
skilled in the art. One example of such a circuit is disclosed in
U.S. Pat. No. 3,114,872, issued to G. A. Allard. This reference
discloses a constant current source in which the magnitude of
current supplied by the source is responsive to temperature and
changes inversely with variations in temperature in the relative
amount required by one or more magnetic cores. While the output
current of such a circuit is not constant in a strict sense, the
combination of the regulating circuit and the voltage source may be
considered a constant current source in that the magnitude of the
current supplied is determined fully by the parameters of the
regulating circuit and is independent of the mode and the magnitude
of the voltage of the source. Such a constant current source finds
utility in supplying read and write half currents to a coincident
current magnetic core memory in which the hysteresis
characteristics of the magnetic cores are quite temperature
dependent.
Another type of circuit that supplies a constant current to a load
is a switching regulator such as disclosed in U.S. Pat. No.
3,350,628, issued to L. E. Gallaher, et al. According to that
invention, constant current is supplied to a load from a regulated
power supply of the type employing a transistor switch connected
between the source and the load. The switch is driven by a Schmitt
trigger which is responsive not only to a first feedback signal
derived from deviations from a desired value of a current supply to
the output filter, but also to a second feedback signal. The second
feedback signal is an alternating current signal derived from the
switching action of the transistor and applied in a sense to reduce
the hysteresis of the trigger circuit.
A regulated power supply circuit which discloses a feedback circuit
wherein the error signal is derived solely from deviations of the
output from a desired value is furthermore disclosed in U.S. Pat.
No. 3,233,915, issued to H. R. Ryerson, et al. The frequency of
switching varies in response to the direct current feedback signal
to facilitate rapid correction of the output current.
SUMMARY
While the above noted prior art operates in the manner intended,
the present invention is directed to a temperature stable constant
current source which constantly delivers a predetermined value of
current selectively to one of two signal paths by means of a pair
of hot carrier diodes which are operated in accordance with a
differential amplifier driver circuit controlled by means of a
digital input trigger signal. An output load is connected to one of
the switching diodes. The current source is connected in series
between a supply potential and the pair of switching diodes and
comprises a feedback amplifier in which a Darlington transistor
circuit is connected in a DC feedback loop to one DC amplifier
input. The DC feedback loop supplies a second input which is
applied to the DC amplifier and which is a function of the desired
constant current supplied to the pair of switching diodes. The
second input is developed across a temperature stabilized resistor
and any parameter variations in the circuit are effectively nulled
out by the Darlington feedback loop.
BRIEF DESCRIPTION OF THE DRAWING
The sole FIGURE is an electrical schematic diagram of the preferred
embodiment of the subject invention.
Description of the Preferred Embodiment
Referring now to the drawing, the circuit diagram shown is
comprised of four circuit portions, namely a current source 10, a
load current switch circuit 12, a load current switch driver
circuit 14 and a voltage reference source 16. An output load 18
which may be, for example an input device for a binary ladder
network of an analogue to digital converter for a digital signal
processor, is coupled to the switch circuit 12 and more
particularly to one semiconductor diode 20 of a pair of diodes 20
and 22 having their respective anode electrodes directly connected
at the circuit junction 24. The load 18 is connected from the
opposite or anode electrode of the diode 20 to a point of reference
potential illustrated as ground.
The semiconductor diodes, moreover, 20 and 22 are comprised of
high-speed switching diodes and are preferably hot carrier diodes
generically referred to as Schottky barrier diodes. These devices
are extremely fast acting due to their inherent low internal
electrode capacitance. Additionally these devices exhibit an
extremely low back bias leakage current characteristic, being in
the order of 2.times.10.sup.-.sup.9 amperes.
The anode electrode of the second switching diode 22 is connected
to the driver circuit 14 and more particularly to the collector
electrode of transistor 26 which is additionally coupled to a +12
volt power supply potential through a zener diode 28 and resistor
30. Transistor 26 forms one-half of a differential amplifier
circuit additionally including transistors 32, 34, 36 and
transistor 38. The collector of transistor 32 is returned to
ground. However, the input or base electrode of both transistors 26
and 32 are adapted to have a digital input trigger signal and its
complement respectively applied thereto by means of transistors 36
and 38. Zener diode 40 and resistor 41 couple the emitter of
transistor 36 to the base of transistor 26 while zener diode 42 and
resistor 43 couple the emitter of transistor 38 to the base of
transistor 32. The emitter electrodes of transistors 26 and 32 are
connected at a common junction 44 which is also connected to the
collector of transistor 34. With the exception of transistor 26 all
of the transistors included in the driver circuit 14 are powered by
means of a -18 volt supply potential coupled to their respective
emitter electrodes. Mutually opposite polarity trigger input
signals are simultaneously applied to the transistors 36 and 38 to
drive them mutually "on" and "off" and vice versa, causing
transistors 26 and 32 to also be rendered mutually "on" and "off."
Thus if transistor 36 is driven "on" by means of a signal applied
to its base, transistor 26 will also be driven "on;" however,
transistors 38 and 32 will be driven "off."
With respect to transistor 34, however, resistors 46, 48, and 50 as
well as the semiconductor diode 52 maintain transistor 34 in a
constantly conductive state. Thus when transistor 26 is turned
"on," the relatively low DC impedance path through transistors 26
and 34 provides a current path through resistor 30 and a negative
potential (.apprxeq. -8 volts) appears at the anode electrode of
diode 22 which back biases it into its nonconductive state. When
this condition occurs, a load current I.sub.L in the order of 20
milliamperes (10.sup.-.sup.3 amp.) as controlled by the current
source 10 flows through the diode 20 and into the load 18. On the
other hand, when transistor 26 is driven "off" by means of a
negative going trigger signal applied to transistor 36, a positive
potential appears at the anode electrode of the switching diode 22
forward biasing it into conduction whereupon the current I.sub.L as
determined by the current source 10 flows through the diode 22, the
resistors 30 and the zener diode 28. The zener diode 28 acts to
limit the magnitude of the voltage appearing at the anode of diode
22 to for example approximately (+6)-(I.sub.L R.sub.30) volts. This
volt potential appears at the cathode electrode of the switching
diode 20, thereby back biasing it into its nonconductive state.
It is immediately evident, therefore, that the driver circuit 14
under the control of two complementary trigger signals respectively
applied to the transistors 36 and 38 to act to cause a continuous
DC current I.sub.L to either flow through the load 18 or to divert
it through switching diode 22, the zener diode 28 and resistor 30.
Since the current I.sub.L flows continuously either through hot
carrier diode 20 or hot carrier diode 22, load current from the
current source 10 is not interrupted, L does not vary between zero
and the desired value. The problem of switching transients is
immediately eliminated thereby. Secondly, electronic switching of
the current to and from the load 18 occurs in the order 10.times.
10.sup.-.sup.9 seconds due to the extremely fast acting capability
of the hot carrier diodes 20 and 22. It should also be pointed out
that the back bias leakage current of the hot carrier diode is in
the order of 2.times. 10.sup.-.sup.9 amperes, so that substantially
100 percent of the 20 ma. current I.sub.L is flowing at any one
time through only one of the diodes 20 or 22, depending upon which
of the two is driven into conductivity by means of the driver
circuit 14.
The current I.sub.L is, as has been said before, a continuous DC
current and is typically in the order of 20 ma. This is provided by
the current source 10 which is comprised of a high gain DC
operational amplifier 54 coupled to a +12 volt and a -12 volt
supply potential and operated as a differential amplifier.
Amplifier 54 includes a pair of input terminals 56 and 58 as well
as an output terminal 60. An adjustable reference voltage is
applied thereto which is generated by the circuit 16 which is
comprised of a constant voltage source including an operational
amplifier 62 coupled into an emitter follower circuit including
transistor 64. The output or reference voltage is applied to
terminal 56 of the operational amplifier 54 by means of the
resistor 66 which is connected to the emitter of transistor 64. The
reference voltage magnitude is determined by the potentiometer 68
coupled between resistor 70 and 72. One end of resistor 72 is
coupled to a zener diode 74 which establishes a fixed voltage
thereacross depending upon its threshold voltage while one end of
resistor 70 is coupled back to the emitter of transistor 64 and
thereby provides a DC feedback path for the amplifier 62. The
voltage reference circuit 16 then is simply a voltage regulator
circuit and is shown for sake of illustration only, it being
understood that any other constant voltage source may be employed
when desired.
Returning now to a consideration of the constant current source 10,
which is the principal circuit portion of the subject invention,
input terminal 56 has an adjustable reference voltage applied
thereto as determined by the potentiometer 68 of the voltage
reference source 16. The other input terminal 58 of the operational
amplifier 54 is connected to circuit junction 76 to which is
connected to temperature stabilized resistor 78 and which has its
other end connected to circuit junction 80. A -12 volt supply
potential is connected to circuit junction 80. Additionally, a
resistor 82 is connected between circuit junction 80 and the first
input terminal 56 of the operational amplifier 54. Capacitor means
including the electrical capacitors 84 and 86 are coupled between
circuit junction 80 and ground to provide a filtering action for
the -12 volt supply potential.
A feedback loop comprising a Darlington transistor configuration
including transistors 88 and 90 is coupled between the amplifier
output terminal 60 and the second input terminal 58 which is also
common to the resistor 78 at circuit junction 76. The output of the
operational amplifier comprises the base input current I.sub.B for
the transistors 88 and 90 while the collector current (I.sub.C) is
the desired constant load current I.sub.L so that I.sub.L =I.sub.C.
This is accomplished by means of commonly connecting the collector
electrodes of transistors 88 and 90 to circuit junctions 24 of the
hot carrier diode switch circuit 12. The emitter current I.sub.E
flowing from transistor 90 is substantially equal to the collector
current I.sub.C plus the base current I.sub.B into the transistor
88. The voltage drop across resistor 78 caused by the emitter
current I.sub.E appears as an input signal at terminal 58 of the
operational amplifier 54. The operational amplifier 54 is
internally connected so that the output signal current I.sub.B
changes until the voltage at terminal 58 equals the reference
voltage applied to the other input terminal 56. The DArlington
configuration of transistors 88 and 90, moreover, provides an
overall current gain (I.sub.C =h.sub.FE I.sub.B) which is equal to
the product of the h.sub.FE of each transistor. Thus for example
where the DC h.sub.FE of both transistors is in the order of 50, a
current I.sub.B in the order of 8 microamperes will produce the
required collector current I.sub.C of 20 milliamps. Any changes
occurring in the gain characteristic of the transistors 88 and 90
is reflected as a voltage change across resistor 78; however, the
output I.sub.B of the operational amplifier 54, however, will be
driven in the proper direction to force the voltages at input
terminals 58 and 56 to be equal, thus bringing the value of the
load current I.sub.L to the required value.
The following Table I represents a tabulation of typical operating
results obtained for a temperature range between -50.degree. C. to
+100.degree. C. The output current was measured by monitoring the
voltage across a load resistor 18 having a resistance value of 170
ohms. A current change of less than 0.0013 percent was
observed.
Temperatures in .degree. C. Voltage across load resistor 18
__________________________________________________________________________
-50 -2.702 -40 -2.701 -30 -2.701 -20 -2.701 -10 -2.701 0 -2.701 +10
-2.700 +20 -2.700 +30 -2.699 +40 -2.700 +50 -2.699 +60 -2.699 +70
-2.699 +80 -2.699 +90 -2.699 +100 -2.699
---------------------------------------------------------------------------
TABLE I
in summation, therefore, the collector current flowing through the
Darlington configuration of transistors 88 and 90 powered by the
-12 volt supply potential applied to circuit junction 80 is
maintained at a constant value by means of the feedback amplifier
configuration including the operational amplifier 54. Moreover, the
collector current of the feedback transistors 88 and 90 is a
continuously flowing current which is switched by means of the
driver circuit 14 so that it either flows through the diode 20 and
into the load resistor 18 or is diverted into the diode 22 which
then flows through resistor 30 and the zener diode 28.
* * * * *