U.S. patent number 3,587,110 [Application Number 04/838,226] was granted by the patent office on 1971-06-22 for corporate-network printed antenna system.
This patent grant is currently assigned to RCA Corporation. Invention is credited to Oakley McDonald Woodward.
United States Patent |
3,587,110 |
Woodward |
June 22, 1971 |
CORPORATE-NETWORK PRINTED ANTENNA SYSTEM
Abstract
A corporate-network printed antenna system is described wherein
the feed lines are located in coplanar relationship with and in the
field of the antenna.
Inventors: |
Woodward; Oakley McDonald
(Princeton, NJ) |
Assignee: |
RCA Corporation (N/A)
|
Family
ID: |
25276587 |
Appl.
No.: |
04/838,226 |
Filed: |
July 1, 1969 |
Current U.S.
Class: |
343/813; 333/238;
343/814; 333/243; 343/905 |
Current CPC
Class: |
H01Q
9/065 (20130101); H01Q 21/062 (20130101) |
Current International
Class: |
H01Q
9/04 (20060101); H01Q 9/06 (20060101); H01Q
21/06 (20060101); H01g 021/06 (); H01q 021/12 ();
H01p 003/08 () |
Field of
Search: |
;333/84,84M
;343/810--816,835,844,905 |
References Cited
[Referenced By]
U.S. Patent Documents
Other References
"Microwave Printed Circuits -- A Historical Survey," (Barrett), in
IRE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, Volume NTT-3,
Number 2 March 1955, TK7800I23, pages 1, 4--5, 8, and title
page.
|
Primary Examiner: Saalbach; Herman Karl
Assistant Examiner: Nussbaum; Marvin
Claims
What I claim is:
1. An antenna system comprising:
a broad sheet of dielectric material,
a plurality of planar dipole elements with a first half portion of
each dipole element fixed to one of the broad surfaces of said
sheet and with the second half portion of each dipole element fixed
to the opposite broad surface of said sheet,
feed means including two narrow conductive strips fixed in opposed
relation on said broad surfaces of said dielectric sheet and
extending from a common feed point to said plurality of dipole
elements with a length between the common feed point and one of
said dipole elements being the same as that from the common feed
point to any of the other dipole elements, said dipole elements
being arranged on said sheet so that said feed means extends
horizontally and vertically from said common feed point to said
elements, said horizontally extending feed means at the junction
with said vertically extending feed means having a notch located
thereat in a manner so that currents will not be introduced into
the feed means which are equal in magnitude and flow in the same
direction.
2. An antenna system comprising:
a broad sheet of dielectric material,
a plurality of planar dipole elements with a first half portion of
each dipole element fixed to one of the broad surfaces of said
sheet and with the second half portion of each dipole element fixed
to the opposite broad surface of said sheet,
feed means including two narrow conductive strips fixed in opposed
relation on said broad surfaces of said dielectric sheet and
extending from a common feed point to said plurality of dipole
elements with the length between the common feed point and one of
said dipole elements being the same as that from the common feed
point to any of the other dipole elements, said feed means being
unbalanced for a given length from said common feed point and
balanced from the end of said given length remote from said common
feed point to said dipole elements.
3. The combination as claimed in claim 2, wherein one of said
conductive strips forming said given length of said feed means is
of constant width and the second conductive strip forming said
given length of said feed means is tapered in width to provide said
unbalance, the common feed point being located at the narrowest end
of said given length.
Description
The invention herein described was made in the course of or under a
contract or subcontract thereunder with the Department of the
Army.
This invention relates to antenna systems and more particularly to
an array of printed antennas energized from a corporate feed
network.
Microwave antenna array systems which are lightweight, rugged,
low-cost and compact find wide use in both military and commercial
applications. Printed antenna systems which are generally made of a
plurality of dipoles formed on the surface of a low dielectric
circuit board provide these desirable features. The feed for the
plurality of dipoles is either provided by a plurality of feed
lines on both sides of the insulating board or in a different plane
from that of the dipoles. The dipoles are usually arranged in rows
with the dipoles in each row spaced approximately one-half
wavelength apart with the feed lines and dipoles arranged in
transposed relation so that the dipoles are fed in equal phase.
This type of system is inherently narrow in bandwidth.
It is therefore an object of the present invention to provide an
improved printed antenna system which is broadband.
Briefly, this and other objects of the present invention are
provided by an improved, lightweight, compact printed antenna
system wherein a plurality of dipoles arranged in adjacent pairs
are secured to the broad planar surfaces of a sheet of insulative
material. Pairs of adjacent dipoles are connected in parallel
through feeder lines disposed on the insulating material. The
center point of the feeder lines is connected by another feeder
line to another double group. Likewise, this is repeated whereby
all of the dipoles are fed with feeder lines of equal length.
Additional features and objects of the invention will be more
clearly apparent as the invention is described in connection with
the drawing in which:
FIG. 1 illustrates the general layout of an antenna system in
accordance with an embodiment of the present invention,
FIG. 2 illustrates one broad surface of the sheet of insulative
material having a portion of the feed line and dipoles thereon,
FIG. 3 illustrates the opposite broad surface of the sheet of
insulative material having a portion of the feed lines and dipoles
thereon,
FIG. 4 is a cross-sectional view of a portion of the antenna in
accordance with an embodiment of the present invention,
FIG. 5 is a cross-sectional view of feed points to the antenna
system, and
FIG. 6 is a circuit diagram illustrating the impedance matching
network.
Referring to FIGS. 1, 2 and 3, there is shown the general layout of
the fanlike center fed dipoles 11 and feed line 13 of a printed
circuit panel antenna system 10 in accordance with a preferred
embodiment of the present invention. The fanlike dipoles 11 and the
feed lines 13 are placed on insulative sheet 15 of a one
thirty-second inch thick, low dielectric material such as low loss
polyolifin dielectric having a dielectric constant of 2.32. A
half-portion 12 of each dipole element 11 is on one surface of the
sheet 15, and the remaining half-portion 14 of each dipole element
11 is on the opposite surface of the sheet 15. That side of the
sheet 15 having half-portions 14 thereon is shown in FIG. 1, with
the half-portions 12 on the opposite side of sheet 15 not visible
in FIG. 1 shown as dotted lines. As shown in FIGS. 2 and 3, the
feed lines 13 are made up of a transmission line of the character
having one conductor 17 on one surface and a second conductor 19 on
the opposite surface. Conductors 17 on one surface, illustrated in
FIG. 2, are coupled to the half-portion 12 of each dipole element
11 on that one surface, and conductors 19 on the opposite surface,
illustrated in FIG. 3, are coupled to the half-portion 14 of each
dipole 11 on the opposite surface.
The slight offset due to the thickness of the insulative sheet
between the two halves of each of the dipoles is electrically
insignificant and eliminates the need for pass-through connections
which would be required if both halves of the dipoles were on the
same side of the sheet.
For purposes of description, FIG. 1 is described in detail, bearing
in mind however, that in actual practice there are feed lines on
both sides of the dielectric sheet 15 with the feed line on one
surface coupled to the half-portion of the dipole element on that
one surface and the feed line on the opposite surface of the
insulative sheets coupled to the half-portion of the dipole element
on the opposite surface. If unidirectivity is desired, this printed
circuit panel antenna system 10 having half of the dipole on one
side and half of the dipole on the opposite side may be foam
supported in a shallow metal pan with the metal pan acting as a
reflector for the dipoles. FIG. 4 shows a cross-sectional view of a
portion of such an arrangement. The transmission line conductors 17
and 19 on either side of a dielectric sheet 15 are spaced from a
reflector 23 by means of foam section 21. To provide weather
proofing and mechanical protection of the printed circuit panel
network, another layer of foam 25 and a second dielectric sheet 27
may be provided on the opposite surface of sheet 15.
As shown in FIG. 5, a coaxial line 28 may be coupled near the
center of the printed circuit panel antenna system 10. The outer
conductor 29 of the coaxial line 28 is coupled to conductor 59 at
the one or bottom surface of the printed circuit dielectric sheet
panel 15 at points 35 and 36 and is also coupled to the shallow
metal pan or ground plane reflector 23. The center conductor 31 of
the coaxial line 28 is fed through the insulative sheet 15 to the
conductor 57 of the feed lines at the upper surface of the
insulative sheet at point 31 as shown in FIGS. 2 and 5. At point B
conductor 57 is connected to conductor 17 and conductor 59 is
connected to conductor 19. The individual dipole radiators 11 are
made in the form of fans having a flare angle of 90.degree. in
order to provide greater impedance bandwidth.
The dipoles are fed from a corporate network of balanced
transmission line sections branching out from points 37 and 39 in
FIG. 1. The conductors 17, 19 which make up the feed lines from
points 37 and 39 to the dipoles on opposite sides of the insulative
sheet are of equal width to provide balanced lines from points
37,39 to the dipoles 11. The width of the conductor 17 from point B
to point 37, and from point B to point 39 on the surface of the
insulative sheet 15 changes so that a 50 ohm balanced impedance at
the points 37,39 is transformed to 100 ohm unbalanced impedance at
point B (see FIG. 2). The width of the line on the opposite surface
of the panel 15 does not change from point B to points 37 or 39
(see FIG. 3). The two halves of the complete array, when joined
together, as in the example, give a 50 ohm impedance. The impedance
of the line at the point of the coaxial input connection across
points 31 and 35,36 is also 50 ohms to match the coaxial line
impedance.
The impedance in the line from point B to point 31 is matched by a
section of microstrip line where, as shown in FIGS. 2 and 3, the
conductor 57 shown in FIG. 2 is considerably narrower than that of
59 illustrated in FIG. 3 to make a microstrip transmission line. A
vernier impedance matching device 58 is formed by a small chip of
dielectric material with a conductor such as copper on the upper
surface. By changing the length of the chip 58 and its position
along the microstrip line, an impedance match between the coaxial
line 28 across points 31 and 35, 36 and point 35,36 is provided
with low VSWR at the given frequency. Once the optimum chip
position is located, one may simply glue the chip to the surface of
the conductor 57.
From points 37 or 39 on the feed lines to the dipoles 11, the feed
lines on the opposite ends of the array are identical and follow
from a basic building block as described further in connection with
FIG. 6. Referring now to FIG. 6, each of four antenna dipole
elements 11 has a load impedance Z.sub.A, for example. Lines 43 and
44 each represent that section of line in the array directly
connected to a dipole 11. Thus, it is to be understood that line 43
terminates at a dipole 11 including half-portions 12 and 14.
Likewise, line 44 terminates at a second dipole 11 including
half-portions 12 and 14. Again, it is to be remembered that each
line 43,44 represents a conductor on one side of the sheet 15 and a
matching conductor on the opposite side thereof. The configuration
of lines 43 and 44 are each arranged to provide a characteristic
impedance of Z.sub.1, for example. The lines 43 and 44 are
identical with both being one-half wavelength long. The impedance
at the junction point 45 is Z.sub.A/2 independent of the value of
the characteristic impedance Z.sub.1 of lines 43 and 44. A line 47
having a configuration such as to provide a characteristic
impedance of Z.sub.2, for example, is coupled perpendicular to the
lines 43 and 44 at point 45 to form a T with the lines and extends
a length one-quarter wavelength long (.lambda./4) at approximately
the mean operating frequency of the antenna system. The impedance
at point 49 is equal to (Z.sub.2).sup.2 /(Z.sub.A/2 ) or
2(Z.sub.2).sup. 2 /Z.sub.A. A second line 51 one-quarter wavelength
long at approximately the mean operating frequency of the antenna
system connected to the free end of line 47 at point 49 will give
an impedance at point 53 (.lambda./4 wavelength from point 49) of
Z.sub.3 .sup.2 (Z.sub.3 being the characteristic impedance of line
51) divided by the impedance at point 49 resulting in (Z.sub.A
Z.sub.3 .sup.2) (2Z.sub.2 .sup.2). Since the lower half 54 of the
circuit is identical to that of the upper half 41, the impedance at
the junction 53 is halved and is equal to (Z.sub.A Z.sub.3
.sup.2)/(4Z .sub.2 .sup.2). Now if the characteristic impedance
Z.sub.3 of the line 51 is equal to twice that of the characteristic
impedance or Z.sub.2 of line 47, then the impedance of point 53 is
equal to that of Z.sub.A or the load. Thus if there is no coupling
between the antenna elements, the input impedance to the corporate
network feed is equal to the individual antenna load impedance. The
characteristic impedance Z.sub.1 or Z.sub. 2 may have any chosen
value. The only requirement is that Z.sub.3 be twice Z.sub.2. In
practice, it is desirable to choose the values of Z.sub.) and
Z.sub.2 to minimize the standing waves throughout the network.
Referring now to FIG. 1, the four element array of FIG. 6 may be
any one of the four element arrays such as the four element array
61 in FIG. 1. The antenna loads provided by dipoles 11 are, for
example, 50 ohms. The feed line section 62 between the dipoles 11
and the common point 63 of the array, is for example, half a
wavelength long with the characteristic impedance Z.sub.1 of the
line being 50 ohms. The characteristic impedance Z.sub.2 of the
line 66 between the junction at point 63 and point 64 is 50 ohms.
The length of the line 66 between point 63 and point 64 is
one-quarter of a wavelength. Following with the arrangement
described in FIG. 6, the length of the line 67 between point 64 and
common point 65 which is the junction point with the lower half of
the circuit is likewise one-quarter wavelength long. The width of
the conductor 67 is narrower than that of line 66, so as to provide
a characteristic impedance of 100 ohms. Considering the four
element array 61 in FIG. 1 and FIG. 6 as one load, the dipole array
61 is joined with a similar corporate network to three other
similar four element arrays, 71, 72 and 73 to give a 16 dipole
array which 16 dipole array has a total input impedance of (in this
example) 50 ohms. Impedance match is provided by the .lambda./4
stub at the junction and the 2 to 1 ratio in the 2 impedance of the
two line section. In the present application, this process is
repeated once more, where four 16 dipole arrays 75, 76, 77 and 78
are combined resulting in a 64 dipole array fed at point 37 of FIG.
2. Hence if the antenna impedance is 50 ohms, the impedance at
point 37 is also 50 ohms and the greatest theoretical VSWR
throughout the system is about two-to-one. Repeating the structure
described at point 39 on the other end of the printed circuit array
provides an array when combined at point B, of 128 dipole elements
impedance-matched at points 37 or 39 at 50 ohms. The result is also
feed lines of equal length to all of the dipoles.
The corporate network in the present array is located in the same
plane as that of the dipole array. One-quarter wavelength notches
81 as shown in FIG. 1 are cut at the T-junctions where horizontal
lines branch into vertical lines. This notch effectively breaks the
currents which may be induced on the two conductor lines by the
radiating dipoles and which are equal in magnitude and flow in the
same direction. By breaking this current flow in the same
direction, the push-push mode which would result in undesired
transmission line radiation is prevented. The notch width is made
relatively small compared to the line width, so that the
characteristic impedance of the line operating in the push-pull
mode would not be greatly changed.
* * * * *