U.S. patent application number 17/143379 was filed with the patent office on 2022-07-07 for method and device for detecting discontinuous transmission (dtx) assisted by noise estimation.
The applicant listed for this patent is Hong Kong Applied Science and Technology Research Institute Co., Ltd. Invention is credited to Man Wai Kwan, Xiangyu Liu, Yaming Luo, Kong Chau Tsang, Ying Lun Tsui, Yunxiang Yao.
Application Number | 20220217714 17/143379 |
Document ID | / |
Family ID | |
Filed Date | 2022-07-07 |
United States Patent
Application |
20220217714 |
Kind Code |
A1 |
Luo; Yaming ; et
al. |
July 7, 2022 |
Method and Device for Detecting Discontinuous Transmission (DTX)
Assisted by Noise Estimation
Abstract
Described is a method of processing a signal received at an
uplink control information (UCI) receiver in a wireless
communication system. The method comprises processing a signal
received on an uplink (UL) at said UCI receiver to transform said
received signal into a likelihood calculation of possible
transmitted codewords (.theta..sub.1 . . . .theta.i . . .
.theta..sub.N) and determining a maximum magnitude .theta..sub.max
value from said likelihood calculation. The method includes
comparing said maximum magnitude .theta..sub.max value to a
selected, calculated or predetermined scaled threshold S.tau. where
.tau. is a threshold and S is a scaling factor for the threshold
.tau.. The comparison step is such that, where
|.theta..sub.max|.sup.2>S.tau., the method comprises determining
that the signal received comprises a linear block encoded signal.
In the method, prior to said comparison step, the scaling factor S
is selected from a plurality of scaling factor options. One scaling
factor option (i) is a scaling factor S.sub.RE derived from a
combination of estimated noise and/or signal power at an output of
a resource element (RE) demapper module and an estimated channel
response from/before an equalizer module of said UCI receiver. The
options also include using a combination of S.sub.RE and a suitable
scaling factor derived excluding option (i).
Inventors: |
Luo; Yaming; (Kwan Tong,
HK) ; Yao; Yunxiang; (Sai Kung, HK) ; Kwan;
Man Wai; (Ma On Shan, HK) ; Liu; Xiangyu;
(Shenzhen City, CN) ; Tsui; Ying Lun; (Ma On Shan,
HK) ; Tsang; Kong Chau; (Kowloon, HK) |
|
Applicant: |
Name |
City |
State |
Country |
Type |
Hong Kong Applied Science and Technology Research Institute Co.,
Ltd |
Shatin |
|
HK |
|
|
Appl. No.: |
17/143379 |
Filed: |
January 7, 2021 |
International
Class: |
H04W 72/04 20060101
H04W072/04; H04W 76/28 20060101 H04W076/28; H04B 1/06 20060101
H04B001/06; H04L 25/02 20060101 H04L025/02 |
Claims
1. A method of processing a signal received at an uplink control
information (UCI) receiver in a wireless communication system, the
method comprising: processing a signal received on an uplink (UL)
at said UCI receiver to transform said received signal into a
likelihood calculation of possible transmitted codewords
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N); determining a
maximum magnitude .theta..sub.max value from said likelihood
calculation of possible transmitted codewords (.theta..sub.1 . . .
.theta.i . . . .theta..sub.N); and comparing said maximum magnitude
.theta..sub.max value to a selected, calculated or predetermined
scaled threshold S.tau. where .tau. is a threshold and S is a
scaling factor for the threshold .tau. and said scaled threshold
S.tau. is a product of the threshold .tau. and the scaling factor
S, the comparison being such that, where
|.theta..sub.max|.sup.2>S.tau., the method comprises determining
that the signal received on the UL at said UCI receiver comprises a
linear block encoded signal; wherein, prior to said comparison
step, the scaling factor S is selected from a plurality of scaling
factor options.
2. The method of claim 1, wherein, where
|.theta..sub.max|.sup.2.ltoreq.S.tau., the method comprises
outputting a discontinuous transmission (DTX) signal.
3. The method of claim 1, wherein the scaling factor options
comprise: (i) S=S.sub.RE where S.sub.RE is derived from a
combination of estimated noise and/or signal power at an output of
a resource element (RE) demapper module of the UCI receiver and an
estimated channel response from or before an equalizer module of
said UCI receiver; (ii) S=S.sub.OTHER where S.sub.OTHER is any
method of deriving a suitable scaling factor excluding option (i);
and (iii) S=S.sub.COMB where S.sub.COMB is derived from a
combination of S.sub.RE and S.sub.OTHER.
4. The method of claim 3, wherein S.sub.COMB=f(S.sub.OTHER,
S.sub.RE)=.alpha.(S.sub.OTHER).sup..lamda.(S.sub.RE).sup.1-.lamda.,
where .lamda. comprises a weighting value less than or equal to 1
and .alpha. comprises a combination coefficient.
5. The method of claim 4, wherein the combination coefficient
.alpha. is derived from a payload bit length.
6. The method of claim 3, wherein S.sub.OTHER=S.sub.HAD where
S.sub.HAD is derived from a multi-dimensional DFT (.theta..sub.1 .
. . .theta.i . . . .theta..sub.N) of the signal received on the UL
at said UCI receiver.
7. The method of claim 6, wherein S.sub.COMB=f(S.sub.HAD,
S.sub.RE)=.alpha.(S.sub.HAD).sup..lamda.(S.sub.RE).sup.1-.lamda.,
where .lamda. comprises a weighting value less than or equal to
1.
8. The method of claim 7, wherein .lamda.>0.5. and is preferably
equal to 0.667, and .alpha.=1.
9. The method of claim 3, wherein the step of selecting the scaling
factor S from the plurality of scaling factor options comprises:
selecting option (i) if the accuracy of the estimated noise and/or
signal power at the output of the RE demapper module is at an
acceptable or better level, otherwise; selecting option (iii) if
the number of UCI payload bits is large, otherwise; selecting
option (ii).
10. The method of claim 3, wherein the step of selecting the
scaling factor S from the plurality of scaling factor options
comprises: select option (ii) if a code mask is not applied at an
encoder module of the UCI receiver, otherwise; select option (iii)
if a code mask is applied.
11. The method of claim 3, wherein the step of selecting the
scaling factor S from the plurality of scaling factor options
comprises: select option (ii) if a payload bit length is smaller
than or equal to a maximum unmask bit payload length, otherwise;
select option (iii) if the payload bit length is larger than the
maximum unmask bit payload length.
12. The method of claim 1, wherein S=S.sub.RE and S.sub.RE is
derived from: S RE = r .times. i .times. k .times. g r , l , k g r
, l , k '' .sigma. r 2 ##EQU00004## where .sigma..sub.r.sup.2 is
the estimated noise variance or signal power corresponding to the
r-th receiver antenna obtained at the output of the RE demapper
module; g.sub.r,l,k is the estimated channel response from the
equalizer module with r comprising a receiver antenna index value,
l comprising a time domain index value and k comprising a frequency
domain index value.
13. The method of claim 1, wherein the step of selecting the
scaling factor S is omitted such that the comparison step comprises
comparing said .theta..sub.max value to the scaled threshold S.tau.
such that, where |.theta..sub.max|.sup.2>S.tau., the method
comprises determining that the signal received on the UL at said
UCI receiver comprises a linear block encoded signal.
14. The method of claim 1, wherein the likelihood calculation of
possible transmitted codewords (.theta..sub.1 . . . .theta.i . . .
.theta..sub.N) comprises a multi-dimensional discrete Fourier
Transform (DFT) (.theta..sub.1 . . . .theta.i . . . .theta..sub.N)
of said signal received on the UL at said UCI receiver and the
maximum magnitude .theta..sub.max value is derived from a plurality
of real numbers comprising said multi-dimensional DFT.
15. The method of claim 14, wherein the multi-dimensional DFT
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N) comprises a
Hadamard transform of the signal received on the UL at said UCI
receiver.
16. The method of claim 1, wherein the method is utilized to
determine that the signal received on the UL at said UCI receiver
comprises a small block encoded signal in a long-term evolution
(LTE) communication system.
17. The method of claim 16, wherein the method is utilized to
determine DTX in a small block encoded signal comprising a new
radio (NR) Physical Uplink Control Channel (PUCCH) format such as
PUCCH format 2, PUCCH format 3, or PUCCH format 4.
18. The method of claim 1, wherein the linear block code comprises
Reed-Muller (RM) code or RM-based super code.
19. An uplink control information (UCI) receiver in a wireless
communication system, the receiver comprising: a memory storing
machine-readable instructions; and a processor for executing the
machine-readable instructions such that, when the processor
executes the machine-readable instructions, it configures the
receiver to: process a signal received on an uplink (UL) at said
UCI receiver to transform said received signal into a likelihood
calculation of possible transmitted codewords (.theta..sub.1 . . .
.theta.i . . . .theta..sub.N); determine a maximum magnitude
.theta..sub.max value from said likelihood calculation of possible
transmitted codewords (.theta..sub.1 . . . .theta.i . . .
.theta..sub.N); and compare said maximum magnitude .theta..sub.max
value to a selected, calculated or predetermined scaled threshold
S.tau. where .tau. is a threshold and S is a scaling factor for the
threshold .tau. and said scaled threshold S.tau. is a product of
the threshold .tau. and the scaling factor S, the comparison being
such that, where |.theta..sub.max|.sup.2>S.tau., the method
comprises determining that the signal received on the UL at said
UCI receiver comprises a linear block encoded signal; wherein,
prior to said comparison step, the scaling factor S is selected
from a plurality of scaling factor options.
20. A method of processing a signal received at an uplink control
information (UCI) receiver in a wireless communication system, the
method comprising: processing a signal received on an uplink (UL)
at said UCI receiver to transform said received signal into a
likelihood calculation of possible transmitted codewords
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N); determining a
maximum magnitude .theta..sub.max value from said likelihood
calculation of possible transmitted codewords (.theta..sub.1 . . .
.theta.i . . . .theta..sub.N); and comparing said .theta..sub.max
value to a selected, calculated or predetermined scaled threshold
S.tau. where .tau. is a threshold and S is a scaling factor for the
threshold .tau. and said scaled threshold S.tau. is a product of
the threshold .tau. and the scaling factor S, and where the scaling
factor is S derived from a combination of estimated noise and/or
signal power at an output of a resource element (RE) demapper
module of the UCI receiver and an estimated channel response from
an equalizer module of said UCI receiver, the comparison being such
that, where |.theta..sub.max|.sup.2>S.tau., the method comprises
determining that the signal received on the UL at said UCI receiver
comprises a linear block encoded signal.
Description
FIELD OF THE INVENTION
[0001] The invention relates to a method and device for detecting
Discontinuous Transmission (DTX) assisted by noise estimation. The
invention relates particularly, but not exclusively, to an improved
method and device for determining that a signal received on an
uplink (UL) at an Uplink Control information (UCI) receiver in a
wireless communications system comprises a linear block encoded
signal. The invention also relates to a method and device for
improved detection of DTX on a UL at a UCI receiver particularly
for small block encoded signals.
BACKGROUND OF THE INVENTION
[0002] In long-term evolution (LTE) communications systems, in a
downlink (DL), a data payload is carried by transport blocks which
are encoded into codewords which are sent over a DL physical data
channel called the Physical Downlink Shared Channel (PDSCH). The
scheduling information of the PDSCH codeword(s), including its
resource allocation in the subframe and its modulation and coding
scheme, is included in the physical control channel, called the
Physical Downlink Control Channel (PDCCH). Generally, the receiving
user equipment (UE) decodes the messages in PDCCH and, where it
finds that a PDSCH has been assigned to it, it decodes the PDSCH
codeword(s) according to the scheduling information decoded from
the PDCCH. In other words, correctly decoding PDCCH is a
prerequisite for properly decoding PDSCH.
[0003] In order to prevent the loss of transport blocks, LTE has
adopted the Hybrid Automatic Repeat Request (HARQ) scheme. In the
physical layer of Evolved UMTS Terrestrial Radio Access Network
(E-UTRA), HARQ is implemented both in the UL and the DL. The
acknowledgement message in E-UTRA is denoted as HARQ-ACK.
[0004] HARQ-ACK may be transmitted by the UE in response to certain
PDSCH transmissions and includes one or several acknowledgements,
either positive (ACK) or negative (NACK) in response to transport
blocks transmitted in the DL. HARQ-ACK may be transmitted on one of
the physical channels Physical Uplink Control Channel (PUCCH) or
Physical Uplink Shared Channel (PUSCH).
[0005] But if the UE is not able to correctly decode the PDCCH, it
cannot correctly decode the PDSCH, and may even not know that it
needs to send the HARQ feedback. This is called Discontinuous
Transmission (DTX).
[0006] If the eNodeB (base station (BS)) detects ACK instead of
DTX, a so called ACK false detection, the eNodeB will erroneously
consider the corresponding DL transport block as correctly
received. Since the transport block has not been correctly received
by the UE, corresponding data will not be passed to the Medium
Access Control (MAC) layer and from the MAC layer to the Radio Link
Control (RLC) layer. Data will hence be missing in the RLC layer.
This will cause ARQ retransmissions in the RLC layer which
introduce delay and possibly large retransmissions which is very
undesirable. Also, if a NACK is detected erroneously that in
reality is DTX, the eNodeB will retransmit the packet in such a way
that the UE will not be capable of decoding it.
[0007] As already indicated, a problem arises when the UE is not
aware of the presence of the PDSCH assigned to it if it fails to
decode the PDCCH successfully. In this case the UE will not
generate ACK/NACK information. This situation has been well
recognized and the UE response in such case is DTX, that is,
neither an ACK nor a NACK signal is transmitted to the eNodeB.
Since the eNodeB has no prior knowledge of whether the UE has
failed to detect the PDCCH, it expects or deems, that the symbols
of the predetermined positions are ACK/NACK symbols and extracts
them for the ACK/NACK decoder to decode. If the eNodeB disregards
the possibility of DTX, either an ACK or NACK message will be
returned by the ACK/NACK decoder to a higher layer upon the
decoding of the extracted symbols, which are, in fact. conveying no
information. In general, both ACK and NACK messages are equally
likely to be returned.
[0008] The consequence of wrongly detecting a DTX as an ACK is more
adverse to the system performance than wrongly detecting a DTX into
a NACK.
[0009] Similarly, in 5G (or new radio (NR)) wireless communication
systems, a message feedback scheme is also used for re-transmission
control. ACK or NACK (AN) signals are used to indicate whether the
signal is received successfully or not by the UE and whether the BS
needs to retransmit the data. If the UE misses a DL control signal,
the UE may encounter DTX in DL and the UE will not send any message
back to the BS. However, the BS needs to detect one of three
possible feedback states, i.e. ACK, NACK or DTX, for rearranging a
next transmission to the UE.
[0010] FIG. 1 illustrates a method by which UL signals from the UE
to the BS control transmission of payload control data and payload
data on the DL from the BS to the UE. In the example of FIG. 1, it
can be seen that, in response to a first "DL control for payload
allocation #1" message from the BS to the UE, the UE, in this
instance, responds with a UCI "NACK" message. The NACK message is
received by the UCI receiver at the BS and, as a consequence, the
BS is configured to retransmit to the UE the first "DL control for
payload allocation #1" message and its associated first "DL payload
data #1" message. In this example, the UE then returns a UCI "ACK"
message to the UCI receiver in response to the retransmitted
control signal message and, as a consequence, the BS is configured
to then transmit to the UE the second "DL control for payload
allocation #2" message and its associated second "DL payload data
#2" message (not shown in FIG. 1). FIG. 1 therefore illustrates how
data is retransmitted by the BS to the UE when the UE indicates
that is has not successfully received a DL data control
message.
[0011] In contrast, FIG. 2 illustrates what may happen when the UE
misses a DL data control message. In this example, the UE has
missed the first "DL control for payload allocation #1" message and
consequently sends no ACK/NACK message back to the BS in response.
This scenario represents a DTX state. The UCI receiver at the BS
only receives noise but processes this as though it comprises a UL
UCI signal with the result that, in this example, the UCI falsely
detects or determines receipt of an ACK message from the UE and
thus outputs a false ACK message. This causes the BS to commence a
new control and payload data transmission in response to the false
ACK message, e.g. "DL control for payload allocation #2", etc.
[0012] For 5G UCI, 3GPP Technical Specification 38.212 requires the
support of two types of channel codes, namely polar code and small
block code as illustrated respectively by FIGS. 3 and 4. Polar code
relates to the situation where the number of payload bits is
greater than 11. Small block code relates to the situation where
the number of payload bits is equal to or less than 11.
[0013] As shown in FIG. 3, in a conventional polar code-based
receiver, a cyclic redundancy check (CRC) may assist in detecting
whether or not DTX occurs. The output from the polar code decoder
comprises UCI bits but the CRC check function (module) enables the
polar code-based receiver to distinguish between DTX on the one
hand and UCI bits indicative of ACK or NACK on the other hand.
[0014] In FIG. 4 which shows a conventional small block code-based
receiver where a CRC function is not available, incorrect detection
of the ACK, NACK, or DTX signals leads to a waste of resources for
retransmission and/or a loss of data packets. In the conventional
small block code-based receiver where CRC is not available, ACK and
NACK each issue with about 50% probability where the UE misses a DL
control message and transmits nothing to the UE such that the BS
receives only noise. In the small block code-based receiver, the
output from the small block code decoder are assumed to be UCI bits
leading to possible false ACK or false NACK outcomes. In other
word, there is no means for distinguishing between DTX on the one
hand and UCI bits indicative of ACK or NACK on the other hand.
[0015] In the conventional small block code-based UCI receiver of
FIG. 4, the resource element (RE) demapper output will be treated
by an equalizer module to generate an equalized signal. The
equalized signal will then be treated by a demodulation module to
generate a demodulated soft bit sequence (SEQ). The demodulated
soft bit SEQ will be handled by a descrambling module to create a
descrambled soft bit SEQ. The descrambled soft bit SEQ will then be
handled by a rate de-matching module to create a de-matched soft
bit SEQ. The de-matched soft bit SEQ will be decoded through a
decoder for small block code module to generate UCI bits
(ACK/NACK). The soft bits comprise real signal values which differ
from hard bits which are resolved to binary values.
[0016] As already explained with respect to FIGS. 1 and 2, if a UE
loses a DL control signal, the UE will not send UCI ACK/NACK
feedback, i.e. a DTX state will occur. The BS treats DTX as an
unsuccessful DL transmission. Re-transmission is required if and
when DTX occurs. But if the DTX is falsely detected as ACK,
re-transmission will not be performed.
[0017] CN105262568 relates to ACK/NACK and DTX detection in a
wireless communication system where the DTX status threshold is
calculated based on the statistics of signal-to-noise ratio (SNR).
However, it can be challenging to obtain accurate noise
estimations.
[0018] CN102740316 relates to a method for detecting an uplink DTX
state. The method comprises receiving data information from uplink
user equipment of the current cell; calculating a confidence value
corresponding to the data information, wherein the confidence value
is used for reflecting the accuracy of data information decoding
carried out by a receiving terminal; comparing the confidence value
with a preset DTX judgment threshold; and determining whether the
uplink user equipment is in the DTX state or not according to a
comparative result. Here, the preset DTX judgment threshold must
change for different channel conditions and thus determination of
the DTX judgment threshold requires considerable computational
effort.
[0019] U.S. Pat. No. 8,315,185 relates to ACK/NACK detection in an
LTE wireless communication system. The ACK/NACK detector has a soft
decoder and decision-maker. A threshold value is used to determine
whether the transmitted signal from the UE contains an ACK/NACK
transmission when the threshold value is met. If the threshold
value is not met, the transmission is determined to be DTX. The
threshold value is based on a power estimate of soft data bits.
[0020] U.S. Pat. No. 8,891,591 discloses a receiver circuit which
includes an estimation unit configured to estimate a noise power of
a transmission channel, a calculation unit configured to calculate
a decision variable based on the noise power, and a decision unit
configured to make a ternary decision based on the decision
variable.
[0021] What is desired is a method of improving detection of DTX on
a UL at a UCI receiver and/or a method of determining that a signal
received on a UL at a UCI receiver comprises a linear block encoded
signal. What is also desired is a method for detecting
acknowledgment (ACK), negative acknowledgment (NACK) and
discontinuous transmission (DTX) signals more accurately in
wireless communication systems.
Objects of the Invention
[0022] An object of the invention is to mitigate or obviate to some
degree one or more problems associated with known methods of
determining that signals received on a UL at a UCI receiver
comprise linear block encoded signals.
[0023] The above object is met by the combination of features of
the main claims; the sub-claims disclose further advantageous
embodiments of the invention.
[0024] Another object of the invention is to provide an improved
method of detecting DTX on a UL at a UCI receiver especially for
small block encoded signals.
[0025] Another object of the invention is to provide an improved
UCI receiver and/or UCI decoder.
[0026] One skilled in the art will derive from the following
description other objects of the invention. Therefore, the
foregoing statements of object are not exhaustive and serve merely
to illustrate some of the many objects of the present
invention.
SUMMARY OF THE INVENTION
[0027] The invention concerns a method for processing a signal
received at an uplink control information (UCI) receiver in a
wireless communication system. The method comprises processing a
signal received on an uplink (UL) at said UCI receiver to transform
said received signal into a likelihood calculation of possible
transmitted codewords (.theta..sub.1 . . . .theta.i . . .
.theta..sub.N) and determining a maximum magnitude .theta..sub.max
value from said likelihood calculation. The method includes
comparing said maximum magnitude .theta..sub.max value to a
selected, calculated or predetermined scaled threshold S.tau. where
.tau. is a threshold and S is a scaling factor for the threshold r.
The comparison step is such that, where
|.theta..sub.max|.sup.2>S.tau., the method comprises determining
that the signal received on the UL at said UCI receiver comprises a
linear block encoded signal. In the method, prior to said
comparison step, the scaling factor S is selected from a plurality
of scaling factor options. One scaling factor option is a scaling
factor S.sub.RE derived from a combination of estimated noise
and/or signal power at an output of a resource element (RE)
demapper module and an estimated channel response from an equalizer
module of said UCI receiver.
[0028] In a first main aspect, the invention provides a method of
processing a signal received at a UCI receiver in a wireless
communication system, the method comprising: processing a signal
received on a UL at said UCI receiver to transform said received
signal into a likelihood calculation of possible transmitted
codewords (.theta..sub.1 . . . .theta.i . . . .theta..sub.N);
determining a maximum magnitude .theta..sub.max value from said
likelihood calculation of possible transmitted codewords
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N); and comparing
said maximum magnitude .theta..sub.max value to a selected,
calculated or predetermined scaled threshold S.tau. where .tau. is
a threshold and S is a scaling factor for the threshold r and said
scaled threshold S.tau. is a product of the threshold .tau. and the
scaling factor S, the comparison being such that, where
|.theta..sub.max|.sup.2>S.tau., the method comprises determining
that the signal received on the UL at said UCI receiver comprises a
linear block encoded signal; wherein, prior to said comparison
step, the scaling factor S is selected from a plurality of scaling
factor options.
[0029] Preferably, where |.theta..sub.max|.sup.2.ltoreq.S.tau., the
method comprises outputting a discontinuous transmission (DTX)
signal.
[0030] In a second main aspect, the invention provides a UCI
receiver in a wireless communication system, the UCI receiver
comprising: a memory storing machine-readable instructions; and a
processor for executing the machine-readable instructions such
that, when the processor executes the machine-readable
instructions, it configures the receiver to implement the first
main aspect of the invention.
[0031] In a third main aspect, the invention provides a method of
processing a signal received at a UCI receiver in a wireless
communication system, the method comprising: processing a signal
received on a UL at said UCI receiver to transform said received
signal into a likelihood calculation of possible transmitted
codewords (.theta..sub.1 . . . .theta.i . . . .theta..sub.N);
determining a maximum magnitude .theta..sub.max value from said
likelihood calculation of possible transmitted codewords
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N); and comparing
said .theta..sub.max value to a selected, calculated or
predetermined scaled threshold &r where .tau. is a threshold
and S is a scaling factor for the threshold .tau. and said scaled
threshold S.tau. is a product of the threshold .tau. and the
scaling factor S, and where the scaling factor is S derived from a
combination of estimated noise and/or signal power at an output of
a resource element (RE) demapper module of the UCI receiver and an
estimated channel response from an equalizer module of said UCI
receiver, the comparison being such that, where
|.theta..sub.max|.sup.2>S.tau., the method comprises determining
that the signal received on the UL at said UCI receiver comprises a
linear block encoded signal.
[0032] In a fourth main aspect, the invention provides a UCI
receiver in a wireless communication system, the UCI receiver
comprising: a memory storing machine-readable instructions; and a
processor for executing the machine-readable instructions such
that, when the processor executes the machine-readable
instructions, it configures the receiver to implement the third
main aspect of the invention.
[0033] The summary of the invention does not necessarily disclose
all the features essential for defining the invention; the
invention may reside in a sub-combination of the disclosed
features.
[0034] The forgoing has outlined fairly broadly the features of the
present invention in order that the detailed description of the
invention which follows may be better understood. Additional
features and advantages of the invention will be described
hereinafter which form the subject of the claims of the invention.
It will be appreciated by those skilled in the art that the
conception and specific embodiment disclosed may be readily
utilized as a basis for modifying or designing other structures for
carrying out the same purposes of the invention.
BRIEF DESCRIPTION OF THE DRAWINGS
[0035] The foregoing and further features of the present invention
will be apparent from the following description of preferred
embodiments which are provided by way of example only in connection
with the accompanying figures, of which:
[0036] FIG. 1 is a signal diagram illustrating message exchanges
between a BS and a UE for retransmission of control data and
payload data;
[0037] FIG. 2 is a signal diagram illustrating errant transmission
of control data and payload data from a BS to a UE when a UCI
receiver at the BS determines a false ACK message;
[0038] FIG. 3 is a block schematic diagram of a conventional polar
code-based receiver for a 5G communications system;
[0039] FIG. 4 is a block schematic diagram of a conventional small
block code-based receiver for a 5G communications system;
[0040] FIG. 5 is a block schematic diagram of a UCI receiver in
accordance with the invention;
[0041] FIG. 6 is a block diagram illustrating an improved scaling
factor determination method in accordance with one aspect of the
present invention;
[0042] FIG. 7 is a diagram schematically illustrating method steps
in accordance with the invention performed by the UCI receiver of
FIG. 5 utilizing the improved scaling factor determined by the
method of FIG. 6;
[0043] FIG. 8 is a block diagram illustrating a combined scaling
factor determination method in accordance with another aspect of
the present invention;
[0044] FIG. 9 is a block diagram illustrating a scaling factor
selection method in accordance with another aspect of the present
invention;
[0045] FIG. 10 is a diagram schematically illustrating method steps
in accordance with the invention performed by the UCI receiver of
FIG. 5 utilizing a scaling factor derived from a multi-dimensional
DFT of the signal received on the UL at said UCI receiver;
[0046] FIG. 11 is a block diagram illustrating a combined scaling
factor determination method based on the improved scaling factor
determined by the method of FIG. 6 and the scaling factor derived
from the multi-dimensional DFT of the signal received on the UL at
said UCI receiver, and
[0047] FIG. 12 is a block diagram illustrating a scaling factor
selection method in accordance with another aspect of the present
invention.
DESCRIPTION OF PREFERRED EMBODIMENTS
[0048] The following description is of preferred embodiments by way
of example only and without limitation to the combination of
features necessary for carrying the invention into effect.
[0049] Reference in this specification to "one embodiment" or "an
embodiment" means that a particular feature, structure, or
characteristic described in connection with the embodiment is
included in at least one embodiment of the invention. The
appearances of the phrase "in one embodiment" in various places in
the specification are not necessarily all referring to the same
embodiment, nor are separate or alternative embodiments mutually
exclusive of other embodiments. Moreover, various features are
described which may be exhibited by some embodiments and not by
others. Similarly, various requirements are described which may be
requirements for some embodiments, but not other embodiments.
[0050] It should be understood that the elements shown in the FIGS,
may be implemented in various forms of hardware, software or
combinations thereof. These elements may be implemented in a
combination of hardware and software on one or more appropriately
programmed general-purpose devices, which may include a processor,
memory and input/output interfaces.
[0051] The present description illustrates the principles of the
present invention. It will thus be appreciated that those skilled
in the art will be able to devise various arrangements that,
although not explicitly described or shown herein, embody the
principles of the invention and are included within its spirit and
scope.
[0052] Moreover, all statements herein reciting principles,
aspects, and embodiments of the invention, as well as specific
examples thereof, are intended to encompass both structural and
functional equivalents thereof. Additionally, it is intended that
such equivalents include both currently known equivalents as well
as equivalents developed in the future, i.e., any elements
developed that perform the same function, regardless of
structure.
[0053] Thus, for example, it will be appreciated by those skilled
in the art that the block diagrams presented herein represent
conceptual views of systems and devices embodying the principles of
the invention.
[0054] The functions of the various elements shown in the figures
may be provided through the use of dedicated hardware as well as
hardware capable of executing software in association with
appropriate software. When provided by a processor, the functions
may be provided by a single dedicated processor, by a single shared
processor, or by a plurality of individual processors, some of
which may be shared. Moreover, explicit use of the term "processor"
or "controller" should not be construed to refer exclusively to
hardware capable of executing software, and may implicitly include,
without limitation, digital signal processor ("DSP") hardware,
read-only memory ("ROM") for storing software, random access memory
("RAM"), and non-volatile storage.
[0055] In the claims hereof, any element expressed as a means for
performing a specified function is intended to encompass any way of
performing that function including, for example, a) a combination
of circuit elements that performs that function or b) software in
any form, including, therefore, firmware, microcode or the like,
combined with appropriate circuitry for executing that software to
perform the function. The invention as defined by such claims
resides in the fact that the functionalities provided by the
various recited means are combined and brought together in the
manner which the claims call for. It is thus regarded that any
means that can provide those functionalities are equivalent to
those shown herein.
[0056] The invention relates to a method for detecting
acknowledgment (ACK), negative acknowledgment (NACK) and
discontinuous transmission (DTX) signals accurately in uplink
control information (UCI) in wireless communication systems. It is
particularly useful for DTX detection in small block code-based
receivers where cyclic redundancy check CRC is not available for
DTX detection.
[0057] FIG. 5 shows an exemplary embodiment of an improved UCI
receiver device 100 in accordance with concepts of the present
invention. In the illustrated embodiment, the UCI receiver device
100 may comprise communication equipment such as a network node, a
network card, or a network circuit communicatively connected to or
forming part of a BS 103 (denoted by dashed line in FIG. 5), etc.
operating in a 5G communications system environment 115, although
the improved UCI receiver device 100 of the invention is not
limited to operating in a 5G communications system but could
comprise a UCI receiver device for a 4G cellular network or any
cellular network. The BS 103 communicates with one or more UEs
125.
[0058] The UCI receiver device 100 may comprise a plurality of
functional blocks for performing various functions thereof. For
example, the UCI receiver device 100 includes receiver module 110
providing received signal processing and configured to provide
received signals and/or information extracted therefrom to
functional block module(s) 120 such as may comprise various data
sink, control element(s), user interface(s), etc. Although receiver
module 110 is described as providing received signal processing, it
will be appreciated that this functional block may be implemented
as a transceiver providing both transmitted and received signal
processing. Irrespective of the particular configuration of
receiver 110, embodiments include signal detection module 130
disposed in association with the receiver module 110 for
facilitating accurate processing and/or decoding of a received
channel signal in accordance with the invention. Channel signals
may be received via an antenna module 105.
[0059] Although the signal detection module 130 is shown as being
deployed as part of the receiver module 110 (e.g. comprising a
portion of the receiver module control and logic circuits), there
is no limitation to such a deployment configuration according to
the concepts of the invention. For example, the signal detection
module 130 may be deployed as a functional block of UCI receiver
device 100 that is distinct from, but connected to, receiver module
110. The signal detection module 130 may, for example, be
implemented using logic circuits and/or executable code/machine
readable instructions stored in a memory 140 of the UCI receiver
device 100 for execution by a processor 150 to thereby perform
functions as described herein. For example, the executable
code/machine readable instructions may be stored in one or more
memories 140 (e.g. random access memory (RAM), read only memory
(ROM), flash memory, magnetic memory, optical memory or the like)
suitable for storing one or more instruction sets (e.g. application
software, firmware, operating system, applets, and/or the like),
data (e.g. configuration parameters, operating parameters and/or
thresholds, collected data, processed data, and/or the like), etc.
The one or more memories 140 may comprise processor-readable
memories for use with respect to one or more processors 150
operable to execute code segments of signal detection module 130
and/or utilize data provided thereby to perform functions of the
signal detection module 130 as described herein. Additionally, or
alternatively, the signal detection module 130 may comprise one or
more special purpose processors (e.g. application specific
integrated circuit (ASIC), field programmable gate array (FPGA),
graphics processing unit (GPU), and/or the like configured to
perform functions of the signal detection module 130 as described
herein.
[0060] FIG. 6 provides a block diagram illustrating an improved
scaling factor Su determination method and utilization of the
improved scaling factor determined thereby in determining a DTX
state in accordance with one aspect of the present invention. The
scaling factor S.sub.RE is determined, calculated or derived from a
combination of estimated noise and/or signal power at an output of
the RE demapper module of the UCI receiver device 100 and an
estimated channel response from the equalizer module of said UCI
receiver device 100. By improving the scaling factor S, the
determination of a DTX state becomes more accurate. The improved
scaling factor S.sub.RE makes use of the estimated noise and/or
signal power at the output of the RE demapper module which has not
previously been effectively used. Consequently, where
|.theta..sub.max|.sup.2>S.sub.RE.tau., where .tau. is a
predetermined threshold, the method comprises determining that the
signal received on the UL at said UCI receiver device 100 comprises
a linear block encoded signal and conversely, where
|.theta..sub.max|.sup.2.ltoreq.S.sub.RE.tau., the method comprises
determining that the signal received on the UL at said UCI receiver
device 100 comprises a DTX state.
[0061] The scaling factor S.sub.RE is preferably derived from the
equation:
S RE = r .times. i .times. k .times. g r , l , k g r , l , k ''
.sigma. r 2 ##EQU00001##
[0062] where .sigma..sub.R.sup.2 is the estimated noise variance or
signal power corresponding to the r-th receiver antenna obtained at
the output of the RE demapper module; and
[0063] g.sub.r,l,k is the estimated channel response obtained
before the equalizer module as an input to the equalizer module
with r comprising a receiver antenna index value, l comprising a
time domain index value, e.g. an OFDM symbol index, and k
comprising a frequency domain index value, e.g. a subcarrier
index.
[0064] FIG. 7 schematically illustrates an improved linear block
code-based (UCI) receiver device 100/200, an improved decoder 210
for the improved linear block code-based (UCI) receiver device
100/200, and improved and enhanced methods implemented by the
signal detection module 130 comprising the improved decoder 210 for
the improved linear block code-based (UCI) receiver device 100/200
or for the UCI receiver device 100 of FIG. 5.
[0065] As described in greater detail below, the signal detection
module 130 comprising the improved decoder 210 is configured to
implement improved detection or determination of acknowledgment
(ACK), negative acknowledgment (NACK) and discontinuous
transmission (DTX) signals accurately in uplink control information
(UCI) in wireless communication systems.
[0066] In one embodiment, the UCI receiver device 100/200 is
configured to receive a UL UCI signal as a demapper output signal.
The demapper output signal is firstly equalized in a known manner
in an equalizer module 202 to provide an equalized signal. The
equalized signal is then demodulated and descrambled again in a
known manner by a demodulation/descrambling module 204 which
outputs soft bits to the improved decoder 210. In FIG. 6, the
improved decoder 210 is shown as a small block code decoder 210 but
it will be understood that this is shown by way of example only.
The small block code decoder 210 is configured to process said
received signal in a transform module 210A to transform, in step
300, said received signal into a likelihood calculation of possible
transmitted codewords in said received signal. Preferably, the
likelihood calculation of possible transmitted codewords comprises
a multi-dimensional discrete Fourier transform (DFT) (.theta..sub.1
. . . .theta.i . . . .theta..sub.N) of said received signal. The UL
UCI signal is received at the UCI receiver device 100/200 from a UE
125 operating in the 5G communications system environment 115 and
which is wirelessly connected to the BS 103 via a UL channel.
However, it will be understood that the signal received at the UCI
receiver device 100/200 may only comprise noise in an instance
where the UE 125 has missed a DL control message from the BS 103
and the UE 125 has therefore not issued any message or signal in
response to the missed DL control message. In this case, the UCI
receiver device 100/200 anticipates receiving a reply message from
the UE 125 and therefore treats received noise as a UL UCI signal
to be processed. In either case, the small block code decoder 210
processes the `received signal` whether it is a real UL UCI signal
from the UE 125 or whether it is a noise signal mistakenly taken as
being a real UL UCI signal from the UE 125 to transform said signal
into the multi-dimensional discrete Fourier transform (DFT)
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N).
[0067] As indicated above, the signal detection module 130 of FIG.
5 may comprise the improved decoder 210 for an improved linear
block code-based (UCI) receiver device 100/200 of FIG. 7 with, in
one embodiment, the improved decoder 210 replacing the polar code
decoder forming part of the conventional polar code-based receiver
of FIG. 3 or, more preferably, in another embodiment, the improved
decoder 210 replacing, as shown in FIG. 7, the small block code
decoder forming part of the conventional small block code-based
receiver of FIG. 4.
[0068] It will be understood from the description that the signal
detection module 130 comprising the improved decoder 210 may be
implemented through any of software, firmware and/or hardware
changes to conventional linear block code decoders, although it is
possible to implement the improved decoder 210 of the invention by
implementing only software changes.
[0069] The likelihood calculation of possible transmitted codewords
in the UL UCI signal received at said UCI receiver device 100/200
may be expressed as likelihood values. The multi-dimensional DFT
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N) may comprise a
Hadamard transform of said received signal. The Hadamard transform
is also known as the Walsh-Hadamard transform, the
Hadamard-Rademacher-Walsh transform, the Walsh transform or the
Walsh-Fourier transform. Herein, it will be referred to as the
`Hadamard transform` but encompasses all forms of said
transform.
[0070] A module 210B of the small block code decoder 210 is
configured to determine, in step 305, a maximum magnitude
.theta..sub.max value from said likelihood calculation of possible
transmitted codewords. The maximum magnitude .theta..sub.max value
may be determined or calculated from a plurality of real numbers
comprising said multi-dimensional DFT (.theta..sub.1 . . . .theta.i
. . . .theta..sub.N).
[0071] In conventional UCI receivers as exemplified by FIGS. 3 and
4, the UCI bits denoting ACK or NACK messages are derived from the
maximum magnitude .theta..sub.max value's index and sign.
Similarly, a UCI-bits module 210C of the small block code decoder
210 is configured to generate, in a known manner in step 310, UCI
bits according to the index and sign of the maximum magnitude
.theta..sub.max value.
[0072] As already described with respect to FIG. 4, the absence of
a CRC function in the conventional small block code-based receiver
prevents a determination of whether or not a received UL UCI signal
is, in fact, indicative of a DTX state rather than an ACK or NACK
message. In other words, the absence of a CRC function prevents a
determination being made between DTX on the one hand and ACK/NACK
on the other hand.
[0073] Comparing said .theta..sub.max value or, more preferably
|.theta..sub.max|.sup.2, to a selected, calculated or predetermined
scaled threshold S.tau. where S is the scaling factor for the
threshold .tau. and said scaled threshold S.tau. is obtained by
multiplying the threshold .tau. by the scaling factor S, the
comparison being such that, where
|.theta..sub.max|.sup.2>S.tau., the method comprises determining
that the signal received on the UL at said UCI receiver comprises a
linear block encoded signal.
[0074] A first embodiment of the method of the invention includes,
in step 315, the step of comparing said |.theta..sub.max|.sup.2
value to the scaled threshold S.sub.RE.tau.. The scaling factor
S.sub.RE may be obtained by a DTX detector for UCI module 210D by
estimating the scaling factor S.sub.RE from the combination of
estimated noise and/or signal power at the output of the RE
demapper module of the UCI receiver device 100/200 and the
estimated channel response from the equalizer module 202 of said
UCI receiver device 100/200.
[0075] The DTX detector for UCI module 210D for the small block
code decoder 210 has loaded into a memory thereof the predetermined
threshold .tau.. The threshold .tau. is preferably derived from a
target detection performance and a number of detection occurrences
in the signal received on the UL at said UCI receiver device
100/200. The target detection performance may comprise any of: a
target probability of detecting DTX as an acknowledgement message
(ACK) (Pr(DTX.fwdarw.ACK)); a target probability of detecting DTX
as a transmitted message (TX) (Pr(DTX.fwdarw.TX)); or a target
probability of detecting a false alarm (Pr(FA)) in the signal
received on the UL at said UCI receiver device 100/200.
[0076] The number of detection occurrences is preferably determined
from a number of payload bits and/or a number of encoded bits in
the signal received on the UL at said UCI receiver device
100/200.
[0077] The threshold .tau. may also be determined according to a
tail probability of the distribution of the multi-dimensional DFT
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N).
[0078] More particularly, the threshold .tau. is derived from:
.tau. = Q - 1 .function. ( 1 2 - 1 2 .times. ( P detect ) 1 N
detest ) , ##EQU00002##
[0079] where
[0080] where Q.sup.-1( ) is the inverse Q-function
[0081] N.sub.detect=2.sup.N.sup.bit.sup.-1
[0082] P.sub.detect=1-2 Pr(DTX.fwdarw.ACK), or 1-Pr(DTX.fwdarw.TX),
or 1-Pr(FA), and
[0083] N.sub.bit is a number of payload bits and/or a number of
encoded bits in the in the signal received on the UL at said UCI
receiver device 100/200.
[0084] In FIG. 7, only P.sub.detect=1-2 Pr(DTX.fwdarw.ACK) is shown
for clarity of the drawing.
[0085] The threshold .tau. is dependent on two inputs, namely the
target probability and the number of payload bits and/or a number
of encoded bits as hereinbefore described. As such, the threshold
.tau. can be predetermined and loaded into the memory 140 of the
UCI receiver device 100/200. As such, the threshold .tau. does not
necessarily need to be determined in real-time. Furthermore, the
scaled threshold S.tau. is suitable for different channels or
channel conditions which greatly simplifies the method of the
invention and reduces the computational workload in the signal
detection module 130/small block code decoder 210.
[0086] The small block code decoder 210 is configured, in step 315,
to determine whether or not the signal received on the UL at said
UCI receiver device 100/200 comprises a linear block encoded signal
when |.theta..sub.max|.sup.2>S.tau.. However, where
|.theta..sub.max|.sup.2.ltoreq.S.tau., a discontinuous transmission
(DTX) signal is outputted at step 315.
[0087] In the case where |.theta..sub.max|.sup.2>S.tau., step
315 may be enhanced to output an acknowledgement (ACK) message or a
negative-acknowledgement (NACK) message based on the generated UCI
bits.
[0088] The method described with respect to FIG. 7 make uses of
only the improved scaling factor S.sub.RE and therefore references
to S in the above description can be taken to be references to
S.sub.RE. However, in the following description S may comprise one
of a number of scaling factor options as will be described and thus
references to S may comprise references to any of said scaling
factor options.
[0089] Referring to FIG. 8, provided is a block diagram
illustrating a combined scaling factor S.sub.COMB determination
method and utilization of the combined scaling factor S.sub.COMB
determined thereby in determining a DTX state in accordance with
another aspect of the present invention. The scaling factor
S.sub.COMB is determined, calculated or derived from a combination
of the improved scaling factor S.sub.RE and any other scaling
factor S.sub.OTHER suitable for determining a DTX state.
S.sub.OTHER may comprise known scaling factors for determining a
DTX state. The scaling factor S.sub.COMB=f(S.sub.OTHER,
S.sub.RE)=a(S.sub.OTHER).sup..lamda.(S.sub.RE).sup.1-.lamda., where
.lamda. comprises a weighting value less than 1 and .alpha.
comprises a combination coefficient. The scaling factor S.sub.COMB
is therefore derived from a function of the improved scaling factor
S.sub.RE and any other scaling factor S.sub.OTHER suitable for
determining a DTX state. The combination coefficient .alpha. may be
derived from a payload bit length. In some embodiments, the
combination coefficient .alpha. is equal to L The combination
coefficient .alpha. can be a sigmoid function of the payload bit
length l. The weighting value .lamda. may be greater than 0.5, but
is preferably equal to 0.667 (or 2/3), although it may take other
values such as 0 or 1.
[0090] In some embodiments, the combination coefficient .alpha. can
take the expression of the payload bit length l:
.alpha. = c exp .function. ( - ( l - l 0 ) .omega. d ) + .alpha. 0
##EQU00003##
[0091] where c is a scaling coefficient, l.sub.0 is a constant
offset, d is a normalization factor, .omega. is the exponent and
.alpha..sub.0 are parameters of the combination coefficient
.alpha.. Typical values of the parameters may be c=02, .omega.=2,
l.sub.0=2, d=25, .alpha.=09.45.
[0092] Consequently, in this aspect of the invention, the method
comprises determining that the signal received on the UL at said
UCI receiver device 100/200 comprises a linear block encoded signal
when where |.theta..sub.max|.sup.2>S.sub.COMB.tau. and
conversely, where |.theta..sub.max|.sup.2.ltoreq.S.sub.COMB.tau.,
the method comprises determining that the signal received on the UL
at said UCI receiver device 100/200 comprises a DTX state.
[0093] FIG. 9 illustrates another aspect of the invention where the
scaling factor S may be selected from a number of scaling factor
options. The method includes selecting as the scaling factor S one
of (i) S.sub.RE, (ii) S.sub.OTHER, or (iii) S.sub.COMB. The
selection of which scaling factor option to choose may be based on
one or more signal conditions. For example, option (i) may be
selected if the estimated noise and/or signal power at the output
of the RE demapper module is at an acceptable or better level;
otherwise option (iii) may be selected if the number of UCI payload
bits is large; otherwise option (ii) is selected. In some
embodiments, option (ii) may be selected if a code mask is not
applied at the encoder module of the UCI receiver; otherwise option
(iii) may be selected if a code mask is applied. In yet other
embodiments, option (ii) may be selected if a payload bit length is
smaller than or equal to a maximum unmask bit payload length;
otherwise option (iii) may be selected if the payload bit length is
larger than the maximum unmask bit payload length. The maximum
unmask payload bit length can take the value of 6 when the block
code length is 32.
[0094] It will be noted that the step of selecting a scaling factor
option is implemented prior to the step of comparing the resultant
scaled threshold S.tau. to the maximum magnitude .theta..sub.max
value, i.e. to |.theta..sub.max|.sup.2, or configured as a default
option.
[0095] In some embodiments, S.sub.OTHER=S.sub.HAD. FIG. 10 provides
a diagram schematically illustrating method steps in accordance
with the invention performed by the UCI receiver 100 of FIG. 5
utilizing the scaling factor S.sub.HAD derived from the
multi-dimensional DFT of the signal received on the UL at said UCI
receiver 100.
[0096] FIG. 10 schematically illustrates the improved linear block
code-based (UCI) receiver device 100'/200', an improved decoder
210'A for the improved linear block code-based (UCI) receiver
device 100'/200', and improved and enhanced methods implemented by
the signal detection module 130 comprising the improved decoder
210' for the improved linear block code-based (UCI) receiver device
100'/200' or for the UCI receiver device 100 of FIG. 5.
[0097] As described above, the signal detection module 130
comprising the improved decoder 210' is configured to implement
improved detection or determination of acknowledgment (ACK),
negative acknowledgment (NACK) and discontinuous transmission (DTX)
signals accurately in uplink control information (UCI) in wireless
communication systems.
[0098] The UCI receiver device 100'/200' receives the UL UCI signal
as a RE demapper output signal which is firstly equalized in an
equalizer module 202' to provide an equalized signal. The equalized
signal is then demodulated and descrambled again by a
demodulation/descrambling module 204' which outputs soft bits to
the improved decoder 210'.
[0099] In FIG. 10, the improved decoder 210' is shown as a small
block code decoder 210' but it will be understood that this is
shown by way of example only. The small block code decoder 210' is
configured to process said received signal in a transform module
210'A to transform, in step 300', said received signal into a
likelihood calculation of possible transmitted codewords in said
received signal. The likelihood calculation of possible transmitted
codewords comprises a multi-dimensional discrete Fourier transform
(DFT) (.theta..sub.1 . . . .theta.i . . . .theta..sub.N) of said
received signal. The UL UCI signal is received at the UCI receiver
device 100'/200' from a UE 125' operating in the 5G communications
system environment 115' and which is wirelessly connected to the BS
103' via a UL channel. The small block code decoder 210' processes
the `received signal` whether it is a real UL UCI signal from the
UE 125' or whether it is a noise signal mistakenly taken as being a
real UL UCI signal from the UE 125' to transform said signal into
the multi-dimensional discrete Fourier transform (DFT)
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N).
[0100] The likelihood calculation of possible transmitted codewords
in the UL UCI signal received at said UCI receiver device 100'/200'
may be expressed as likelihood values. The multi-dimensional DFT
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N) may comprise a
Hadamard transform of said received signal.
[0101] A module 210'B of the small block code decoder 210' is
configured to determine, in step 305, a maximum magnitude
.theta..sub.max value from said likelihood calculation of possible
transmitted codewords.
[0102] A UCI-bits module 210'C of the small block code decoder 210'
is configured to generate, in a known manner in step 310, UCI bits
according to the index and sign of the maximum magnitude
.theta..sub.max value.
[0103] A first embodiment of the method of the invention
illustrated by FIG. 10 includes, in step 315, the step of comparing
said .theta..sub.max value to a selected, calculated or
predetermined scaled threshold S.sub.HAD.tau.. The scaling factor
S.sub.HAD may be obtained by a DTX detector for UCI module 210'D by
estimating the scaling factor S.sub.HAD from the multi-dimensional
DFT (.theta..sub.1 . . . .theta.i . . . .theta..sub.N) but is
preferably obtained by obtaining an estimate of the noise variance
after the DFT transform step.
[0104] The threshold .tau. is preferably determined in the manner
described with respect to FIG. 7.
[0105] The small block code decoder 210' is configured, in step
315, to determine whether or not the signal received on the UL at
said UCI receiver device 100'/200' comprises a linear block encoded
signal when |.theta..sub.max|.sup.2>S.sub.HAD.tau.. However,
where |.theta..sub.max|.sup.2.ltoreq.S.sub.HAD.tau., a
discontinuous transmission (DTX) signal is outputted at step
315.
[0106] Referring to FIG. 11, provided is a block diagram
illustrating a second combined scaling factor S.sub.COMB
determination method and utilization of the combined scaling factor
Scows determined thereby in determining a DTX state in accordance
with yet another aspect of the present invention. The scaling
factor S.sub.COMB is determined, calculated or derived from a
combination of the improved scaling factor S.sub.RE and the scaling
factor S.sub.HAD of FIG. 10. The scaling factor
S.sub.COMB=f(S.sub.HAD,
S.sub.RE)=.alpha.(S.sub.HAD).sup..lamda.(S.sub.RE).sup.1-.lamda.,
where, as before, .lamda. comprises a weighting value less than 1
and .alpha. comprises a combination coefficient. The scaling factor
S.sup.COMB is therefore derived from a function of the improved
scaling factor S.sub.RE and the scaling factor S.sub.HAD. The
combination coefficient .alpha. may be derived from a payload bit
length. In some embodiments, the combination coefficient .alpha. is
equal to 1. The weighting value) may be greater than 0.5, but is
preferably equal to 0.667, but may take other values as
hereinbefore described.
[0107] Consequently, in this aspect of the invention, the method
comprises determining that the signal received on the UL at said
UCI receiver device 100/200, 100'/200' comprises a linear block
encoded signal when where
|.theta..sub.max|.sup.2>S.sub.COMB.tau. and conversely, where
|.theta..sub.max|.sup.2.ltoreq.S.sub.COMB.tau., the method
comprises determining that the signal received on the UL at said
UCI receiver device 100/200, 100'/200' comprises a DTX state.
[0108] FIG. 12 illustrates a further aspect of the invention where
the scaling factor S may be selected from a number of scaling
factor options. The method includes selecting as the scaling factor
S one of (i) S.sub.RE, (ii) S.sub.HAD, or (iii) S.sub.COMB. The
selection of which scaling factor option to choose may be based on
one or more signal conditions or other factors. For example, it is
found that S.sub.HAD can lead to over-estimation of noise variance
at one end of the variance scale fundamentally due to the fact that
the S.sub.HAD and the |.theta..sub.max|.sup.2 both are obtained
according to the same realizations of (.theta..sub.1 . . . .theta.i
. . . .theta..sub.N), and their monotonicity has a close and
positive relationship. Consequently, under certain conditions it is
better to use S.sub.RE than S.sub.HAD and vice-versa and, in yet
other conditions, it is better to combine S.sub.RE than S.sub.HAD
to provide S.sub.COMB. It is noted, however, that S.sub.RE can lead
to under-estimation of noise variance, especially for the case
where the framework of used noise estimation method is based on
subtracting the estimated signal portion (derived using the
estimated channel) from the overall received signal. Moreover, the
degree of under-estimation by S.sub.RE may be more significant than
the degree of over-estimation caused by S.sub.HAD. Consequently, it
is preferred that the weighting value .lamda. is greater than 0.5
and is preferably as high as 0.667. Simulated results show that a
value of .lamda.=2/3 (0.667) achieves near to 1% false alarm rate
(FAR) which is desirable.
[0109] It has been found that using option (i) S.sub.RE provides
excellent results when there is a good noise estimator at the RE
demapper output, where the noise estimation takes into
consideration the channel/signal characteristics other than PUCCH
such that the under-estimation effect will be weaker than other
cases. This is the preferred option. However, if the noise
estimation is poor and the number UCI payload bits is large. e.g.,
more than 6, then option (iii) S.sub.COMB is preferred because,
when the number UCI payload bits is above 6, the 3GPP standard
38.212 requires a code mask operation to be implemented where the
influence of over-estimation by S.sub.HAD is increased. In the
event that neither of options (i) or (iii) are selected, i.e.,
deemed suitable, then option (ii) S.sub.HAD is selected as the
`baseline` option.
[0110] It can be seen therefore that the methods of the foregoing
aspects and embodiments of the invention can be most usefully,
although not exclusively, utilized in a small block code-based
receiver not having CRC functionality such as that exemplified by
FIG. 4 to determine if a signal received on the UL at the UCI
receiver device 100/200, 100'/200' comprises a linear block encoded
signal and furthermore to detect or determine if the received
signal, whether real or comprising noise, includes an ACK message
from the UE 125, 125' or a NACK message from the UE 125, 125'. In
other words, not only can the method of the above embodiments
determine if the received signal comprises a linear block encoded
signal but it also enables the improved decoder 210, 210' to
distinguish between a DTX state on the one hand and ACK/NACK
signals on the other hand. Consequently, the method of the above
embodiments is particularly useful in wireless communication
systems for DTX detection in small block code-based receivers where
cyclic redundancy check CRC is not available for DTX detection.
[0111] The methods can therefore be utilized to determine that the
signal received on the UL at the UCI receiver device 100/200,
100'/200' comprises a small block encoded signal in a long-term
evolution (LTE) communication system and, more particularly, to
determine DTX in a small block encoded signal comprising a NR (5G)
Physical Uplink Control Channel (PUCCH) format such as PUCCH format
2, PUCCH format 3, or PUCCH format 4.
[0112] It will be understood that the linear block code may be
Reed-Muller (RM) code or RM-based super code.
[0113] Outputting a DTX state may comprise outputting a Boolean or
binary value indicative of said DTX state.
[0114] In general, signal power varies over time. In a case of DTX,
for example, where the received signal only comprises noise, the
noise power is not constant over time. Therefore, it is necessary
to estimate the noise power (e.g., based on all of (.theta..sub.1 .
. . .theta.i . . . .theta..sub.N)), at one or more points in time.
Otherwise, the maximum magnitude .theta..sub.max value derived from
the received signal comprising only noise may still be such that
the maximum magnitude .theta..sub.max value is greater than the
threshold .tau., due to the fact that (.theta..sub.1 . . . .theta.i
. . . .theta..sub.N) are all/mostly large on the whole, rather than
due to the fact that .theta..sub.max is really outstanding among
(.theta..sub.1 . . . .theta.i . . . .theta..sub.N). Using a scaling
factor S with the threshold .tau. helps to address this
problem.
[0115] In other embodiments, it is possible that the scaling factor
S can be omitted in, for example, the case where we have a priori
knowledge of the noise power over a long period of time. In this
case, it is possible to determine that noise on the UL channel does
not vary rapidly over time or to determine that it follows a
certain distribution. In this way, it is possible to treat the
noise power as a constant or at least a known entity. Consequently,
as long as a suitable level for the threshold .tau. is chosen, it
may no longer become necessary to apply a scaling factor to the
threshold .tau..
[0116] The invention also provides a non-transitory
computer-readable medium 140 storing machine-readable instructions,
wherein, when the machine-readable instructions are executed by a
processor 150, they configure the processor 150 to implement the
afore-described methods in accordance with the invention.
[0117] The apparatus described above may be implemented at least in
part in software. Those skilled in the art will appreciate that the
apparatus described above may be implemented at least in part using
general purpose computer equipment or using bespoke equipment.
[0118] Here, aspects of the methods and apparatuses described
herein can be executed on any apparatus comprising the
communication system. Program aspects of the technology can be
thought of as "products" or "articles of manufacture" typically in
the form of executable code and/or associated data that is carried
on or embodied in a type of machine-readable medium. "Storage" type
media include any or all of the memory of the mobile stations,
computers, processors or the like, or associated modules thereof,
such as various semiconductor memories, tape drives, disk drives,
and the like, which may provide storage at any time for the
software programming. All or portions of the software may at times
be communicated through the Internet or various other
telecommunications networks. Such communications, for example, may
enable loading of the software from one computer or processor into
another computer or processor. Thus, another type of media that may
bear the software elements includes optical, electrical and
electromagnetic waves, such as used across physical interfaces
between local devices, through wired and optical landline networks
and over various air-links. The physical elements that carry such
waves, such as wired or wireless links, optical links or the like,
also may be considered as media bearing the software. As used
herein, unless restricted to tangible non-transitory "storage"
media, terms such as computer or machine "readable medium" refer to
any medium that participates in providing instructions to a
processor for execution.
[0119] While the invention has been illustrated and described in
detail in the drawings and foregoing description, the same is to be
considered as illustrative and not restrictive in character, it
being understood that only exemplary embodiments have been shown
and described and do not limit the scope of the invention in any
manner. It can be appreciated that any of the features described
herein may be used with any embodiment. The illustrative
embodiments are not exclusive of each other or of other embodiments
not recited herein. Accordingly, the invention also provides
embodiments that comprise combinations of one or more of the
illustrative embodiments described above. Modifications and
variations of the invention as herein set forth can be made without
departing from the spirit and scope thereof, and, therefore, only
such limitations should be imposed as are indicated by the appended
claims.
[0120] In the claims which follow and in the preceding description
of the invention, except where the context requires otherwise due
to express language or necessary implication, the word "comprise"
or variations such as "comprises" or "comprising" is used in an
inclusive sense, i.e., to specify the presence of the stated
features but not to preclude the presence or addition of further
features in various embodiments of the invention.
[0121] It is to be understood that, if any prior art publication is
referred to herein, such reference does not constitute an admission
that the publication forms a part of the common general knowledge
in the art.
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