U.S. patent application number 16/735667 was filed with the patent office on 2021-07-08 for inductor current based mode control for converter circuit.
The applicant listed for this patent is Goodix Technology Inc.. Invention is credited to Esmail BABAKRPUR NALOUSI, Ahmed EMIRA, Siavash YAZDI.
Application Number | 20210211046 16/735667 |
Document ID | / |
Family ID | 1000004589475 |
Filed Date | 2021-07-08 |
United States Patent
Application |
20210211046 |
Kind Code |
A1 |
YAZDI; Siavash ; et
al. |
July 8, 2021 |
INDUCTOR CURRENT BASED MODE CONTROL FOR CONVERTER CIRCUIT
Abstract
A converter circuit includes a pull up component, a pull down
component, and a controller configured to operate the pull up
component and the pull down component so as to deliver power to a
load. The controller is configured to operate the pull up and pull
down components in first and second operational modes, based on an
average current delivered to the load. The converter circuit also
includes a mode control circuit to generate a mode control signal
based in part on a representation of a peak current received at the
switch node from the pull up component.
Inventors: |
YAZDI; Siavash; (San Diego,
CA) ; BABAKRPUR NALOUSI; Esmail; (San Diego, CA)
; EMIRA; Ahmed; (San Diego, CA) |
|
Applicant: |
Name |
City |
State |
Country |
Type |
Goodix Technology Inc. |
San Diego |
CA |
US |
|
|
Family ID: |
1000004589475 |
Appl. No.: |
16/735667 |
Filed: |
January 6, 2020 |
Current U.S.
Class: |
1/1 |
Current CPC
Class: |
H02M 1/0025 20210501;
H02M 3/156 20130101; H02M 1/0009 20210501 |
International
Class: |
H02M 3/156 20060101
H02M003/156 |
Claims
1. A converter circuit, comprising: a switch node; a pull up
component configured to cause a voltage at the switch node to be
substantially equal to a voltage at a positive power supply,
wherein turning off the pull up component causes the voltage at the
switch node to decrease; a pull down component configured to cause
the voltage at the switch node to be substantially equal to a
voltage at a negative power supply, wherein turning off the pull
down component causes the voltage at the switch node to increase; a
controller configured to operate the pull up component and the pull
down component so as to deliver power to a load, where the
controller is configured to operate the pull up component and the
pull down component in either of first and second operational
modes, wherein the first operational mode is preferred if an
average current delivered to the load is greater than a current
threshold, and wherein the second operational mode is preferred if
the average current delivered to the load is less than the current
threshold; and a mode control circuit configured to generate a mode
control signal based in part on a representation of a peak current
received at the switch node from the pull up component, wherein the
controller is configured to operate the pull up component and the
pull down component in either of the first and second operational
modes based on the mode control signal.
2. The converter circuit of claim 1, wherein the first operational
mode is a continuous conduction mode.
3. The converter circuit of claim 1, wherein the second operational
mode is a pulse frequency modulation mode.
4. The converter circuit of claim 1, wherein the mode control
circuit comprises a peak current circuit configured to generate a
signal at a first node, wherein the signal that the first node
corresponds with the peak current received at the switch node from
the pull up component.
5. The converter circuit of claim 4, wherein the peak current
circuit comprises a current source configured to source current to
the first node while the pull up component delivers current to the
switch node, and wherein a magnitude of a current of the current
source is proportional to a current delivered by the pull up
component to the switch node.
6. The converter circuit of claim 4, wherein the mode control
circuit comprises a weighting circuit configured to multiply the
signal at the first node substantially by a ratio of an on time to
a period time to generate a weighted signal at a second node,
wherein the on time is equal to a duration of time when either the
pull up component or the pull down component are conductive during
a cycling period, and wherein the period time is equal to the total
duration of the cycling period.
7. The converter circuit of claim 6, wherein the weighting circuit
comprises: a buffer configured to drive a third node with a voltage
at the first node during the on time; and a switch configured to
connect the third node to a ground voltage while the buffer is not
driving the third node with the voltage at the first node.
8. The converter circuit of claim 6, wherein the mode control
circuit comprises a comparison circuit configured to compare the
weighted signal at the second node with a mode control threshold to
generate the mode control signal.
9. The converter circuit of claim 8, wherein the comparison circuit
comprises a comparator configured to compare the mode control
signal such that if the weighted signal at the second node is
greater than the mode control threshold, the mode control signal
causes the controller to operate the pull up component and pull
down component in the first operational mode.
10. The converter circuit of claim 8, wherein the comparison
circuit comprises a comparator configured to the mode control
signal such that if the weighted signal at the second node is less
than the mode control threshold, the mode control signal causes the
controller to operate the pull up component and pull down component
in the second operational mode.
11. A method of operating a converter circuit, the converter
circuit comprising: a switch node; a pull up component; a pull down
component; a controller; and a mode control circuit, the method
comprising: with the pull up component, causing a voltage at the
switch node to be substantially equal to a voltage at a positive
power supply, wherein turning off the pull up component causes the
voltage at the switch node to decrease with the pull down
component, causing the voltage at the switch node to be
substantially equal to a voltage at a negative power supply,
wherein turning off the pull down component causes the voltage at
the switch node to increase; with the controller, operating the
pull up component and the pull down component so as to deliver
power to a load; with the controller, operating the pull up
component and the pull down component in either of first and second
operational modes, wherein the first operational mode is preferred
if an average current delivered to the load is greater than a
current threshold, and wherein the second operational mode is
preferred if the average current delivered to the load is less than
the current threshold; with the mode control circuit, generating a
mode control signal based in part on a representation of a peak
current received at the switch node from the pull up component; and
with the controller operating the pull up component and the pull
down component in either of the first and second operational modes
based on the mode control signal.
12. The method of claim 11, wherein the first operational mode is a
continuous conduction mode.
13. The method of claim 11, wherein the second operational mode is
a pulse frequency modulation mode.
14. The method of claim 11, wherein the mode control circuit
comprises a peak current circuit, and the method further comprises,
with the peak current circuit, generating a signal at a first node,
wherein the signal that the first node corresponds with the peak
current received at the switch node from the pull up component.
15. The method of claim 14, wherein the peak current circuit
comprises a current source, and the method further comprises, with
the current source, sourcing current to the first node while the
pull up component delivers current to the switch node, and wherein
a magnitude of the current of the current source is proportional to
the current delivered by the pull up component to the switch
node.
16. The method of claim 14, wherein the mode control circuit
comprises a weighting circuit, and the method further comprises,
leaving circuit multiplying the signal at the first node
substantially by a ratio of an on time to a period time to generate
a weighted signal at a second node, wherein the on time is equal to
a duration of time when either the pull up component or the pull
down component are conductive during a cycling period, and wherein
the period time is equal to the total duration of the cycling
period.
17. The method of claim 16, wherein the weighting circuit comprises
a buffer and a switch, and wherein the method further comprises:
with the buffer, driving a third node with a voltage at the first
node during the on time; and with the switch, connecting the third
node to a ground voltage while the buffer is not driving the third
node with the voltage at the first node.
18. The method of claim 16, wherein the mode control circuit
comprises a comparison circuit, and the method further comprises,
with the comparison circuit, comparing the weighted signal at the
second node with a mode control threshold to generate the mode
control signal.
19. The method of claim 18, wherein the comparison circuit
comprises a comparator, and the method further comprises, with the
comparator, generating the mode control signal such that if the
weighted signal at the second node is greater than the mode control
threshold, the mode control signal causes the controller to operate
the pull up component and pull down component in the first
operational mode.
20. The method of claim 18, wherein the comparison circuit
comprises a comparator, and the method further comprises, with the
comparator, generating the mode control signal such that if the
weighted signal at the second node is less than the mode control
threshold, the mode control signal causes the controller to operate
the pull up component and pull down component in the second
operational mode.
Description
FIELD OF THE INVENTION
[0001] The present application generally pertains to converter
circuits, and more particularly to converter circuits which switch
between a pulse frequency modulation (PFM) operational mode and a
continuous conduction mode (CCM) operational mode.
BACKGROUND OF THE INVENTION
[0002] Certain data converters operate in either a pulse frequency
modulation (PFM) operational mode or a continuous conduction mode
(CCM) operational mode. The PFM operational mode may be
preferentially used for relatively low current load conditions, and
the CCM operational mode may be preferentially used for relatively
high load conditions. Techniques for determining current load
conditions are needed to effectively control the operational
mode.
BRIEF SUMMARY OF THE INVENTION
[0003] One aspect is a converter circuit. The converter circuit
includes a pull up component to cause a voltage at a switch node to
be substantially equal to a voltage at a positive power supply, a
pull down component to cause the voltage at the switch node to be
substantially equal to a voltage at a negative power supply, a
controller configured to operate the pull up component and the pull
down component so as to deliver power to a load. The controller is
configured to operate the pull up component and the pull down
component in either of first and second operational modes, where
the first operational mode is preferred if an average current
delivered to the load is greater than a current threshold, and
where the second operational mode is preferred if the average
current delivered to the load is less than the current threshold.
The converter circuit also includes a mode control circuit to
generate a mode control signal based in part on a representation of
a peak current received at the switch node from the pull up
component, where the controller is configured to operate the pull
up component and the pull down component in either of the first and
second operational modes based on the mode control signal.
[0004] Another inventive aspect is a method of operating a
converter circuit, the converter circuit including a switch node, a
pull up component, a pull down component, a controller, and a mode
control circuit. The method includes, with the pull up component,
causing a voltage at the switch node to be substantially equal to a
voltage at a positive power supply, where turning off the pull up
component causes the voltage at the switch node to decrease with
the pull down component. The method also includes causing the
voltage at the switch node to be substantially equal to a voltage
at a negative power supply, where turning off the pull down
component causes the voltage at the switch node to increase. The
method also includes, with the controller, operating the pull up
component and the pull down component so as to deliver power to a
load. The method also includes, with the controller, operating the
pull up component and the pull down component in either of first
and second operational modes, where the first operational mode is
preferred if an average current delivered to the load is greater
than a current threshold, and where the second operational mode is
preferred if the average current delivered to the load is less than
the current threshold. The method also includes, with the mode
control circuit, generating a mode control signal based in part on
a representation of a peak current received at the switch node from
the pull up component, and, with the controller operating the pull
up component and the pull down component in either of the first and
second operational modes based on the mode control signal.
BRIEF DESCRIPTION OF THE DRAWINGS
[0005] FIG. 1 is a schematic diagram of a converter circuit
configured to operate in either a pulse frequency modulation (PFM)
operational mode or a continuous conduction mode (CCM).
[0006] FIG. 2 is a schematic plot indicating time periods during
which the pull up component of the converter circuit of FIG. 1 is
on, and during which the pull down component of the converter
circuit of FIG. 1 is off.
[0007] FIG. 3 is a schematic plot indicating time periods during
which the pull up component of the converter circuit of FIG. 1 is
off, and during which the pull down component of the converter
circuit of FIG. 1 is on.
[0008] FIG. 4 is a schematic plot indicating time periods during
which the pull up component of the converter circuit of FIG. 1 is
off, and during which the pull down component of the converter
circuit of FIG. 1 is off.
[0009] FIG. 5 is a schematic plot of the current of the inductor of
the converter circuit of FIG. 1.
[0010] FIG. 6 is a schematic diagram of an embodiment of a mode
control circuit configured to control the operational mode of
converter circuit of FIG. 1 according to inductor current.
DETAILED DESCRIPTION OF THE INVENTION
[0011] Particular embodiments of the invention are illustrated
herein in conjunction with the drawings.
[0012] Various details are set forth herein as they relate to
certain embodiments. However, the invention can also be implemented
in ways which are different from those described herein.
Modifications can be made to the discussed embodiments by those
skilled in the art without departing from the invention. Therefore,
the invention is not limited to particular embodiments disclosed
herein.
[0013] FIG. 1 is a schematic diagram of a converter circuit 100
configured to operate in either a pulse frequency modulation (PFM)
operational mode or a continuous conduction mode (CCM). The
illustrated circuit is an example only. The principles and aspects
discussed herein may be applied to other convert circuits, as
understood by those of skill in the art.
[0014] Converter circuit 100 includes controller 110, pull up
component 120, pull down component 130, inductor 140, and capacitor
150.
[0015] Converter circuit 100 generates a substantially DC voltage
at output node OUT by controlling the switching operations of pull
up component 120 and pull down component 130. As understood by
those of skill in the art, pull up component 120 causes the voltage
at node SW to be substantially equal to the voltage at the positive
power supply, and turning off pull up component 120 causes the
voltage at node SW to decrease because of the continuous current in
inductor 140. Similarly, pull down component 130 causes the voltage
at node SW to be substantially equal to the voltage at the negative
power supply, and turning off pull down component 130 causes the
voltage at node SW to increase because of the continuous current in
inductor 140.
[0016] While operating in PFM mode, during each cycling period, the
controller 110 causes the voltage at node SW to be substantially or
about equal to the voltage of the positive power supply for a first
duration T1 and to be substantially or about equal the voltage of
the negative power supply for a second duration T2. During a third
duration T3, the voltage at node SW is not cause to be
substantially or about equal to the voltage of the positive power
supply or to the voltage of the negative power supply. The first
and second durations T1 and T2 have substantially fixed lengths,
and converter circuit 100 influences the voltage at output node OUT
by controlling and adjusting the third duration T3. For example, in
response to an indication that the voltage at output node OUT is
too low, controller 110 may decrease the third duration T3.
Likewise, in response to an indication that the voltage at output
node OUT is too high, controller 110 may increase the third
duration T3. The frequency associated with the cycling period is
therefore adjusted to cause the target voltage value at the output
node OUT.
[0017] While operating in CCM mode, during each cycling period, the
controller 110 causes the voltage at node SW to be substantially or
about equal to the voltage of the positive power supply for a first
duration T1 and to be substantially or about equal the voltage of
the negative power supply for a second duration T2. The sum of the
first duration T1 and the second duration T2 is fixed. Converter
circuit 100 influences the voltage at output node OUT by
controlling and adjusting the first and second durations T1 and T2,
without changing the sum of the first and second durations T1 and
T2. For example, in response to an indication that the voltage at
output node OUT is too low, controller 110 increases the first
duration T1 and decreases the second duration T2. Likewise, in
response to an indication that the voltage at output node OUT is
too high, controller 110 decreases the first duration T1 and
increases the second duration T2. Accordingly, the frequency
associated with the cycling period during CCM operation is fixed,
and the duty cycle is adjusted to cause the target voltage value at
the output node OUT.
[0018] The PFM operational mode may be preferentially used for
relatively low current load conditions, and the CCM operational
mode may be preferentially used for relatively high load
conditions. Accordingly, a measurement of load current can be used
to determine which mode the converter circuit 100 is to be operated
in.
[0019] Load current, however, may be difficult or impractical to
determine. Instead, average inductor current may be used as a proxy
for load current. And, as shown below, other circuit signals may be
used as an indication of average inductor current.
[0020] FIGS. 2-5 are schematic plots which are referenced to
establish that the other circuit signals may be used as an
indication of average inductor current using geometric principles.
In this example, the converter 100 is operating in PFM mode.
[0021] FIG. 2 is a schematic plot indicating time periods during
which pull up component 120 is on, and during which pull down
component 130 is off.
[0022] FIG. 3 is a schematic plot indicating time periods during
which pull up component 120 is off, and during which pull down
component 130 is on.
[0023] FIG. 4 is a schematic plot indicating time periods during
which pull up component 120 is off, and during which pull down
component 130 is off.
[0024] FIG. 5 is a schematic plot of the current of inductor 140,
as derived based on the various time periods indicated in FIGS. 2,
3, and 4.
[0025] During the time periods indicated in FIG. 2, during which
pull up component 120 is on and pull down component 130 is off, the
voltage at node SW is substantially or about equal to the voltage
at the positive power supply. Because the voltage at the output
node OUT may be considered DC, the current of inductor 140
increases substantially or about linearly from a minimum value or
zero to a peak value Ipeak.
[0026] During the time periods indicated in FIG. 3, during which
pull up component 120 is off and pull down component 130 is on, the
voltage at node SW is substantially or about equal to the voltage
at the negative power supply. Because the voltage at the output
node OUT may be considered DC, the current of inductor 140
decreases substantially or about linearly from the peak value Ipeak
to a minimum value or zero.
[0027] During the time periods indicated in FIG. 4, during which
pull up component 120 is off and pull down component 130 is off,
the voltage at node SW is substantially or about equal to the
voltage at the output node OUT. Therefore, the current of inductor
140 is a minimum value or zero.
[0028] Using geometric principles well understood in the art,
during the time periods indicated in FIG. 2, during which pull up
component 120 is on and pull down component 130 is off, the average
current of inductor 140 is equal to Ipeak/2. Similarly, during the
time periods indicated in FIG. 3, during which pull up component
120 is off and pull down component 130 is on, the average current
of inductor 140 is also equal to Ipeak/2. In addition, during the
time periods indicated in FIG. 4, during which pull up component
120 is off and pull down component 130 is off, the current of
inductor 140 is a minimum value or zero.
[0029] Accordingly, the average current Iavg of inductor 140 is
shown by:
Iavg=Ipeak/2.times.(TPUon+TPDon)/(TPUon+TPDon+Toff),
where TPUon is equal to the duration of the time periods indicated
in FIG. 2, during which pull up component 120 is on and pull down
component 130 is off, TPDon is equal to the duration of the time
periods indicated in FIG. 3, during which pull up component 120 is
off and pull down component 130 is on, and Toff is equal to the
duration of the time periods indicated in FIG. 4, during which pull
up component 120 is off and pull down component 130 is off.
[0030] FIG. 6 is a schematic diagram of an embodiment of a mode
control circuit 600 configured to control the operational mode of
converter circuit 100 of FIG. 1 according to inductor current. Mode
control circuit 600 may be implemented, for example, as part of the
controller 110.
[0031] Mode control circuit 600 includes current source Is1,
resistor RSW, switch TPUon, resistor R1, capacitor C1, buffer 610
and switch Ton, switch Toff, resistor R2, capacitor C2, and
comparator 620.
[0032] In some embodiments, current source Is1 has a current value
which corresponds with the current of the pull up component 120, as
determined and controlled by a current sensing circuit, such as any
current sensing and controlling circuit known in the art. For
example, current source Is1 may have a current value which is
determined by a scaled down version of pull up component 120, such
that the current of current source Is1 is substantially
proportional to the current of the pull up component 120.
[0033] In some embodiments, current source Is1 sources current
during the time periods indicated in FIG. 2, during which pull up
component 120 is on and pull down component 130 is off (TPUon), and
sources no current outside of those time periods. Accordingly, in
such embodiments, the mode control circuit 600 is configured to
control the operational mode of converter circuit 100 of FIG. 1
based on the inductor current during only a portion of each
inductor current cycle--those TPUon time periods indicated in FIG.
2.
[0034] Controller 110 also controls switch TPUon so that switch
TPUon is conductive during the time periods indicated in FIG. 2,
during which pull up component 120 is on and pull down component
130 is off (TPUon).
[0035] As a result, the voltage at node A corresponds with the
average current of inductor 140 during the TPUon time period,
where, as discussed above, the average current of inductor 140
during the TPUon time period is equal to Ipeak/2. As understood by
those of skill in the art, if the time periods indicated in FIG. 2,
during which pull up component 120 is on and pull down component
130 is off (TPUon), are increased, the voltage at node A likewise
increases. Similarly, if the time periods indicated in FIG. 2,
during which pull up component 120 is on and pull down component
130 is off (TPUon), are decreased, the voltage at node A likewise
decreases.
[0036] Controller 110 control switches Ton and Toff so that buffer
610 and switch Ton cause the voltage at node B to be equal to the
voltage at node A during the time periods indicated in FIGS. 2 and
3, during which either pull up component 120 is on or pull down
component 130 is on (Ton=TPUon+TPDon). In addition, controller 110
controls switches Ton and Toff so that switch Toff causes the
voltage at node B to be equal to the ground voltage during the time
periods indicated in FIG. 4, during which pull up component 120 is
off and pull down component 130 is off (Toff).
[0037] In addition, as understood by those of ordinary skill in the
art, because of the filter formed by resistor R2 and capacitor C2,
the voltage at node C is substantially equal to the average voltage
at node B, where the voltage at node B is substantially equal to
the voltage at node A times (TPUon+TPDon)/(TPUon+TPDon+Toff).
Therefore, because the voltage at node A corresponds with Ipeak/2,
the voltage at node C corresponds with
Ipeak/2.times.(TPUon+TPDon)/(TPUon+TPDon+Toff), which is equal to
the average current of the inductor 140.
[0038] Comparator 620 is configured to compare the voltage at node
C with a threshold voltage at node VTH and to generate a control
signal at node CTRL. In response to the voltage at node C being
less than the threshold voltage at node VTH (indicating that the
load current is less than a PFM-CCM current load threshold), the
comparator generates a control signal at node CTRL which causes
controller 110 to operate the pull up component 120 and the pull
down component 130 such that the converter functions in a pulse
frequency mode (PFM). In response to the voltage at node C being
greater than the threshold voltage at node VTH (indicating that the
load current is greater than a PFM-CCM current load threshold), the
comparator generates a control signal at node CTRL which causes
controller 110 to operate the pull up component 120 and the pull
down component 130 such that the converter functions in a
continuous conduction mode (CCM).
[0039] In some embodiments, comparator 620 is hysteretic, such that
the control signal at node CTRL does not switch between the two
mode control values in response to small variations in the voltage
at node C when the voltage at node C is near the threshold voltage
at node VTH.
[0040] As understood by those of ordinary skill in the art,
complementary switching devices, such as pull up component 120 and
pull down component 130 of FIG. 1, and such as switches Ton and
Toff of FIG. 6 may be operated so as to prevent both of the
complementary switching devices on simultaneously. For the
discussions herein, the brief period of time between one of the
complementary switching devices turning off and the other of the
complementary switching devices turning on (the dead time) is
considered to be in either of the adjacent time periods, as
understood by one of ordinary skill in the art.
[0041] In the example illustrated with reference to FIGS. 2-6, the
converter 100 is operating in PFM mode. As understood by those of
skill in the art, the mode controlling functionality of the mode
control circuit 600 will likewise properly control the operating
mode when the converter 100 is operating in CCM. As understood by
those of ordinary skill in the art, during CCM mode, there will be
no Toff time. Accordingly, switch Toff of FIG. 6 will be
continuously open, and switch Ton of FIG. 6 will be continuously
conductive.
[0042] Though the present invention is disclosed by way of specific
embodiments as described above, those embodiments are not intended
to limit the present invention. Based on the methods and the
technical aspects disclosed herein, variations and changes may be
made to the presented embodiments by those of skill in the art
without departing from the spirit and the scope of the present
invention.
* * * * *