U.S. patent application number 15/069900 was filed with the patent office on 2017-10-19 for wireless physiology monitor.
The applicant listed for this patent is Kenneth Margon. Invention is credited to Kenneth Margon.
Application Number | 20170300650 15/069900 |
Document ID | / |
Family ID | 42665893 |
Filed Date | 2017-10-19 |
United States Patent
Application |
20170300650 |
Kind Code |
A1 |
Margon; Kenneth |
October 19, 2017 |
Wireless Physiology Monitor
Abstract
The present invention provides a new non-invasive technique for
organ, e.g., heart and lung, monitoring. In at least one embodiment
of the invention, a subject is radiated with a non-harmful and
relatively low power electromagnetic source diagnostic signal
normally associated with a communications protocol such as, but not
limited to a version of the IEEE 802.11(x) family of protocols in
the 2.4, 3.6, or 5 GHz spectrum bands. After passing through the
patient, a return signal is acquired from the patient and compared
to the original source signal. The differences between the source
and modified signals are then analyzed to monitor the heart, e.g.,
measure heart rate and detect defects within the heart, and the
lung. For example, using Doppler Effect principles, heart rate and
motion can be measured from the differences in frequency, phase,
and/or wavelength between the source signal and the modified signal
reflected back from the heart moving within the patient.
Inventors: |
Margon; Kenneth; (Oakland,
CA) |
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Applicant: |
Name |
City |
State |
Country |
Type |
Margon; Kenneth |
Oakland |
CA |
US |
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|
Family ID: |
42665893 |
Appl. No.: |
15/069900 |
Filed: |
March 14, 2016 |
Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
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13838661 |
Mar 15, 2013 |
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15069900 |
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13247999 |
Sep 28, 2011 |
8994536 |
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13838661 |
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12712488 |
Feb 25, 2010 |
9035775 |
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13247999 |
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61155510 |
Feb 25, 2009 |
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61179605 |
May 19, 2009 |
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Current U.S.
Class: |
1/1 |
Current CPC
Class: |
A61B 5/113 20130101;
A61B 5/7278 20130101; A61B 5/7207 20130101; A61B 5/05 20130101;
A61B 5/0205 20130101; A61B 5/02405 20130101; A61B 5/725 20130101;
A61B 5/002 20130101; A61B 5/0816 20130101; G01S 7/003 20130101;
A61B 5/0507 20130101; G06F 19/3418 20130101; G16H 40/67 20180101;
A61B 5/0022 20130101; A61B 5/02028 20130101; G01S 13/56 20130101;
A61B 5/024 20130101 |
International
Class: |
G06F 19/00 20110101
G06F019/00; A61B 5/00 20060101 A61B005/00; A61B 5/02 20060101
A61B005/02; A61B 5/0205 20060101 A61B005/0205; A61B 5/00 20060101
A61B005/00 |
Claims
1.-15. (canceled)
16. A method for non-invasive physiology monitoring of a living
subject, the method implemented on a physiology monitoring device
and comprising the steps of: acquiring, at the physiology
monitoring device, a first modulated signal, wherein the first
modulated signal is generated by a source other than the physiology
monitoring device and has passed through tissue of the living
subject, combining, at the physiology monitoring device, the first
modulated signal with itself to form a combined signal, and
processing, at the physiology monitoring device, the combined
signal to monitor a physiological function of an organ of the
living subject.
17. The method of claim 16, wherein the organ is a moving organ and
the first modulated signal is subject to a Doppler effect due to
the moving organ of the living subject.
18. The method of claim 16, wherein the combined signal comprises a
bandwidth that is substantially double of the first modulated
signal.
19. The method of claim 16, wherein the physiological function is
selected from the group consisting of: heart rate; respiratory or
pulmonary rate; ventricular contraction; ventricular relaxation;
atrial contraction; atrial relaxation; arrhythmia; and a
combination thereof.
20. A non-invasive device for physiology monitoring of a living
subject comprising: a mixer for receiving a modulated signal from a
remote source and having passed through tissue of the living
subject, wherein an output signal is generated by the mixer,
wherein the output signal comprises the modulated signal combined
with itself, a filter coupled to the mixer for receiving the output
signal, and circuitry to determine and monitor a physiological
function of an organ of the living subject, wherein the circuitry
processes the output signal.
21. The device for physiology monitoring of claim 20, wherein the
output signal comprises a bandwidth that is substantially double of
the modulated signal.
22. The device for physiology monitoring of claim 20, wherein the
modulated signal is attributed to a Doppler effect reflected from
the organ of the living subject.
23. The device for physiology monitoring of claim 20, wherein the
circuitry comprises a digital signal processing unit to measure,
convert and analyze the output signal for determining and
monitoring a physiological function of an organ of the living
subject.
24. The device for physiology monitoring of claim 20, wherein the
filter comprises a low pass filter or a bandpass filter.
Description
CROSS-REFERENCE TO RELATED APPLICATIONS
[0001] This continuation-in-part application claims the benefit of
U.S. patent application Ser. No. 12/712,488 and PCT/US10/253325,
both filed on Feb. 25, 2010, and both entitled "Wireless Physiology
Monitor," which claim priority under 35 U.S.C. .sctn.119(e) to U.S.
Provisional Patent Application No. 61/155,510, entitled "WiFi OFDM
Modulated Carrier for Heart and Lung Monitoring," filed Feb. 25,
2009, and U.S. Provisional Patent Application No. 61/179,605,
entitled "Fall Detection and Heart/Lung Monitoring," filed May 19,
2009. The disclosures of the above-noted applications are
incorporated by reference herein in their entirety.
BACKGROUND OF THE INVENTION
1. Field of Invention
[0002] The present invention relates to physiological measurement
techniques and biotelemetry (i.e., medical telemetry), and more
particularly to a system, device, and method for heart and lung
monitoring using a modulated radio frequency (RF) carrier, such as
an IEEE 802.11(x) ("WiFi") orthogonal frequency-division
multiplexing (OFDM) signal, as a diagnostic signal.
2. Description of Related Art
[0003] Several technologies have been developed to help doctors and
medical professionals access, visualize, or learn more about a
patient's internal organs without having to undertake an invasive
medical procedure.
[0004] For example, an electrocardiogram (an "EKG") can be used to
determine information about a patient's heart. Electrical waves
generated by the heart are measured by electrodes that are placed
on the skin of a patient. The voltage between the electrodes is
displayed on a monitor for analysis of the patient's heart. EKGs
have several disadvantages, however. The electrodes must be
physically connected to the patient being monitored, which can be
bothersome to the patient, for the duration of the EKG test. In
addition, an EKG does not produce an image of the heart itself and
is not a direct measurement of the motion of the heart. Therefore,
the detected electrical characteristics are merely analogues of the
heart's motion.
[0005] Computer axial tomography ("CAT" or "CT") scans can be used
to generate three-dimensional (3D) images of a human body. CT
scanners emit a fan-shaped x-ray beam, which passes through a
patient's body before being detected by rotating source detectors.
Depending on the type of tissue the x-rays pass through, the x-rays
will be attenuated or will pass through unimpeded. The x-rays that
pass through the body are detected and used to generate an image of
the tissues exposed to the x-rays. Images of internal organs can
therefore be generated. Yet, CT scanners suffer from numerous
disadvantages. They are expensive, bulky and immobile, require
patients to remain generally immobile for extended periods of time
during the scanning, and expose patients to potentially harmful
x-rays.
[0006] Magnetic resonance imaging ("MRI") scanners can be used to
generate images of a human body. An MRI scanner uses magnetic
fields to align the nuclear magnetization of hydrogen atoms in the
body. The magnetization of these atoms is then altered to produce a
magnetic field, which is detected by the scanner and used to
generate an image. As with CT scanners, MRI scanners are expensive,
very large and immobile, and require patients to remain relatively
immobile during the procedure. Furthermore, MRI scanners cannot be
used by some people with metal implants.
SUMMARY OF THE INVENTION
[0007] The present invention overcomes these and other deficiencies
of the prior art by providing a Doppler based physiological
monitoring technique that implements modulated radio signals, such
as, but not limited to IEEE 802.11(x) modulated signals, as a
diagnostic signal. The differences between the source diagnostic
and the return signal (i.e., the modified signal after undergoing
modification as it passes through a patient) are then analyzed to
monitor essential and typical life processes, activities, and
functions such as, but not limited to measuring heart rate and
detecting heart defects, and respiratory rate. For example, using
Doppler Effect principles, heart rate and motion can be measured
from the differences in frequency, phase, and/or wavelength between
the source signal and the modified signal reflected back from the
heart moving within the patient.
[0008] In one embodiment, a method for physiology monitoring
comprises the steps of: communicating a first modulated signal
toward a subject, communicating a second modulated signal,
different from the first modulated signal, wherein the first
modulated signal and second modulated signal are combined to form a
third modulated signal, and processing the third modulated signal
to monitor a physiological function of an organ of the subject. The
second modulated signal may be attributed to a Doppler effect
reflected from the organ of the subject and the third modulated
signal may comprise a bandwidth that is substantially double of the
first and second modulated signals. Each modulated signal may
comprise a signal selected from the group consisting of: a
quadrature amplitude modulation with orthogonal frequency-division
multiplexing signal; a IEEE 802.11 compliant signal; a Bluetooth
compliant signal; a WiMax compliant signal; a CDMA signal; a GSM
signal; a 3GPP LTE signal; and a combination thereof. The
physiological function may be selected from the group consisting
of: heart rate; respiratory or pulmonary rate; ventricular
contraction; ventricular relaxation; atrial contraction; atrial
relaxation; arrhythmia; and a combination thereof. The method may
further comprise the step of detecting movement of the subject. The
movement may comprise a fall. The method may further comprise the
step of recording the monitored physiological function upon
detection of the movement.
[0009] In another embodiment, a system for physiology monitoring
comprises: a mixer for receiving a modulated signal from a fixed
source and an altered modulated signal from a subject, wherein an
output signal is generated by the mixer, a filter coupled to the
mixer for receiving the output signal, and a circuitry to determine
and monitor a physiological function of an organ of the subject.
The output signal may comprise a bandwidth that is substantially
double of the modulated signal and altered modulated signal. The
modulated signal may comprise a signal selected from the group
consisting of: a quadrature amplitude modulation with orthogonal
frequency-division multiplexing signal; a IEEE 802.11 compliant
signal; a Bluetooth compliant signal; a WiMax compliant signal; a
CDMA signal; a GSM signal; a 3GPP LTE signal; and a combination
thereof. The altered modulated signal may be attributed to a
Doppler effect reflected from the organ of the subject. The
circuitry may comprise a digital signal processing unit to measure,
convert and analyze the output signal for determining and
monitoring a physiological function of an organ of the subject. The
fixed source may be transmitted from public broadcasting wireless
stations. The filter may comprise a low pass filter or a bandpass
filter.
[0010] The foregoing, and other features and advantages of the
invention, will be apparent from the following, more particular
description of the preferred embodiments of the invention, the
accompanying drawings, and the claims.
BRIEF DESCRIPTION OF THE DRAWINGS
[0011] For a more complete understanding of the present invention,
the objects and advantages thereof, reference is now made to the
following descriptions taken in connection with the accompanying
drawings in which:
[0012] FIG. 1 illustrates a biotelemetry system according to an
embodiment of the invention;
[0013] FIG. 2 illustrates a physiological measurement process
according to an embodiment of the invention;
[0014] FIG. 3 illustrates the in-phase component of a base band
signal, a pulse-shaped signal before it modulates the carrier, and
a modulated carrier obtained by multiplying the pulse-shaped
base-band signal with carrier signal;
[0015] FIG. 4 illustrates the mixer output signal corrupted with
strong white noise;
[0016] FIG. 5 illustrates the output of Kalman filter applied on
the corrupted signal in FIG. 4;
[0017] FIG. 6 illustrates the detection of heart period in a Kalman
filtered signal;
[0018] FIG. 7 illustrates computed frequency shifts corresponding
to the Doppler effect;
[0019] FIG. 8 illustrates detection of curvature with convex shape
peaks;
[0020] FIG. 9 illustrates detection sharp convex curves;
[0021] FIG. 10 illustrates detection of concave curves;
[0022] FIG. 11 illustrates detection of sharp concave curves;
[0023] FIG. 12 illustrates envelopes in the down-converted signal
(in phase) due to Doppler effect;
[0024] FIG. 13 illustrates the product of the original baseband and
the down-converted signal;
[0025] FIG. 14 illustrates a baseband transmission signal;
[0026] FIG. 15 illustrates envelopes in the RF signal due to the
Doppler effect;
[0027] FIG. 16 illustrates the down converted signal;
[0028] FIG. 17 illustrates the product of the baseband return
signal and the original baseband transmission signal;
[0029] FIG. 18 illustrates the FFT of the product of baseband
transmission and the return signals;
[0030] FIG. 19 illustrates a high-level diagram of a Doppler
radar-based physiology monitoring device according to embodiment of
the invention;
[0031] FIG. 20 illustrates an RF diagram of a Doppler radar-based
physiology monitoring device according to embodiment of the
invention;
[0032] FIG. 21 illustrates a physiology monitoring system according
to an embodiment of the invention;
[0033] FIG. 22 illustrates an extraction of Doppler information
from RF signal using a mixer;
[0034] FIG. 23 illustrates a mixer output (in-phase component);
and
[0035] FIG. 24 illustrates an FFT analysis of the mixer output.
DETAILED DESCRIPTION OF EMBODIMENTS
[0036] Further features and advantages of the invention, as well as
the structure and operation of various embodiments of the
invention, are described in detail below with reference to the
accompanying FIGS. 1-24, wherein like reference numerals refer to
like elements. Although the embodiments of the invention are
described in the context of a radio frequency (RF) modulated
carrier, such as any one of the family of IEEE 802.11(x) protocols
(more commonly referred to as WiFi), one of ordinary skill in the
art readily appreciates that any type of modulated communication
signal can be implemented for the investigation of physiological
functions within a patient. For example, the inventive concepts
described herein may be implemented using any modulated or wireless
communications protocol such as, but not limited to Bluetooth,
WiMax (Worldwide Interoperability for Microwave Access), CDMA (Code
Division Multiple Access), GSM (Global System for Mobile
Communication), and 3GPP LTE (Long Term Evolution) or a signal that
is generated by a pseudo-random generator and then modulated as a
spread signal as in spread spectrum or Orthogonal
frequency-division multiplexing ("OFDM").
[0037] The present invention provides a new non-invasive technique
for physiology monitoring and assessment. In at least one
embodiment of the invention, a patient is subjected to a
non-harmful and relatively low power electromagnetic RF source
diagnostic signal normally associated with a communications
protocol such as, but not limited to a version of the IEEE
802.11(x) family of protocols in the 2.4, 3.6, or 5 GHz spectrum
bands. In lay terms, that source diagnostic signal undergoes
modification as it passes through the medium of the patient due to
absorption, reflection, scattering, etc., the precise physics of
which are readily understood by one of ordinary skill in the art.
After passing through the patient, the modified signal is acquired
and compared to the original source signal. The differences between
the source and modified signals are then analyzed to monitor
essential and typical life processes, activities, and functions
such as, but not limited to measuring heart rate and detecting
heart defects, and respiratory rate. For example, using Doppler
Effect principles, heart rate and motion can be measured from the
differences in frequency, phase, and/or wavelength between the
source signal and the modified signal reflected back from the heart
moving within the patient.
[0038] Although it is challenging to use a modulated carrier as the
diagnostic signal because of the jittery nature of a RF mixer
output, the effect of the base band signal (on the order of
Megahertz) on the carrier can be considered as pseudo random noise
when viewed in the low scale of heart beat frequency (on the order
of hertz). To overcome this challenge, the present invention
employs powerful filters to effectively eliminate this noise as
detailed below.
[0039] Unlike conventional Doppler-based radar systems, which
attempt to receive a signal from a quiet background, the present
invention is designed to extract deviation from randomness from a
background of random noise. This technique permits amplification of
the received signal even though it raises the noise floor. The
present invention optimizes the use of OFDM and exploits a
multipath environment.
[0040] In an embodiment of the invention, the modified signal
received from the patient goes through a quadrature demodulator
similar to using two separate mixers. The input to the local
oscillator is the original WiFi transmitted diagnostic signal (TX
signal). The input to the demodulator is from the signal received
back from the patient (the Doppler RX signal). The resulting output
is a spectrum consisting of the error between the TX and the RX
plus noise that is not related to the TX source. The TX signal is
much stronger than other signals that make up the received
spectrum. The Doppler radar technique of the present invention
removes the strongest signal from the spectrum, which reduces the
randomness of the received signal relative to the effects of the
perturbations of the spectrum due to heart movement and
respiration. This process also enhances the non-random
characteristics that represent the perturbations to the received
signal.
[0041] The fundamental concept employed in the present invention is
analogous to looking for a picture in a background of static noise
or finding a sign of intelligence in a sky of random radiation. The
more random the noise background is the more effective the present
invention is at looking for non-random changes in the received
signal. Another analogy is a boat traveling across a body of water
such as a lake. Whether the lake is completely calm or has a chop,
the boat deforms the waves. One can say that the chop is not truly
random, but looking at it from a distance it will have some visual
equilibrium that is disturbed by the boat, e.g., the boat's wake.
It is the disturbance in the equilibrium that the present invention
is measuring--the present invention measures both the rate of
change and the magnitude of the change. This allows for the
detection of speed, distance, and overall size information.
[0042] In an embodiment of the invention, a functioning WiFi signal
is used. The present invention measures heart rate and respiration
rate using a WiFi equipped device without interfering with the
normal communications and interaction between an Access Point (AP)
and the WiFi device. If no AP is present, then the WiFi device is
put into a 802.11 probing mode so that it transmits a signal. The
IEEE 802.11 protocol signal is time-division duplex (TDD) and
therefore intermittent, however it does not affect the overall
measurement. The present invention processes both I and Q channels
(abbreviation for respective in-phase and quadrature channels) at a
bandwidth of between 10 and 11 megahertz. Because of the high
bandwidth of the WiFi encoded information, it is not necessary to
process the signal to account for the quadrature amplitude
modulation (QAM) constellation as it is affected by the information
encoded in the signal. Baseband processors typically "whiten" the
data stream by limiting the number of consecutive "1s" or "0s" to
prevent DC offset.
[0043] Fundamentally, the present invention looks for perturbations
in a spectrum of random noise and then characterizes the
perturbations. The output from the demodulator is in the form of I
and Q signals--the reason for this is that since the present
invention is looking for information that approaches DC, both I and
Q signals are needed to maintain signal resolution near DC levels.
The I and Q channels are processed by two separate analog to
digital converters (ADCs) and then the spectrum is combined into
input filters based on Kalman equations or other filtering
algorithms such as, but not limited to modified particle filter
algorithms, the implementation of which is apparent to one of
ordinary skill in the art. The implementation of the Kalman
equations analyzes the spectrum of input signals in both the
frequency and time domains to enhance the non-random signals in the
input spectrum and suppress random signal in the input
spectrum.
[0044] It is clear that most of the noise in the input spectrum is
not truly random. In some ways randomness is in the eye of the
beholder. The appearance of randomness depends on the observer's
capabilities as in the example above where a lake has a chop on it.
It is really understood that the chop is driven by the wind and
flows in a certain direction. At a certain height above the lake
only the white caps are seen. At even a higher height all of the
white caps blend into a random flat pallet. A wake of the boat
moving through the waves changes the texture and color of this
pallet. Kalman equations are manipulated to look for perturbation
in the spectrum of frequencies input to the enhancer. The tools are
mathematical and don't depend on human senses. Other filters such
as an infinite impulse response (IIR) filter and/or a finite
impulse response (FIR) filter could be used, but processing would
require a much higher signal level. Other energy not originating
from the diagnostic Wifi signal, which is technically not Doppler,
also bounces off the organs and contributes to the energy evaluated
by the filters. The Doppler ends up working more like a pilot
signal so that the modeling can adjust dynamically and faster. The
key is that the Doppler effect is used as a guide and a dynamic
model of heart and lung signals is produced.
[0045] FIG. 1 illustrates a biotelemetry system 100 according to an
embodiment of the invention. The system 100 comprises a device 110
(e.g., sensing device) and a network node 120, which each comprise
a transmitter (not shown) and receiver (not shown) to communicate
with one another through communication signals 112 and 122, which
are preferably communication signals for transmission through a
wireless medium, although a wired medium may be implemented as
well. The network node 120 (e.g., access point) is also in
communication with a network (not shown) such as, but not limited
to a local network and/or the Internet. In operation, the device
110 transmits a source diagnostic signal 114 toward a patient 130.
A modified signal 134 is then obtained from the movement of a
targeted organ such as the heart of the patient 130 to the device
110. The device 110 includes circuitry (not shown) for measuring
the differences such as, but not limited to frequency, phase,
and/or wavelength differences between the source signal 114 and the
modified signal 134, and for computing and displaying physiological
functions such as, but not limited to heart and respiratory
rate.
[0046] In an alternative embodiment of the invention, the
diagnostic signal 114 may originate from background noise. For
example, rather than the device 110 transmitting the source
diagnostic signal 114, the diagnostic signal 114 originates from a
third-party source (not shown) such as, but not limited to an
access point. The device 110 detects the diagnostic signal 114 from
background noise and measures the characteristics of the diagnostic
signal 114 to perform the various physiological measurements noted
herein. In other words, if a modulated communication signal is
already present in the patient's environment, the device 110 may
use such as the diagnostic signal 114 without having to transmit
the diagnostic signal 114 itself
[0047] The device 110 can take any form factor. In one embodiment
of the invention, the device 110 is a standalone hand-held device
for optimum portability. For example, the device 110 may take the
form of a pendant, which may be worn around a patient's neck. In
another embodiment of the invention, the device 110 can be included
as a component within a multi-purpose mobile device such as, but
not limited to a cell phone, a laptop computer, a personal digital
assistant (PDA) or smart-phone, e.g., Blackberry, PALM, iPhone, and
the like. In yet another embodiment of the invention, the device
110 is included as a component within a relatively immobile device
such as a desktop computer or wireless router such as the network
node 120. Alternatively, the device 110 may be included as a part
of a larger apparatus such as a hospital bed, gurney, or any type
of equipment where a patient may be located or adjacent thereto.
The device 110 may further include a biometric sensor (not shown)
for identifying the individual using the device 110. For example,
the device 110 may optionally include a fingerprint scanner,
retinal scanner, or other biometric scanner, the identification and
implementation of which is apparent to one of ordinary skill in the
art.
[0048] FIG. 2 illustrates a physiological measurement process 200
according to an embodiment of the invention. The device 110 is
positioned (step 210) adjacent to an organ of the patient 130. The
diagnostic signal 114 is then transmitted (step 220) toward the
patient 130. For example, if the signal 114 is implemented
according to the IEEE 802.11(a) protocol, the signal is generally a
2.4 GHz signal that operates at no more than 40 mW. That diagnostic
signal is generated by an 802.11 compliant transmitter and needs no
special modification before being transmitted as the diagnostic
signal 114. Thus, in an embodiment of the invention, the device 110
is implementing the same 802.11 signal used for wireless
communications, e.g., signal 112, for the diagnostic signal
114.
[0049] Utilizing signals that meet such ubiquitous protocols not
only ensures that embodiments of the invention can be implemented
by numerous devices, such as cell phones and laptop computers, but
also permits reduced power consumption, since such protocols often
implement advanced power saving techniques. For instance, where the
signal is compliant with an 802.11 protocol, the signal 114 is
subject to power saving mechanisms ("PSMs"), the identification and
implementation of which are readily apparent to one of ordinary
skill in the art. In at least one embodiment of the invention, the
signal 114 is a "bursty signal," which reduces the power
consumption of the device 110 while also minimizing the amount of
electromagnetic radiation in the environment.
[0050] In an embodiment of the invention, the source signal 114 is
a modulated signal such as a QAM with OFDM signal, the
implementation of which are both well known to one of ordinary
skill in the art. These modulation methods have advantages over
using simpler modulation techniques such as quadrature phase-shift
keying (QPSK), binary phase-shift keying (BPSK), and
frequency-shift keying (FSK), which are nonetheless feasible for
implementation in the present invention. The more complex the
modulation of the source signal, the better background signal is
created for later processing. OFDM has the advantage of having
multiple carriers so that there are more strong multipath signals
received. For example, the use of OFDM allows embodiments of the
invention to be used in non-line of sight environments. For
example, in a disaster area such as an earthquake, a patient may be
buried under rubble and debris. Furthermore, it is relatively
easier to derive intelligence from a noisy radio environment using
such advanced modulation techniques. This occurs because
non-randomness elements from many multi-paths in a background of
random noise are more easily processed than non-random events over
a very narrow band.
[0051] The signal 114 is then returned (step 230) from the patient
as a modified signal 134. Different parts of the patient reflect
components of the signal 114 back in different ways. For example,
different bodily tissues, such as skin, lungs, heart, bones, etc.
reflect components of the signal back differently. This is because
the tissues have unique features due to varying material
constituents and Doppler effects caused by different movements from
the different tissues. For instance, a patient's lungs move
differently than the patient's heart, and therefore the components
of the signal reflected by the heart and lungs have different
unique features.
[0052] After the device 110 receives the components of the signal
134 back from the patient, the received signal is then fed to a
mixer, the implementation of which is apparent to one of ordinary
skill in the art. The mixer is also fed (step 240) the original
transmitted signal 114 as the other input, which is used to
determine frequency differences between the original transmitted
signal and the signal received by the device 110. The output of the
mixer is a superposition of signals representing frequency
differences between transmitted and received signals along with
other high frequency components. The output of the mixer is then
filtered (step 250) using advance mathematical techniques, which
are discussed in more detail below. These filtering techniques
require less processing than conventional filtering techniques, and
are used to extract pertinent information from the output,
depending on the specific physiological application.
[0053] In at least one embodiment of the invention, the output of
the filter(s) is fed (step 260) to a digital signal processing
(DSP) module, which extracts useful physiological information from
the output for analysis. For example, the DSP module extracts
frequency components corresponding to heartbeat and respiratory
rates and displays those frequency components on a display for
review. The physiological information gathered by the device 110
may be transmitted to a central monitoring unit (CMU) over the
Internet or other type of communications medium, the identification
and implementation of which is apparent to one of ordinary skill in
the art.
[0054] Referring to FIG. 3, consider the in-phase component of a
base band signal as shown in FIG. 3(a). The signal is pulse-shaped
as shown in FIG. 3(b) before being used to modulate the carrier.
Assuming a base band frequency of 10 MHz and a carrier frequency of
2.3 gigahertz, the modulated carrier obtained by multiplying the
pulse-shaped base-band signal with the carrier signal is shown in
FIG. 3(c) with a portion zoomed in as shown in FIG. 3(d). As seen
in FIG. 3(d), the amplitude of the modulated carrier fluctuates
with the base-band signal. Also, the frequency of the modulated
carrier is no longer equal to the carrier frequency. Rather the
frequency is spread over upper and lower side bands.
[0055] The modulated carrier can be used as a diagnostic signal 114
for Doppler based organ, e.g., heart and lung, monitoring. If the
two input signals to the RF mixer are
v.sub.1(t)=A.sub.1sin(2.pi.f.sub.1t+.phi..sub.1) and
v.sub.2(t)=A.sub.2sin(2.pi.f.sub.2t+.phi..sub.2),
the output of the mixer, disregarding constant phase, is
v 1 ( t ) v 2 ( t ) = A 1 A 2 2 [ cos ( 2 .pi. ( f 1 - f 2 ) t ) -
cos ( 2 .pi. ( f 1 + f 2 ) t ] ##EQU00001##
After filtering out the high frequency part, the mixer output
is,
v out = A 1 A 2 2 cos ( 2 .pi. ( f 1 - f 2 ) t ) ##EQU00002##
That is,
[0056] v out = A 1 A 2 2 cos ( .omega. 1 t - .omega. 2 t )
##EQU00003##
Thus, there will be fluctuations in the mixer output if there are
fluctuations in the amplitudes of the input signals or in the phase
difference. In the case of an OFDM modulated carrier, both types of
fluctuations are present. However, if viewed in the scale of heart
beat frequency, these high-frequency amplitude and phase
fluctuations can be considered as pseudo-random noise and can be
eliminated by a suitably designed filter, such as a Kalman filter,
as described below. Slowly varying frequency shifts (and thus phase
shifts) due to the Doppler effect of heart and lung movements
remain persistent and appear in the Kalman filtered output.
[0057] In an embodiment of the invention, the device 110 filters
the output of the mixer using one Kalman filter and five
correlation filters. A brief description about each of these
filters is given below. General implementation of a correlation
filter is apparent to one of ordinary skill in the art.
1. Kalman Filter
[0058] The Kalman filter is used to eliminate random noise from the
mixer output. A sample mixer output with strong white noise and the
Kalman filtered recovered signal are shown in FIGS. 4 and 5,
respectively.
2. Correlation Filters
[0059] Correlation filters are applied on rectified mixer output to
detect events in the heart cycle. In an exemplary embodiment of the
invention, five correlation filters are used and are described in
what follows.
2.1 Heart Period Detection
[0060] A correlation filter with appropriately chosen filter
coefficients is applied on the Kalman filtered signal as shown in
FIG. 5. This filter produces peak values when it is convolved with
lowest points of the signal. These lowest points correspond to
ventricular contraction of heart. Thus any two successive peak
values of the correlation filter marks a period--from one
ventricular contraction to subsequent ventricular contraction.
Correlation based heart period marking is shown in FIG. 6.
2.2 Events Detection
[0061] A set of four filters detects important events within the
heart period--namely atrial and ventricular contraction and
relaxation. Contraction is characterized by negative frequency
shift and relaxation by positive frequency shift. As the mixer
output provides cosine/sine of relative phase, pure phase
information is extracted from the output and differentiated to find
frequency shifts. These frequency shifts correspond to frequency
shifts due to the Doppler effect. FIG. 7 shows computed frequency
shifts. The four correlation filters are described below.
2.2.1 Convex Curve Detection
[0062] A correlation filter is designed for detection of curvature
with convex shape as shown in FIG. 8. Peak values in the filter
output correspond to the atrial and ventricular relaxation of
heart. (Note that atrial relaxation and ventricular relaxation
happen at overlapping times). FIG. 8(a) shows the correlation
template. FIG. 8(b) shows candidate curves in the frequency shift
signal.
2.2.2 Convex Sharp Curve Detection
[0063] A correlation filter is designed to detect sharp convex
curves as shown in FIG. 9. Peak values of this filter correspond to
gap between atrial and ventricular contraction peaks. FIG. 9(a)
shows the correlation template. FIG. 9(b) shows candidate sharp
curves in the frequency shift signal.
2.2.3 Concave Curve Detection
[0064] This correlation filter detects concave curves as shown in
FIG. 10. Peak values correspond to peak atrial contractions. FIG.
10(a) shows the correlation template. FIG. 10(b) shows candidate
concave curves in the frequency shift signal.
2.2.4 Concave Sharp Curve Detection
[0065] The last correlation filter detects sharp concave curves as
shown in FIG. 11. Peak values correspond to peak ventricular
contractions. FIG. 11(a) shows the correlation template. FIG. 11(b)
shows candidate sharp concave curves in the frequency shift
signal.
[0066] The techniques, systems, and methods described herein to
measure heart rhythm and respiration, including, for example, the
use of the Doppler effect to create a radar and post process it
with filters and then apply various state machines, can be extended
to many other applications. For example, in some embodiments, other
Arrhythmias, such as Fibrillation, Super Ventricular Tachycardia,
Ventricular Tachycardia, and Strength of the pulse, are detected to
help determine the efficiency of the heart. The breathing rate and
heart rate of a patient can also be determined. In other
embodiments, the techniques, systems, and methods are used in
applications unrelated to medicine, such as determining when
someone enters a room. As discussed above, the sensor device does
not have to be in direct physical contact with a patient.
Therefore, in some embodiments, the sensor device can be used to
determine nervousness, or excitement in a variety of situations
from security evaluations to reaction to stimulus, such as in
movies.
Experimental Results
[0067] Doppler shift has a significant effect on the carrier
frequency due to the relatively small wavelength of the carrier,
while its effects on baseband signal components are negligible due
to comparatively longer wavelengths. Because of the phase changes
of the carrier due to Doppler effect, periodic rotations are
noticed in the constellation diagram of the down-converted signal.
This is common physics shared by both OFDM and non-OFDM based
transmissions. By processing these periodic rotations, the movement
frequencies of the sources of the Doppler effect can be estimated.
In the present case, sources of the Doppler effect are moving
organs such as the lung and heart. The I and Q parts of the
down-converted signal exhibit envelops due to rotations as shown in
FIG. 12. If one takes a Fast Fourier Transfer (FFT) or similar
frequency component measurement of this down-converted signal, no
useful information can be achieved, because the signal is pseudo
noisy. In order to extract useful information from the envelopes,
multiply this with the original baseband signal. The result is
similar to the signal shown in FIG. 13, which is periodic with
alternating positive and negative envelops. Clear peaks at Doppler
shifts can be seen in the corresponding frequency spectrum. The
intermittent nature of WiFi transmission due to TDD does not affect
the frequency spectrum except slightly weakening the peaks at
Doppler shifts and introduction of a new peak at the TDD
frequency.
[0068] The WiFi RF transmission for Doppler effect based heartbeat
and lung rate detection was simulated as follows. The baseband TX
signal is shown in FIG. 14. The modulated carrier signal with very
low frequency envelopes due to Doppler effects of heart and lung
movements is shown in FIG. 15. Upon down-conversion of the RF
signal, envelops are seen in the in the baseband RX signal as shown
in FIG. 16. The down-converted signal is multiplied with the
original signal to obtain the result shown in FIG. 17. Finally FFT
is performed on the product signal shown in FIG. 17. The resulting
frequency spectrum is shown in FIG. 18. Although for mathematical
analysis, FFT has been used to estimate energy at different
frequencies, a Goertzel algorithm was used in the actual
experiment.
[0069] As is apparent, embodiments of the invention have several
advantages over current sensing technologies. Embodiments of the
invention are implemented using wireless technology, and therefore
do not require electrodes and physical human contact to function.
Because embodiments of the invention operate using standard
wireless communication protocols, inexpensive and readily available
devices such as cell phones and WiFi complaint devices can be used
to implement embodiments of the invention. Also, because the
filtering techniques are computationally efficient, real-time
and/or near real-time scanning and/or detection can take place.
[0070] The present invention can be used as a non-line of sight
motion detector. As an example, it can be used for an intrusion
alarm in a house or office--the range of detection being dependent
on the range of the modulated carrier, e.g., WiFi signal. If
implementing a microwave signal, it can go through walls and can
cover a much larger area than ultrasonic or infra-red detection.
Regardless of the type of source signal, the movement of organs of
a person within a respective detection range can be detected by the
present invention, thereby signaling the presence of that
person.
[0071] In a military application, the present invention can be used
to detect the movement of aircraft such as through a pass in the
mountains where there is no direct line of sight to the radar. It
can be used to detect stealth aircraft that diffuse radar signals
or absorb them since the equilibrium of the infinite multi-paths
will be disturbed by the aircraft moving.
[0072] In the medical area of heart and respiration monitoring, the
present invention is directly measuring the motion characteristics
of the hearts instead of inferring the motion of the heart from the
electrical signals shown on an EKG. The motion characteristics of
the heart as a result of the electrical signals in the heart have
been well documented; a reverse function can detect variance in the
expected movement in time, speed, and distance. A pseudo EKG can be
generated so that it can be compared to normal characteristics of
an EKG such as whether the heart is actually moving when expected
as well as providing the traditional measurements of the various
characteristics of an EKG. In this way it has some of the
characteristics of an EKG and an Echo Cardiogram.
[0073] FIG. 19 illustrates a high-level diagram of a Doppler
radar-based physiology monitoring device 1900 according to
embodiment of the invention. The physiology monitoring device 1900
comprises RF signal acquisition circuitry 1910, signal enhancement
circuitry 1920, cardiac and pulmonary analysis circuitry 1930, and
pseudo-EKG estimation circuitry 1940. The signal acquisition
circuitry 1910 comprises an RF Doppler-sensor 1915 for detecting
the diagnostic signal 114 and the modified signal 134 discussed
above. These signals are enhanced using the signal enhancement
circuitry 1920, which comprises a Kalman filter 1925. The enhanced
signal is fed into a frequency estimator 1932, such as an estimator
based on the Goertzel algorithm, the implementation of which is
apparent to one of ordinary skill in the art, which is a digital
signal processing technique for identifying frequency components of
a signal. The frequency estimator 1932 is used to determine the
average heartbeat and/or respiration rate of a suitably located
patient. The enhanced signal is also fed into a pattern detector
1934, which may include one or more correlation filters 1934, to
detect patterns associated with the movement of organs in the
patient such as, but not limited to a heart arrhythmia. Detection
circuitry 1936 is implemented to correlate the detected patterns
with certain conditions such as an arrhythmia. The frequency
estimator 1932, pattern detector 1934, and detection circuitry 1936
are included within the cardiac and pulmonary analysis circuitry
1930. The detection circuitry 1936 may be coupled to one or more
life signs or medical alarms (not shown). The pseudo-EKG estimation
circuitry 1940 comprises a motion-to-EKG mapper 1945 to generate a
pseudo EKG.
[0074] FIG. 20 illustrates an RF diagram of a Doppler radar-based
physiology monitoring device 2000 according to embodiment of the
invention. The physiology monitoring device 2000 comprises a WiFi
module 2005 to generate the diagnostic signal 114. The diagnostic
signal 114 is split by a splitter 2010 with one signal part being
transmitted into the surrounding area through a suitable antenna
2015. A receiving antenna 2020 is provided to detect the modified
signal 134. The detected modified signal 134 is processed through a
band-pass filter 2025, which attenuates unwanted frequencies, and a
low noise amplifier 2030, which amplifies the modified signal 134
after it leaves the band-pass filter 2025. The modified signal 134
and the other part of the diagnostic signal 114 are fed into a
quadrature demodulator 2040, the implementation of which is
apparent to one of ordinary skill in the art. The quadrature
demodulator 2040 recovers the I and Q channels, which are each
processed by a low-pass filter 2045I or 2045Q, a variable gain
amplifier 2050I or 2050Q, and an analog-to-digital converter 2055I
or 2055Q, respectively. The digital output of the converters 2055I
and 2055Q undergo further processing as noted above to determine
heart and respiratory rates, detect arrhythmias, etc.
[0075] FIG. 21 illustrates a physiology monitoring system 2100
according to an embodiment of the invention. The physiology
monitoring system 2100 comprises a hospital bed 2110 and a
physiology monitor 2120. The inclusion of the hospital bed 2110 is
exemplary only and can replaced with any type of medical equipment
where a patient can be located such as, but not limited to a
gurney, a stretcher, a trolley, an examination table, a back board
(sometimes referred to as a spine board), a cot or portable bed, an
infant bed or crib, an incubator, and various forms of furniture
and other medical devices. The physiology monitor 2120 is coupled
to the bed 2110. For example, in an embodiment of the invention,
the physiology monitor 2120 is disposed on the bottom of the bed
2110 as shown. Here, the physiology monitor 2120 is located on the
underneath side of the bed 2110 opposite of where a patient's
scapular, i.e., shoulder blade, would be located if the patient was
lying back-down on the bed 2110. This location is preferable as it
permits the physiology monitor 2120 to be placed close to the
patient's heart and lungs. In an embodiment of the invention, the
physiology monitor 2120 comprises a directional antenna (not shown)
to efficiently direct the diagnostic signal 114 to the patient and
width of the bed while limiting the range of the diagnostic signal
114, e.g., within two or three feet, to prevent interference by the
presence of other persons in the vicinity of the bed 2110.
[0076] In at least one embodiment of the invention, the device 110
comprises a means for motion detection (not shown) such as, but not
limited to a 3-axis accelerometer or the like, the identification
and implementation of which is apparent to one of ordinary skill in
the art. As used herein, "motion detection" generally refers to the
ability to sense whether a human has moved and if so, the direction
and magnitude of such movement at any given instant in time. This
includes "fall detection," which refers to a patient such as an
elderly user of the device 110 having fallen or moved suddenly and
perhaps harmfully due to, for example, an accident or syncope,
which is a partial or complete loss of consciousness and posture.
Falls, syncope, and the associated complications are among the most
serious problems that face the elderly population. The most common
underlying causes and risk factors for falls include muscle
weakness, gait and balance problems, visual impairment, cognitive
impairment, depression, functional decline, and particular
medications (especially in the presence of environmental hazards).
Studies have identified the relative risks for these factors that
enable a fairly accurate prediction of who is at high risk for
falls and what areas to target for falls-prevention activity.
Certain studies have shown that 64 percent of patients with
recurrent syncope sustained an arrhythmia at the time of their
sudden loss of consciousness.
[0077] In operation, once a fall or other irregular movement is
detected by the accelerometer, the device 110 begins monitoring and
preferably recording (either locally or remotely by a CMU) various
functions of the patient's heart and lungs as detailed above. In
other words, a fall may trigger the operation of the device 110
according to an embodiment of the invention. The physiological data
gathered by the device 110 can be transmitted in real-time to CMU
to convey the data as well as the occurrence of the fall itself to
a medical provider or health care professional. In another
embodiment of the invention, the device 110 includes a button that
a user can press to activate monitoring of physiological
functions.
[0078] In another embodiment of the invention, the device 110
(including accelerometer) is implemented in connection with another
medical data acquisition device such as, but not limited to a
weight scale or a blood pressure monitor to collect and transmit a
range of medical data associated with the patient using the device
110 and transmit such to a remote server, e.g., CMU. In the case of
a weight scale, the weight scale comprises a vibration source for
emitting a vibration at a predetermined frequency. When a patient
wearing the device 110 steps onto the weight scale, the vibration
is transmitted from the weight scale, through the patient, and to
the device 110, which the accelerometer detects. The device 110
then measures the particular frequency of vibration and transmits
this information to the CMU, which is also in communication with
the scale as well. Based on the measured frequency, the CMU is able
to know that the same patient wearing the device 110 is also the
same patient being weighed and is thus able to store both weight
and the physiology data measured by the device 110 into a record
corresponding to the particular patient. One of ordinary skill in
the art recognizes that the use of a scale or blood pressure
monitor is exemplary only and that other medical data acquisition
devices may be implemented with vibration sources to achieve the
same objective of recording various medical information.
[0079] The following example is provided to better illustrate the
above acquisition technique. The weight scale receives a magnitude
of a vibration frequency from the CMU of 57 Hz. The patient wearing
the device 110 steps on the scale, which vibrates at 57 Hz at some
point. The device 110 detects the vibration of 57 Hz and transmits
this to the CMU. The CMU then knows that the particular scale,
which vibrated at 57 Hz, is weighing the same patient weighing the
device 110, which detected the 57 Hz. Both weight data and
physiology data acquired by the device 110 are associated with one
another and the corresponding patient--this information can then be
stored into a respective electronic medical record associated with
the patient. If the device 110 further includes a biometric sensor,
the CMU is able to acquire the respective biometric information
sensed and determine the identity of the patient if the appropriate
corresponding biometric record of that patient already exists.
[0080] At some point afterward, the scale switches to a different
vibration frequency such as 61 Hz. A second patient (using the same
device 110 as the first patient was using or a different device
110) then steps on the scale and is vibrated at 61 Hz, which is
detected by the accelerometer of the worn device 110. The CMU is
then able to determine that the second patient's weight from the
scale should be associated with the information acquired from the
device 110 being worn by the patient at that time. One of ordinary
skill in the art recognizes that numerous permutations exist on the
above technique for acquiring medical data from other medical
devices used in connection with the device 110. For example, as
described above, the medical device, e.g., scale, blood pressure
monitor, oximeter, breath analyzer, etc., may request the CMU to
identify a particular vibration frequency. In another example, the
medical device may select a vibration frequency and transmit the
magnitude of the known frequency to the CMU rather than requesting
it. The medical device may change vibration frequencies at
predetermined intervals--after every 30 or 60 seconds the medical
device switches to a new frequency.
[0081] In a military scenario, the device 110 may be included as
part of a larger physiologic monitoring system for monitoring the
health and situation of a soldier in the field. For example, a
number of accelerometers are positioned in the uniform, garment, or
shielding worn by a soldier along with the device 110 to monitor
movement and vital signs. The accelerometers are positioned at key
points, the identification of which is apparent to one of ordinary
skill in the art, of the soldier's body such as feet, knees, waist,
hands, elbows, shoulders, and head, or any combination thereof. The
accelerometers along with the device 110 are in communication with
a CMU. The CMU is thus able to determine the soldier's motion
(e.g., running, walking, stationary, direction, and location),
mortality, limb loss, consciousness, tremors due to shock and
extreme environmental conditions, fatigue (as a function of
posture, gate, and other vital signs), physical and concussive
impact, weapons discharge, injury via gate analysis, and full body
motion including arms and legs with stride analysis and/or
visualization. The accelerometers may be sewn/integrated into the
soldier's clothing, belts, helmets, or boots, and can be connected
via a wired bus in the clothing or can communicate wirelessly to a
gateway located in the belt. The gateway may store the acquired
data for later inspection (such as a "black box") or may transmit
the acquired data to the CMU in real-time or near real-time. The
device 110 may be worn as a pendant around the neck of the
soldier--thereby, replacing the function of a soldier's
conventional "dog-tag."
[0082] Military applications have special considerations. For
example, any physiological monitoring system including the device
110 must not be detectable by the enemy. Accordingly, any radio
diagnostic frequency emitted by the device 110 must have a
relatively low power, e.g., can only be detected within a small
radius, e.g., a 2-3 foot sphere, around the solider. In some
scenarios, the diagnostic signal of the device 110 should not be a
widely-known protocol such as IEEE 802.11(x) in places where such a
signal would not normally exist, e.g., in desert conditions. In
other scenarios, this may be less of a concern in areas where the
same protocols are normally implemented, e.g., in urban
environments. In an alternative embodiment, the diagnostic
radiation appears as random background noise to an observer.
Moreover, any communication from the device 110 to a CMU should use
secure military communications, the identification and
implementation of which is apparent to one of ordinary skill in the
art, to prevent detection of the soldier or unauthorized access to
the data being communicated. As noted above, the present invention
is able to harness the secure military communication signal
(implemented between the device 110 and the CMU) as the diagnostic
signal.
[0083] The physiology monitoring techniques disclosed herein may
also be used as a means to identify particular individuals as every
person's heart has a unique data signature that is detectable. In
other words, the device 110 is capable of capturing the unique
elements of heart movement to create a unique identification. For
example, the frequency and period of ventricular contractions (as
well as particular arrhythmias) are unique to each individual. Such
an identification technique can be combined with the vibration
sensor for positive identification for access control
purposes--e.g., the user of the device 110 may place their hand on
a wall plate that vibrates at a particular frequency to gain access
to a secure area.
[0084] In another embodiment, improving the overall system 100 for
detecting a signal from a diagnostic RF source reflected from slow
moving objects may be achieved by enhancing the bandwidth of the
signal prior to the DSP module step (step 260) of FIG. 2.
Furthermore, novel statistical integration techniques may be
applied to the reflected signal to improve the effectiveness of
differentiating the Doppler effect on the reflected signal from
other signals.
[0085] In one medical related implementation, as shown in the
system 100 of FIG. 1, a transmitted diagnostic signal S.sub.T 114
generated from a device 110 is incident upon a first part of a
patient 130 such as, for example, the patient's chest and a
different portion of the signal S.sub.T is reflected from other
bodily tissues in motion of the patient, including but not limited
to the chest, lung and heart surfaces. The reflected signal 134 is
received at an RX antenna of the device 110.
[0086] In general, reflected signals may undergo a Doppler effect
as characterized by a decrease or increase in a received frequency
from an electromagnetic radiation source, as compared to a
frequency emitted from the original source signal. Although the
Doppler effect from fast moving objects are detectable by
conventional means such as optical and radar systems, in a slow
moving object, such as in the heart or lung, generate low bandwidth
signals, making detection of the Doppler effect of the slow moving
object a challenge due to low bandwidth spread. FIGS. 22-24
describe a system and method for increasing the detection of the
Doppler effect of a slow moving object.
[0087] FIG. 22 illustrates one implementation of a system 2200 for
improving the Doppler shift associated with a slow moving object.
The system 2200 comprises a mixer 2201 and a low pass filter LPF
2205, where one input I.sub.LO to the mixer 2201 may be any
band-limited RF signal and the other input I.sub.s to the mixer
2200 may be the same RF signal but shifted due to the Doppler
Effect. The mixer output 2203 is a superposition of low frequency
signals near baseband frequency and high frequency signals centered
near 2f.sub.c, where f.sub.c is a carrier frequency generated by a
device 110 as shown in FIG. 1. The high frequency components may be
suppressed by a low pass filter to extract a portion of the signal
information 2207. Using statistical sampling methods, the signal
information may be refined, evaluated and correlated to the
physiological response of the patient's organs in real-time.
[0088] The above diagnostic signal in system 2200 may be
implemented with a variety of wireless protocols, including WiFi,
WiMAX, and OFDM. These protocols have beneficial features for
detecting slow moving objects, including sensitivity to the Doppler
shift of the received signal and substantially even levels of
energy distributed across the entire band. When the object in
consideration moves toward the receiver, the frequency of the
signal components throughout the bandwidth increases due to Doppler
shift. As such, the full bandwidth of signal moves toward higher
frequency. At a particular frequency point, if the energy versus
frequency distribution is a decreasing function, then this Doppler
shift will increase energy at the frequency in consideration.
However, at an earlier frequency, the energy will decrease. On the
average, it is expected that energy distribution at the edge will
be a decreasing function. In that case, it is expected that the
energy at the band-edge will increase, when the object moves toward
the receiver. When the object moves away from the receiver, the
situation is reversed. Thus, the energy is expected to decrease at
the band edge when the object moves away from the receiver.
[0089] One advantage of the system 2200 is that the bandwidth of
the output of the low pass filter is double the original baseband
bandwidth. In other words, if the bandwidth of I.sub.s as well as
of I.sub.LO is W then the bandwidth of low pass filter is 2W. Thus,
an object, such as the heart, having a rate of 2 Hz may be doubled
to 4 Hz, wherein 4 Hz may be further doubled to 8 Hz, 8 Hz to 16
Hz, and so on. The bandwidth of the signal may be characterized as
a signal having a center frequency f.sub.c, a lower band edge
frequency f.sub.l, and an upper band edge f.sub.h, where the
bandwidth is defined by f.sub.h-f.sub.l. Useful Doppler effect
information (i.e., heart rate, lung expansion, etc.) typically
occurs along the band edges of a signal when estimating Doppler
shift from the change in the energy distribution across OFDM
bandwidth due to object movement. As mentioned earlier, when the
object in consideration moves toward the receiver, the full
bandwidth of signal moves toward higher frequency and vice-versa.
OFDM signal is quite evenly distributed across the bandwidth.
Therefore, change in the energy at frequencies within the bandwidth
may not be appreciable. However, it is expected that energy
distribution at the edge is a decreasing function of frequency.
Therefore, change in energy due to Doppler shift would be
appreciable around the band-edge. As bandwidth increases, the band
edge frequencies (f.sub.h and f.sub.l) are moved away from the
center frequency f.sub.c, making the Doppler effect due to the
relative motion of the heart, for example, easier to detect in the
system 2200 than in other conventional systems.
[0090] The mixer 2201 doubles the bandwidth and implements
equations 1-6 below. The mixer 2201 multiplies the signals
appearing at the input ports I.sub.s and I.sub.LO, which is
necessary to realize the equations. Suppose the original baseband
signal is
S b = k a k cos ( 2 .pi. f k t ) + b k sin ( 2 .pi. f k t ) ( 1 )
##EQU00004##
Then for a carrier signal
S.sub.c=a.sub.c cos(2.pi.f.sub.ct), (2)
the transmitted RF signal is
S T = S c S b = k a c a k cos ( 2 .pi. f c t ) cos ( 2 .pi. f k t )
+ a c b k cos ( 2 .pi. f c t ) sin ( 2 .pi. f k t )
##EQU00005##
On simplification, we obtain,
S T = k [ A k { cos ( 2 .pi. ( f c + f k ) t ) + cos ( 2 .pi. ( f c
- f k ) t ) } + B k { sin ( 2 .pi. ( f c + f k ) t ) - sin ( 2 .pi.
( f c - f k ) t ) } ] Where , A k = a c a k 2 and B k = a c b k 2 .
( 3 ) ##EQU00006##
[0091] For mathematical simplicity, it is assumed that the received
signal originates from a single moving object. If the instantaneous
Doppler shift is f.sub.d.sup.(k +)(t) for the frequency
(f.sub.c+f.sub.k) and f.sub.d.sup.(k -)(t) for the frequency
(f.sub.c-f.sub.k), then, ignoring the overall phase, the received
signal may be given by,
S R = k [ A k { cos ( 2 .pi. ( f c + f k + f d ( k + ) ) t ) + cos
( 2 .pi. ( f c - f k + f d ( k - ) ) t ) } + B k { sin ( 2 .pi. ( f
c + f k + f d ( k + ) ) t ) - sin ( 2 .pi. ( f c - f k + f d ( k -
) ) t ) } ] ( 4 ) ##EQU00007##
Now, if S.sub.T and S.sub.R are fed into inputs I.sub.LO and
I.sub.s, respectively, of the mixer, the output of the mixer
O.sub.M can be given by,
O M = S R .times. S T = k l [ A kl { cos ( 2 .pi. ( 2 f c + f k + f
l + f d ( d + ) ) t ) + cos ( 2 .pi. ( f k - f l + f d ( d + ) ) t
) + cos ( 2 .pi. ( 2 f c + f k - f l + f d ( d + ) ) t ) + cos ( 2
.pi. ( f k + f 1 + f d ( d + ) ) t ) + cos ( 2 .pi. ( 2 f c - f k +
f l + f d ( d - ) ) t ) + cos ( 2 .pi. ( - f k - f l + f d ( d - )
) t ) + cos ( 2 .pi. ( 2 f c - f k - f l + f d ( d - ) ) t ) + cos
( 2 .pi. ( - f k + f l + f d ( d - ) ) t ) } + B kl { sin ( 2 .pi.
( 2 f c + f k + f l + f d ( d + ) ) t ) - sin ( 2 .pi. ( 2 f c + f
k - f l + f d ( d + ) ) t ) + } + C kl { cos ( 2 .pi. ( f k - f l +
f d ( d + ) ) t ) - cos ( 2 .pi. ( 2 f c + f k + f l + f d ( d + )
) t ) - cos ( 2 .pi. ( f k + f l + f d ( d + ) ) t ) + cos ( 2 .pi.
( 2 f c + f k - f l + f d ( d + ) ) t ) - cos ( 2 .pi. ( - f k - f
l + f d ( d - ) ) t ) + cos ( 2 .pi. ( 2 f c - f k + f l + f d ( d
- ) ) t + cos ( 2 .pi. ( - f k + f l + f d ( d - ) ) t ) - cos ( 2
.pi. ( 2 f c - f k - f l + f d ( d - ) ) t ) } ] ( 5 )
##EQU00008##
[0092] Upon eliminating high frequency components via a low pass
filter, for example, the resulting output mixer signal O.sub.M may
be further simplified as,
O M = k l [ A kl { cos ( 2 .pi. ( f k + f l + f d ( d + ) ) t ) +
cos ( 2 .pi. ( f k - f l + f d ( d + ) ) t ) + cos ( 2 .pi. ( - f k
- f l + f d ( d + ) ) t ) + cos ( 2 .pi. ( - f k + f 1 + f d ( d +
) ) t ) } + B kl { } + C kl { cos ( 2 .pi. ( f k - f l + f d ( d +
) ) t ) - cos ( 2 .pi. ( f k + f l + f d ( d + ) ) t ) - cos ( 2
.pi. ( - f k - f l + f d ( d + ) ) t ) + cos ( 2 .pi. ( - f k - f l
+ f d ( d + ) ) t ) } ] ( 6 ) ##EQU00009##
In Eq. (6), 0.ltoreq.f.sub.k.ltoreq.W and 0.ltoreq.f.sub.l.ltoreq.W
. Assuming that f.sub.d.sup.(k+)<<W and
f.sub.d.sup.(k-)<<W, the bandwidth of O.sub.M is determined
by solving for max(|f.sub.k+f.sub.l|)-min(|f.sub.k-f.sub.l|), which
is 2W-0=2W, or double the original baseband bandwidth.
[0093] A zooming function can be accomplished using multiple mixers
in a cascaded system creating a Doppler microscope. Input to the
cascaded system has an embedded Doppler frequency shift f.sub.D for
a received signal reflected from a heart or lung. f.sub.D can be
input into an I.sub.s and I.sub.LO of a first mixer. The output of
the first mixer is doubled (2f.sub.D) and can be passed through a
bandpass filter. 2f.sub.D can be input into an I.sub.s and I.sub.LO
of a second mixer, outputting 4f.sub.D. The process can be repeated
(e.g., a third mixer would output 8f.sub.D). Frequency zooming is
advantageous in handling very low frequency components of the
signal, for example heartbeat and respiration rates having nominal
values of 1.2 Hz and 0.3 Hz respectively. Frequency zooming can be
used to convert slowly varying signal to signal with higher
frequencies. For example, the frequency of the respiration signal
(0.3 Hz) can be converted to 0.3*2=0.6 Hz, or 0.3*4=1.2 Hz or to
higher frequencies, 0.3*2.sup.n, n=1, 2, 3 . . . .
[0094] FIGS. 23-24 illustrate empirical results of a frequency
spectrum response supporting a 2.times. increase of the original
baseband bandwidth, using a WiFi transmitted diagnostic and Doppler
received signals. In FIG. 23, a spectral response at the mixer
output, as indicated by amplitudes of the in-phase component from
as a function of various measured samples, is produced by feeding a
WiFi TX transmitted signal I.sub.LO and a Doppler RX received
signal I.sub.s inputs to the mixer. This experimental result may be
used as a basis for comparison to support a 2.times. increase in
baseband bandwidth. Specifically, FIG. 22 shows a snapshot of mixer
output. A portion of the signal is zoomed in FIG. 23. An FFT
analysis of the signal in FIG. 23 is given in FIG. 24. As an ADC
sampling frequency of 40 MHz, maximum frequency component in the
ADC output is 20 MHz. Therefore, no frequency higher than 20 MHz is
expected in the FFT output. This is indeed reflected in FIG. 24
(energies at frequencies from 20 MHz to 40 MHz simply being
reflection of the energies at 0 MHz to 20 MHz). However, it is
noticed that non-zero energy components are present throughout the
band from0 to 20 MHz. As the original bandwidths at ports I.sub.s
and I.sub.LO are 11 MHz, FIG. 24 clearly indicates that the
bandwidth at the mixer output is double the bandwidths at the
inputs. It is readily understood by one of ordinary skill in the
art that other diagnostic signal other than WiFi may be used to
support this increase in bandwidth.
[0095] FIG. 24 illustrates a frequency analysis plot of the signal
in which the mixer output is sampled at 40 MHz. Due to limited
sampling frequency, FFT cannot show frequency more than 20 MHz. As
evidenced in FIG. 24, the signal contains non-zero frequency
components up to 20 MHz. One of the properties of FFT is that for a
real signal, FFT components at frequencies more than half of the
sampling frequency are simply reflections of components at lower
frequencies. As seen in FIG. 24, FFT components at frequencies more
than 20 MHz are reflections of low frequency components. For
example, energy at 30 MHz is equal to that at (40-30)=10 MHz,
energy at 35 MHz is equal to that at (40-35)=5 MHz, and so on.
Thus, although FIG. 24 shows non-zero values for frequencies 0 to
40 MHz, energies only at frequencies 0 to 20 MHz can be estimated
from this figure. In contrast, if the I.sub.LO input of the mixer
is connected to a center frequency pure tone, both in-phase (I) and
out-of-phase (Q) components contain non-zero frequency components
only up to 11 MHz. In the pure tone case, the signal drops
significantly after 8.3 MHz. The drop at around 8.3 MHz, instead of
11 MHz, is due to guard bands. Thus, a comparison of these
empirical results indicates that the frequency at the mixer output
is double of the baseband bandwidth for the input configuration
shown in FIG. 22.
[0096] Therefore, in order to receive the mixer output signal
intact, bandpass filters for both in-phase (I) and out-of-phase (Q)
components are configured to have a minimum bandwidth of 22 MHz,
having each component centered near the center frequency. Here,
where I.sub.LO is fed with a WiFi TX signal, each of I and Q has 22
MHz bandwidth. In the normal case, that is where input to I.sub.LO
is pure tone, each of I and Q outputs has a bandwidth of 11 MHz. In
practice, two 11 MHz bandpass filters may be implemented, one for
the in-phase component and the other for the out-of-phase
component.
[0097] Next, a novel method of extracting and enhancing pertinent
physiological information from a reflected wireless signal is
provided using statistical integration methods. The tasks of
extracting and enhancing pertinent physiological information from a
reflected wireless signal using statistical integration methods are
performed by DSP 260 of FIG. 2. In this approach, a portion of a
diagnostic transmitted signal such as WiFi, for example, is
reflected from different body organs of the patient in test. When
the reflected signal is received and fed to the mixer 2201 as the
I.sub.s input along with the original TX signal as the I.sub.LO
input, the mixer output signal 2203 generally depends on following
three parameters.
[0098] P1. Product of amplitudes of I.sub.s and I.sub.LO.
[0099] P2. Phase difference between I.sub.s and I.sub.LO inputs due
to difference in effective path lengths for I.sub.s and I.sub.LO
inputs from TX antenna to the mixer. While the fixed path from TX
to I.sub.LO comprises mainly of PCB traces, the path from TX to
I.sub.s incorporates air and human tissues.
[0100] P3. Phase difference between I.sub.s and I.sub.LO inputs due
to Doppler Effect of heart, lung and other body parts in motion.
Frequency of the I.sub.s signal may be instantaneously changed due
to the Doppler Effect. These frequency shifts, integrated over
time, contribute to phase difference.
[0101] Each parameter has certain characteristics tied to a
function of the input signals. Parameter P1 is the product of the
amplitudes of I.sub.s and I.sub.LO. The signal I.sub.LO is the WiFi
TX signal which is basically a carrier signal (pure tone) modulated
by baseband signal. Although the carrier signal has constant
amplitude, the modulated signal I.sub.LO amplitude varies at the
baseband frequency. Again, the signal I.sub.s is basically I.sub.LO
further modulated by medium and moving objects in the propagation
path. Therefore, the parameter P1 varies at the baseband
frequency.
[0102] The second parameter (P2) can be assumed nearly constant for
a particular setup. In the present context, the relevant part of
the setup consists of the RF propagation path .PHI..sub.LO between
the WiFi TX and I.sub.LO and the RF propagation path .PHI..sub.s
between WiFi TX and I.sub.s. Parameter P2 is the phase difference
between inputs at I.sub.s and I.sub.LO ports. .PHI..sub.LO involves
RF shielded wires and PCB traces and is therefore nearly constant.
The overall path length of .PHI..sub.s is also nearly constant if
the semi-periodic path difference due movements of vital organs is
not considered (movements of vital organs are taken into
consideration in parameter P3 ). Therefore parameter P2 is nearly
constant so long as the pendant is not displaced from the chest.
The third parameter is semi-periodic at very low frequencies (e.g.,
near 1.2 Hz for heart movement and 0.3 Hz for lung movement).
Sampling of the mixer output signal 2203 may be performed at a high
frequency (e.g. 40 MHz) and integrated over sufficiently large
number of samples (e.g. 80,000 samples) so that the high frequency
fluctuation in mixer output signal 2203 due to the first parameter
(P1) is reduced, and edge signals for the third parameter (P3)
attributed to the slow varying pattern due to third parameter (P3)
are increased, resulting in improved detection by the DSP module
260. The detection is performed by the DSP 260. As the input to DSP
260 is improved because of integration over a large number of
samples, the output of the DSP 260 is also enhanced.
[0103] Using this method, two mixers in quadrature phase
relationship are used. Although the in-phase (I) or out-of-phase
(Q) outputs of the mixer 2201 may be integrated directly as an
attempt to isolate the third parameter (P3), a problem arises as
explained below.
[0104] The I mixer output, for example, can be given by
o.sub.I=A.sub.sA.sub.LO cos(.DELTA..phi.) (7)
[0105] where, .DELTA..phi. is the phase difference between the
I.sub.s and I.sub.LO inputs. The cosine function increases with
increase in .DELTA..phi. for some ranges of .DELTA..phi., while it
decreases with increase in .DELTA..phi. for other ranges as
follows.
0 .ltoreq. .DELTA. .PHI. .ltoreq. .pi. 2 : cos ( .DELTA..PHI. )
decreases with increase in .DELTA..PHI. . .pi. 2 .ltoreq. .DELTA.
.PHI. .ltoreq. .pi. : cos ( .DELTA..PHI. ) decreases with increase
in .DELTA..PHI. . .pi. .ltoreq. .DELTA. .PHI. .ltoreq. 3 .pi. 2 :
cos ( .DELTA..PHI. ) increases with increase in .DELTA..PHI. . 3
.pi. 2 .ltoreq. .DELTA. .PHI. .ltoreq. 2 .pi. : cos ( .DELTA..PHI.
) increases with increase in .DELTA..PHI. . ##EQU00010##
[0106] Thus for the same velocity of heart or lung, there may be
increase or decrease in mixer output depending on the range of
.DELTA..phi.. For example, when the lung is expanding, mixer output
may increase or decrease depending on the distance of the lung
surface. More importantly, as WiFi baseband signal changes fast
from symbol to symbol, range of .DELTA..phi. switches from quadrant
to quadrant because of path difference between the mixer inputs. To
see the effect of this fast switching, let us denote
cos(.DELTA..phi.) when the moving object is at its neutral position
as cos(.DELTA..phi..sup.(0)) and that when the moving object is at
position x(t) as cos(.DELTA..phi..sup.(x)) . The polarity of
deviation,
d.sub.x=cos(.DELTA..phi..sup.(x))-cos(.DELTA..phi..sup.(0)),
toggles very fast, because of the high frequency of the baseband
signal. Therefore, if we integrate a large number of samples, the
integrated value of d.sub.x due to Doppler Effect will be a random
number close to zero, resulting in loss of poor detection of the P3
parameter.
[0107] This problem can be solved, if the I and Q mixer output 2203
pair are first converted from Cartesian coordinate to polar
coordinate ((R, .phi.) and integration is performed over .phi.,
defining deviation in .phi. as
d.sub..phi.=.DELTA..phi..sup.(x)-.DELTA..phi..sup.(0). Although
.phi. may vary from quadrant to quadrant during fast change of
baseband signal, the deviation d.sub..phi. persistently increases
when the moving object gets closer to the sensor. Similarly,
d.sub..phi. persistently decreases when the object gets away from
the sensor. Thus when integration is performed over .phi., the
effect of frequent varying of .phi. from one quadrant to another is
made smooth, while the persistent contribution of Doppler Effect,
d.sub..phi. are enhanced, and thus improving signal detection
associated with the patient's heart, lung and other body parts in
motion.
[0108] Although the embodiment presented hereinabove is implemented
in a medical application, the system 2200 and method for the
detection of slow moving objects may be applied to other
applications. Some of these applications include theft prevention
through detection of thief movement, window flip detection,
etc.
[0109] In another embodiment, the system 2200 may operate with the
transmitted diagnostic signal supplied by an external RF source
which is not provided by system 100 or system 2200. Ambient RF
energy sources transmitted from public broadcasting wireless
stations such as WiFi hotspots, cellular towers, satellites, or
public RF transmission stations may be used as input signals to the
system 2200, where the Doppler effect from reflected objects are
measured directly. Publicly broadcasted wireless signals received
by the system 2200 include but are not limited to WiFi, WiMAX, GPS,
and OFDM. By eliminating the diagnostic transmitter portion of the
system, a compact passive physiological monitoring device may be
constructed at a lower cost.
[0110] Although the invention has been described in the context of
a human patient, the inventive concepts described herein can be
used on any type of living subject including animals. For example,
the inventive concepts can be implemented in veterinarian
applications where medical information is sought for animals such
as dogs and cats. The device 110 may implemented as part of a
collar or harness worn by the animal
[0111] In accordance with some embodiments, the various aspects
described above may be implemented using computer programming or
engineering techniques including computer software, firmware,
hardware or any combination or subset thereof. Any resulting
program, having computer-readable code means, may be embodied or
provided within one or more computer-readable media, thereby making
a computer program product, i.e., an article of manufacture,
according to the invention. The computer readable media may be, for
instance, a fixed (hard) drive, diskette, optical disk, magnetic
tape, semiconductor memory such as read-only memory (ROM), etc., or
any transmitting/receiving medium such as the Internet or other
communication network or link. The article of manufacture
containing the computer code may be made and/or used by executing
the code directly from one medium, by copying the code from one
medium to another medium, or by transmitting the code over a
network. In addition, one of ordinary skill in the art of computer
science will be able to combine the software created as described
with appropriate general purpose or special purpose computer
hardware, Personal Digital Assistant (PDA) hardware, cellular
telephone hardware or other electronic hardware to create a
computer system or computer sub-system embodying the method of the
invention. One of ordinary skill in the art will understand that
the various embodiments can also be implemented on circuitry,
which, as defined herein, can be any combination of general purpose
hardware, software, firmware, and/or special purpose hardware,
including, but not limited to, a central processing unit, FPGA,
ASIC or other known devices.
[0112] The invention has been described herein using specific
embodiments for the purposes of illustration only. It will be
readily apparent to one of ordinary skill in the art, however, that
the principles of the invention can be embodied in other ways.
Therefore, the invention should not be regarded as being limited in
scope to the specific embodiments disclosed herein.
* * * * *