U.S. patent application number 14/700961 was filed with the patent office on 2015-08-20 for systems and methods to control color and brightness of lighting devices.
The applicant listed for this patent is Hunter Industries, Inc.. Invention is credited to Peter John Woytowitz.
Application Number | 20150237700 14/700961 |
Document ID | / |
Family ID | 53799386 |
Filed Date | 2015-08-20 |
United States Patent
Application |
20150237700 |
Kind Code |
A1 |
Woytowitz; Peter John |
August 20, 2015 |
SYSTEMS AND METHODS TO CONTROL COLOR AND BRIGHTNESS OF LIGHTING
DEVICES
Abstract
Systems and methods are provided to control the color and
brightness of LED lighting. A control signal generator generates a
hybrid control signal using pulse width modulation and analog
control to drive an LED driver with increased resolution to
maintain color mixing while adjusting brightness of the LED
lighting.
Inventors: |
Woytowitz; Peter John; (San
Diego, CA) |
|
Applicant: |
Name |
City |
State |
Country |
Type |
Hunter Industries, Inc. |
San Marcos |
CA |
US |
|
|
Family ID: |
53799386 |
Appl. No.: |
14/700961 |
Filed: |
April 30, 2015 |
Related U.S. Patent Documents
|
|
|
|
|
|
Application
Number |
Filing Date |
Patent Number |
|
|
13750815 |
Jan 25, 2013 |
|
|
|
14700961 |
|
|
|
|
13230665 |
Sep 12, 2011 |
8710770 |
|
|
13750815 |
|
|
|
|
61511934 |
Jul 26, 2011 |
|
|
|
Current U.S.
Class: |
315/307 |
Current CPC
Class: |
H05B 47/19 20200101;
H05B 45/37 20200101; H05B 45/20 20200101; Y02B 20/30 20130101; Y02B
20/341 20130101; H05B 47/185 20200101; H05B 45/50 20200101 |
International
Class: |
H05B 33/08 20060101
H05B033/08 |
Claims
1. A method to increase a resolution of intensity control in a
lighting module comprising an LED, the method comprising:
determining, at the lighting module, an intensity level for the
LED; generating a first control signal that when coupled to an LED
driver results in a first drive signal having a first resolution of
intensity control, the first control signal based at least in part
on the intensity level; generating a second control signal that
when coupled to the LED driver results in a second drive signal
having a second resolution of intensity control, the second control
signal based at least in part on the intensity level; combining the
first and second control signals to create a hybrid control signal;
and coupling the hybrid control signal to the LED driver to produce
a third drive signal having a third resolution of intensity
control, wherein the third resolution of intensity control results
in a greater resolution of intensity control than the first
resolution of intensity control and the second resolution of
intensity control.
2. The method of claim 1 wherein the hybrid control signal
comprises a pulse width modulation (PWM) signal having an amplitude
and a duty cycle.
3. The method of claim 2 wherein the amplitude is based at least in
part on the first control signal and the duty cycle is based at
least in part on the second control signal.
4. The method of claim 2 wherein creating the hybrid control signal
comprises converting a digital value that is responsive to the
amplitude to an analog signal, and modulating the analog signal
according to the duty cycle.
5. The method of claim 2 wherein creating the hybrid control signal
comprises filtering with a low-pass filter a first PWM waveform, a
duty cycle of the first PWM waveform based on the amplitude and the
filtered first PWM waveform approximating an analog signal having
the amplitude, and modulating the analog signal with a second PWM
waveform having the duty cycle of the hybrid control signal.
6. The method of claim 2 wherein creating the hybrid control signal
comprises generating a digital value for predetermined intervals
and converting the digital value to an analog value during the
predetermined intervals, the digital value based on the amplitude
and the predetermined intervals based on the duty cycle.
7. The method of claim 2 wherein creating the hybrid control signal
comprises averaging a PWM waveform, a duty cycle of the PWM
waveform based on the amplitude and the averaged PWM waveform
approximating an analog signal having the amplitude, and turning
the PWM waveform ON and OFF at predetermined times, the
predetermined times based on the duty cycle of the hybrid control
signal.
8. The method of claim 7 wherein averaging the PWM waveform
comprises filtering the PWM waveform with a low-pass filter.
9. The method of claim 8 wherein components of the low-pass filter
are selected so that a frequency of the PWM waveform is outside of
the pass band of the low-pass filter and a frequency of the hybrid
control signal is within the pass band.
10. A lighting module comprising: an LED configured to illuminate
when driven by an output of an LED driver circuit; a processor
configured to determine an intensity level for the LED, the
processor further configured to generate a first control signal
that when coupled to the LED driver circuit results in a first
drive signal having a first resolution of intensity control and to
generate a second control signal that when coupled to the LED
driver circuit results in a second drive signal having a second
resolution of intensity control, the first and second control
signals based at least in part on the intensity level; and a hybrid
control signal generator configured to combine the first and second
control signals to create a hybrid control signal, the LED driver
circuit configured to receive the hybrid control signal and to
output a third drive signal having a third resolution of intensity
control, wherein the third resolution of intensity control results
in a greater resolution of intensity control than the first
resolution of intensity control and the second resolution of
intensity control.
11. The lighting module of claim 10 wherein the hybrid control
signal comprises a pulse width modulation (PWM) signal having an
amplitude and a duty cycle.
12. The lighting module of claim 11 wherein the amplitude is based
at least in part on the first control signal and the duty cycle is
based at least in part on the second control signal.
13. The lighting module of claim 11 wherein the hybrid control
signal generator comprises a microcontroller configured to generate
a digital value responsive to the amplitude and a PWM waveform
responsive to the duty cycle, and a digital to analog converter
(DAC) configured to enable a conversion of the digital value to an
analog signal according to the PWM waveform.
14. The lighting module of claim 11 wherein the hybrid control
signal generator comprises a microcontroller configured to generate
a digital value responsive to the amplitude and a PWM waveform
responsive to the duty cycle, a digital to analog converter (DAC)
configured to convert the digital value to an analog signal, and a
switch configured to modulate the analog signal according to PWM
waveform.
15. The lighting module of claim 11 wherein the hybrid control
signal generator comprises a microcontroller configured to generate
a first PWM waveform, a low-pass filter configured to average the
first PWM waveform to approximate an analog signal having the
amplitude, the microcontroller further configured to generate a
second PWM waveform having the duty cycle, the hybrid control
signal generator further comprising a switch configured to modulate
the averaged first PWM waveform with the second PWM waveform.
16. The lighting module of claim 11 wherein the hybrid control
signal generator comprises a microcontroller configured to generate
a digital value for predetermined intervals and a digital to analog
converter (DAC) configured to convert the digital value to an
analog signal during the predetermined intervals, the digital value
based on the amplitude and the predetermined intervals based on the
duty cycle.
17. A method to control color and brightness of a lighting module
comprising one or more LEDs, the method comprising: decoding data
associated with a user-selected color and a user-selected
brightness, the decoded data comprising a color ratio and an
intensity level; determining, for each LED of the one or more LEDs,
a corresponding amplitude and a corresponding duty cycle of a pulse
width modulation (PWM) signal in response to the color ratio at the
intensity level; and generating, for each LED of the one or more
LEDs, a corresponding hybrid control signal having the
corresponding amplitude and the corresponding duty cycle, each LED
of the one or more LEDs further associated with a corresponding
hysteretic LED driver; wherein the corresponding hybrid control
signal comprises an analog component and a digital component, and
permits the color ratio at varying intensities to be controlled
with a level of resolution that is greater than the level of
resolution provided by the analog component alone and the level of
resolution provided by the digital component alone.
18. The method of claim 17 wherein the analog component comprises
the corresponding amplitude and the digital component comprises the
corresponding duty cycle.
19. The method of claim 17 further comprising receiving at the
lighting module a data encoded power signal over a two-wire
communication network, the data encoded power signal comprising the
data associated with the user-selected color and the user-selected
brightness for the lighting module, wherein the data encoded power
signal forms a sinusoidal waveform between zero crossings.
20. The method of claim 17 further comprising providing, for each
LED of the one or more LEDs, the corresponding hybrid control
signal to the corresponding hysteretic LED driver to generate a
corresponding output signal based on the corresponding hybrid
control signal, and driving each LED of the one or more LEDs with
the corresponding output signal to cause the lighting module to
illuminate in response to the user-selected color and the
user-selected brightness.
Description
RELATED APPLICATIONS
[0001] Any and all applications for which a foreign or domestic
priority claim is identified in the Application Data Sheet as filed
with the present application are hereby incorporated by reference
under 37 CFR 1.57.
BACKGROUND
[0002] Traditionally, outdoor lighting systems include a plurality
of lamps connected to a transformer. There may be one or more
"legs" or sets of wires coming out of the transformer, each
connected to at least one light. A timer box connects to the
transformer. The user programs the on/off times and all of the
lights energize in unison, such that all lights connected to a
particular transformer turn ON or OFF together regardless of which
leg they are on.
[0003] Some manufacturers provide lighting systems with addressable
lighting modules. The timer box of the traditional lighting system
is replaced with a lighting controller that supplies the lighting
modules with a separate power and data signal. Each lighting module
has an address and is independently addressable by the lighting
controller via the data signal. These networked lighting systems
provide the lighting modules with two sets of wires instead of the
one or more legs. One set provides a power signal to illuminate the
lamps or LEDs and a second set provides the lighting module with a
data signal. The user programs the lighting controller to turn-on
and turn-off lights at individual addresses such that a single
light can turn-on or turn-off independently of the other lights in
the network, when, for example, the data signal carries the address
of a particular light.
[0004] In some instances, the power signal is the output of a low
voltage power transformer, which is connected directly to the
lighting modules to power the lamps or LEDs. For example, a primary
AC to 12 VAC transformer accepts 120 VAC and outputs 12 VAC, where
the 12 VAC power signal electrically couples directly to the
lighting modules and powers the lamps/LEDs.
[0005] In other instances, the power signal is the output of a DC
switching power supply. For example, a DC switching power supply
accepts 120 VAC and outputs 12 VDC, where the 12 VDC power signal
electrically couples directly to the lighting modules and powers
the lamps/LEDs.
[0006] Other manufacturers of addressable lighting systems send
power and data to the lighting modules on the primary power wires.
The user programs the lighting controller to turn-on and turn-off
lights at individual addresses such that a single light can turn-on
or turn-off independently of the other lights in the network. In
some instances, these lighting systems use a high frequency
carrier, such as 125 kHz, and superimpose this signal on the power
line. This approach requires large inductors, or complex Digital
Signal Processors (DSPs) to decode the data contained in the
carrier. One such commercially available system is the X10 control
system originally developed by Pico Electronics of Glenrothes,
Scotland.
[0007] In other instances, these lighting systems amplify the data
signal to the level that can be used to power the lighting modules.
For example, a PWM stepper motor driver chip can amplify a 0 volt
to 5 volt transistor-transistor logic (TTL) data signal to positive
24 volts to reflect a logical one and negative 24 volts to reflect
a logical zero. The amplified data signal electrically couples to
the lighting module, where the voltage is sufficient to supply
power to the lamps/LEDs while maintaining the logical data values
of the data stream.
SUMMARY
[0008] Based on the foregoing, each of the present manufacturing
solutions suffers from a variety of drawbacks. In the context of
individually addressable lighting networks with low voltage power
transformers, they often employ special wiring or cabling. In
particular, one wire and its return are needed for electrical
power, while a second wire path comprising two or more wires is
needed for data. For example, using a low voltage power transformer
directly coupled to the lamps/LEDs to supply power prevents the
data from being carried on the same power lines and, thus requires
the two sets of wires. Accordingly, the owner of an existing set of
lights must take significant effort to rewire in order to have a
digitally controlled lighting environment.
[0009] In the context of lighting networks using a single wire for
a power and a data signal, problems can occur when using a
switching power supply to supply power to the lighting modules.
Switching power supplies are inefficient when compared to a
well-designed core and coil power transformer. The inefficient
transformation of the primary AC power to a power waveform usable
by the lighting modules creates heat. The heat, in turn, creates
the need for a large enclosure to prevent the lighting controller
circuitry from overheating. For example, a 300 watt switching power
supply that has an efficiency of 85% wastes 45 watts in heat.
[0010] In contrast, in an embodiment of the present disclosure, a
full-wave rectifier coupled to a bridge circuit provides a polarity
controlled, sinusoidal power signal to power a plurality of
lighting modules. The rectifier and bridge circuit include MOSFETs
and each MOSFET has an integral body diode. When the full-wave
rectifier MOSFETs are enabled at the appropriate point in time,
such as when the body diodes would be conducting, they create a
very low-loss switch. For example, for a MOSFET having a resistance
of approximately 1 milliohm when it is enabled, conducting 25
amperes needed to power the plurality of lighting modules would
lose approximately 25 millivolts of the signal. The corresponding
power lost to heat is approximately 0.625 watts. In contrast, a
standard rectifier would drop approximately 0.7 volts and dissipate
approximately 17.5 watts.
[0011] In embodiments of the present disclosure using the output of
a primary AC to 12 VAC 300 watt transformer to feed the circuitry,
preferably the power lost to heat in the circuitry is less than
approximately 2.0%. More preferably, the power lost to heat is
between approximately 1% and approximately 2%. Even more
preferably, the power lost to heat is between approximately 0.2%
and approximately 1%, and most preferably, the power lost to heat
is less than approximately 0.2%.
[0012] In other embodiments, the advantages of the rectifier and
bridge of the present disclosure creating a very low-loss switch
can be viewed from the drop in voltage across the rectifier. A
transformer in the full-wave rectifier receives the primary AC
signal and transforms the primary AC signal into a secondary AC
power waveform. The full-wave rectifier coupled to a bridge circuit
provides a polarity controlled, sinusoidal power signal to power a
plurality of lighting modules. Preferably, the power waveform
current is more than approximately 4 amperes and the power waveform
voltage drop across the rectifier is less than approximately 0.2
volts and at full load the voltage drop across the rectifier, from
the output of the transformer to the output of the rectifier, is
approximately 25 millivolts. In another embodiment, the voltage
drop across the rectifier is more preferably between approximately
0.1 volts and approximately 0.2 volts, yet more preferably between
approximately 0 volts and approximately 0.1 volts, and most
preferably between approximately 5 millivolts and approximately 30
millivolts. In yet other embodiments, the power waveform current is
more preferably more than 10 amperes, yet more preferably more than
50 amperes, and most preferably more than 75 amperes. One basis for
the above ratings is the wattage used for outdoor lighting systems.
Typical systems are about 60 watts or higher. If such power
requirements should be reduced due to technology advances, such as,
for example, power requirements for lighting sources, or the like,
one of ordinary skill will understand from the disclosure herein
that the forgoing ranges may also change accordingly.
[0013] The low-loss full-wave rectified power waveform from the
full-wave rectifier is communicated to the inputs of the bridge
circuit. The bridge circuit outputs the full-wave rectified
waveform with either a positive polarity or a negative polarity,
thus having the ability to reconstruct the original sinusoidal
output of the transformer, or alter its polarity to send data. The
control signal from a processor in the lighting controller couples
to the MOSFET drivers of the bridge circuit. The control signal
enables certain of the gates in the bridge circuit at certain
points in time to encode a data signal by varying the polarity of
the power waveform.
[0014] In one embodiment, the control signal enables certain of the
gates in the bridge circuit when the data is a logical 1-bit and
others of the gates when the data is a logical 0-bit. This, in
turn, causes the bridge circuit to output the positive polarity
rectified waveform when the data stream is a 1-bit and causes the
bridge circuit to output a negative polarity rectified waveform
when the data stream is a 0-bit. In other embodiments, the bridge
circuit outputs the negative polarity rectified power signal when
the data is a 1-bit and outputs the positive polarity rectified
power signal when the data is a 0-bit.
[0015] In one embodiment, the lighting system includes a controller
having a data signal including data bits. The data bits have a
first state and a second state for sending commands and addresses
to at least one lighting module.
[0016] The lighting system further includes a MOSFET full-wave
rectifier circuit for receiving a 12 VAC RMS power signal having
first and second power waveforms and rectifying the 12 VAC RMS
power signal. The MOSFET full-wave rectifier includes a first
MOSFET coupled in series with a second MOSFET and a third MOSFET
coupled in series with a fourth MOSFET where the series combination
of the first and second MOSFETs electrically couple in parallel
with the series combination of the third and fourth MOSFETs. Each
MOSFET is associated with a gate signal and the gate signals
electrically couple to an output of a comparator comparing the
first and second power waveforms, via driver circuitry. The gates
associated with the second and third MOSFETs are enabled when the
first power waveform is greater than the second power waveform and
the gates associated with the first and fourth MOSFETs are enabled
when the second power waveform is greater than the first power
waveform.
[0017] The lighting system further includes a MOSFET bridge circuit
for receiving the full-wave rectified waveform and providing a
two-wire data/power signal to the at least one lighting module. The
MOSFET bridge circuit includes a fifth MOSFET coupled in series
with a sixth MOSFET and a seventh MOSFET coupled in series to an
eighth MOSFET, where the series combination of the fifth and sixth
MOSFETs couple in parallel with the series combination of the
seventh and eighth MOSFETs. Each MOSFET is associated with a gate
signal and the gate signals electrically coupled to the control
signal. The gates associated with the sixth and seventh MOSFETs are
enabled when the control signal is in the first state and the gates
associated with the fifth and eighth MOSFETs are enabled when the
control signal is in the second state, such that the MOSFET bridge
circuit outputs the rectified waveform having a positive polarity
when the control signal is in the first state and outputs the
rectified waveform having a negative polarity when the control
signal is in the second state. The two-wire data/power signal
includes the positive and negative polarity rectified waveforms
corresponding to the state of the control signal.
[0018] In another embodiment, a lighting system includes a
controller having a data signal including data bits. The data bits
have a first state and a second state for sending commands and
addresses to at least one lighting module.
[0019] The lighting system further includes a MOSFET
full-wave/bridge circuit for receiving a 12 VAC RMS power signal
having first and second waveforms, rectifying the 12 VAC RMS power
signal and providing a two-wire data/power signal to the at least
one lighting module. The first and second power waveforms are
provided by a transformer having a center tap. The MOSFET
full-wave/bridge circuit includes a first MOSFET coupled in series
with a second MOSFET and a third MOSFET electrically coupled in
series with a fourth MOSFET where the series combination of the
first and second MOSFETs electrically couple in parallel with the
series combination of the third and fourth MOSFETs. Each MOSFET is
associated with a gate signal and the gate signals electrically
couple to the control signal. The gates associated with the third
and fourth MOSFETs are enabled when the control signal is in the
first state and the gates associated with the first and fourth
MOSFETs are enabled when the control signal is in the second state,
such that the MOSFET full-wave/bridge circuit outputs the rectified
waveform having a positive polarity when the control signal is in
the first state and outputs the rectified waveform having a
negative polarity when the control signal is in the second state.
The two-wire data/power signal includes the positive and negative
polarity rectified waveforms corresponding to the state of the
control signal.
[0020] In another aspect, systems and methods directed toward a
user interface panel are disclosed. In an embodiment, a lighting
controller includes an operator interface panel, which allows
operator input to program the timing, dimming/brightness, color,
and zones of the lighting system. In one embodiment, the user
enters a chronologic schedule including a lighting group, a time,
an intensity, a color, and the like. The program queues the user
entered events and transmits the commands at the scheduled
times.
[0021] With respect to color, in an embodiment, the colors are
assigned a number and the user enters the number associated with
the desired color. In another embodiment, the user designs a custom
color by inputting the red, green and blue percentages. In some
cases, a percentage of white can also be mixed with the red, green,
and blue. Other user interfaces may include a color wheel with
pointer sections, a scrollable list or color palette, or the like.
The lighting controller then sends commands to the lighting modules
with the user specified color percentages to create the custom
color. In another embodiment, the lighting controller includes a
thin film transistor liquid crystal display (TFT LCD) or the like,
to display the color associated with the color number or the custom
color. In another embodiment, the light controller may have a small
red/green/blue LED, separate from the display, that can be driven
with the proper percentages to mimic the color emitted by the
lighting fixtures.
[0022] In one embodiment, the user has the ability through the
lighting controller to set on or off times around an event, such as
create a lighting event around sunrise or sunset. For example, the
user could use dusk as a reference time and have a zone of lights
turn on at dusk minus two hours or dusk plus two hours. In one
embodiment, the lighting controller includes a photocell and
determines events such as dusk or dawn through the input from the
photocell. In another embodiment, the user enters latitude and
longitude information for his location. The lighting controller
looks up or calculates the astronomical events based on the entered
location values. In yet another embodiment, the lighting controller
displays a map and the user indicates on the map his location. The
lighting controller automatically displays the latitude and
longitude and determines the astronomical events based on the
displayed location values.
[0023] In another aspect, systems and methods relating to
commanding the lighting modules through a remote device are
disclosed. In another embodiment, the lighting system further
includes a remote device and a wireless receiver. The remote device
permits the user to adjust the lighting while in the illuminated
area as an alternative to using the user interface panel in the
lighting controller. The remote interacts with the lighting module
via an optical or other link and interacts with the lighting
controller via the receiver to allow the user to mix the color
coefficients, assign lights to zones, control brightness, control
on/off, or the like. The lighting controller receives the user
requests through a wired or other connection to the receiver and
sends commands to the lighting module through the two wire
data/power path. For example, from the user's point of view, he
points the remote at the desired lighting module and selects the
change zone command. After a short time period, the selected
lighting module is a member of a different lighting zone.
[0024] Certain embodiments relate to a lighting system including a
lighting controller and at least one lighting module having an
address and including a light emitting diode (LED). The LED is
configured to transmit optically the address or other status
information of the lighting module by turning on when transmitting
a 1-bit and turning off when transmitting a 0-bit in the address.
The lighting controller electrically couples to the lighting module
through a two-wire path carrying a power/data signal.
[0025] The lighting system further includes a remote device
including an optical sensor and an RF transmitter. The optical
sensor is configured to receive the address from the lighting
module, and user request from the user interface of the remote
device. The RF transmitter is configured to transmit an RF signal
corresponding to the address and the request.
[0026] The lighting system further includes a wireless receiver
electrically coupled to the lighting controller and configured to
receive the RF transmission from the remote device. The wireless
receiver down converts the RF transmission to a baseband signal
corresponding to the address and request. The wireless receiver is
further configured to electrically send the baseband signal
corresponding to the address and the request to the lighting
controller.
[0027] The lighting controller encodes a command corresponding to
the user's request for the at least one lighting module associated
with the address onto the power/data signal.
[0028] Other aspects relate to a method to increase a resolution of
intensity control in a lighting module comprising an LED. The
method comprises determining, at the lighting module, an intensity
level for the LED, generating a first control signal that when
coupled to an LED driver results in a first drive signal having a
first resolution of intensity control, where the first control
signal is based at least in part on the intensity level, generating
a second control signal that when coupled to the LED driver results
in a second drive signal having a second resolution of intensity
control, where the second control signal is based at least in part
on the intensity level, combining the first and second control
signals to create a hybrid control signal, and coupling the hybrid
control signal to the LED driver to produce a third drive signal
having a third resolution of intensity control, where the third
resolution of intensity control results in a greater resolution of
intensity control than the first resolution of intensity control
and the second resolution of intensity control.
[0029] In an embodiment, the hybrid control signal comprises a PWM
signal having an amplitude and a duty cycle. In another embodiment,
the amplitude is based at least in part on the first control signal
and the duty cycle is based at least in part on the second control
signal. In a further embodiment, creating the hybrid control signal
comprises converting a digital value that is responsive to the
amplitude to an analog signal, and modulating the analog signal
according to the duty cycle. In a yet further embodiment, creating
the hybrid control signal comprises filtering with a low-pass
filter a first PWM waveform, where a duty cycle of the first PWM
waveform is based on the amplitude and the filtered first PWM
waveform approximates an analog signal having the amplitude, and
modulating the analog signal with a second PWM waveform having the
duty cycle of the hybrid control signal.
[0030] In an embodiment, creating the hybrid control signal
comprises generating a digital value for predetermined intervals
and converting the digital value to an analog value during the
predetermined intervals, where the digital value is based on the
amplitude and the predetermined intervals based on the duty cycle.
In another embodiment, creating the hybrid control signal comprises
averaging a PWM waveform, where a duty cycle of the PWM waveform is
based on the amplitude and the averaged PWM waveform approximating
an analog signal having the amplitude, and turning the PWM waveform
ON and OFF at predetermined times, where the predetermined times is
based on the duty cycle of the hybrid control signal. In a further
embodiment, averaging the PWM waveform comprises filtering the PWM
waveform with a low-pass filter. In a yet further embodiment,
components of the low-pass filter are selected so that a frequency
of the PWM waveform is outside of the pass band of the low-pass
filter and a frequency of the hybrid control signal is within the
pass band.
[0031] Certain embodiments relate to a lighting module comprising
an LED configured to illuminate when driven by an output of an LED
driver circuit, a processor configured to determine an intensity
level for the LED and to generate a first control signal that when
coupled to the LED driver circuit results in a first drive signal
having a first resolution of intensity control and to generate a
second control signal that when coupled to the LED driver circuit
results in a second drive signal having a second resolution of
intensity control, where the first and second control signals are
based at least in part on the intensity level, and a hybrid control
signal generator configured to combine the first and second control
signals to create a hybrid control signal. The LED driver circuit
is configured to receive the hybrid control signal and to output a
third drive signal having a third resolution of intensity control,
where the third resolution of intensity control results in a
greater resolution of intensity control than the first resolution
of intensity control and the second resolution of intensity
control.
[0032] In an embodiment, the hybrid control signal generator
comprises a microcontroller configured to generate a digital value
responsive to the amplitude and a PWM waveform responsive to the
duty cycle, and a digital to analog converter (DAC) configured to
enable a conversion of the digital value to an analog signal
according to the PWM waveform. In another embodiment, the hybrid
control signal generator comprises a microcontroller configured to
generate a digital value responsive to the amplitude and a PWM
waveform responsive to the duty cycle, a digital to analog
converter (DAC) configured to convert the digital value to an
analog signal, and a switch configured to modulate the analog
signal according to PWM waveform. In a further embodiment, the
hybrid control signal generator comprises a microcontroller
configured to generate a first PWM waveform, a low-pass filter
configured to average the first PWM waveform to approximate an
analog signal having the amplitude, where the microcontroller is
further configured to generate a second PWM waveform having the
duty cycle, and the hybrid control signal generator further
comprises a switch configured to modulate the averaged first PWM
waveform with the second PWM waveform. In a yet further embodiment,
the hybrid control signal generator comprises a microcontroller
configured to generate a digital value for predetermined intervals
and a digital to analog converter (DAC) configured to convert the
digital value to an analog signal during the predetermined
intervals, where the digital value is based on the amplitude and
the predetermined intervals based on the duty cycle.
[0033] Certain embodiments relate to a method to control color and
brightness of a lighting module comprising one or more LEDs. The
method comprises receiving at the lighting module a data encoded
power signal over a two-wire communication network, where the data
encoded power signal comprises data associated with a user-selected
color and a user-selected brightness for the lighting module. The
method further comprises decoding the data associated with the
user-selected color and the user-selected brightness, where the
decoded data comprises a color ratio and an intensity level,
determining, for each LED of the one or more LEDs, a corresponding
amplitude and a corresponding duty cycle of a pulse width
modulation (PWM) signal in response to the color ratio at the
intensity level, and generating, for each LED of the one or more
LEDs, a corresponding hybrid control signal having the
corresponding amplitude and the corresponding duty cycle, where
each LED of the one or more LEDs is further associated with a
corresponding hysteretic LED driver. The method further comprises
providing, for each LED of the one or more LEDs, the corresponding
hybrid control signal to the corresponding hysteretic LED driver to
generate a corresponding output signal based on the corresponding
hybrid control signal, and driving each LED of the one or more LEDs
with the corresponding output signal to cause the lighting module
to illuminate in response to the user-selected color and the
user-selected brightness, where the corresponding hybrid control
signal comprises an analog component and a digital component, and
permits the color ratio at varying intensities to be controlled
with a level of resolution that is greater than the level of
resolution provided by the analog component alone and the level of
resolution provided by the digital component alone.
[0034] In an embodiment, the analog component comprises the
corresponding amplitude and the digital component comprises the
corresponding duty cycle. In another embodiment, the data encoded
power signal forms a sinusoidal waveform between zero
crossings.
[0035] In an embodiment, generating the corresponding hybrid
control signal comprises converting a digital value that is
responsive to the corresponding amplitude to an analog signal, and
enabling the conversion of the digital value to the analog signal
according to the corresponding duty cycle. In a further embodiment,
generating the corresponding hybrid control signal comprises
converting a digital value that is responsive to the corresponding
amplitude to an analog signal, and modulating the analog signal
according to the corresponding duty cycle. In a yet further
embodiment, generating the corresponding hybrid control signal
comprises filtering with a low-pass filter a first PWM waveform,
where a duty cycle of the first PWM waveform is based on the
corresponding amplitude and the filtered first PWM waveform
approximates an analog signal having the corresponding amplitude,
and where generating the corresponding hybrid control signal
further comprises modulating the analog signal with a second PWM
waveform having the corresponding duty cycle.
[0036] In an embodiment, generating the corresponding hybrid
control signal comprises generating a digital value for
predetermined intervals and converting the digital value to an
analog value during the predetermined intervals, where the digital
value is based on the corresponding amplitude and the predetermined
intervals based on the corresponding duty cycle. In another
embodiment, generating the corresponding hybrid control signal
comprises averaging a PWM waveform, where a duty cycle of the PWM
waveform is based on the corresponding amplitude and the averaged
PWM waveform approximates an analog signal having the corresponding
amplitude, where generating the corresponding hybrid control signal
further comprises turning the PWM waveform ON and OFF at
predetermined times, the predetermined times based on the
corresponding duty cycle. In a further embodiment, averaging the
PWM waveform comprises low-pass filtering the PWM waveform with a
low-pass filter. In a yet further embodiment, components of the
low-pass filter are selected so that a frequency corresponding of
the PWM waveform is outside of the pass band of the low-pass filter
and a frequency of the corresponding hybrid control signal is
within the pass band.
[0037] In another aspect, systems and methods relate to a lighting
module comprising a processor configured to receive a data encoded
power signal over a two-wire communication network, where the data
encoded power signal comprises data associated with a user-selected
color and a user-selected brightness. The processor is further
configured to decode the data, where the decoded data comprises a
color ratio and an intensity level. The processor further is
configured to determine an amplitude and a duty cycle of a hybrid
control signal in response to the color ratio at the intensity
level. The lighting module further comprises a hybrid control
signal generator configured to generate the hybrid control signal
having the amplitude and the duty cycle, an LED driver configured
to receive the hybrid control signal and generate an LED drive
signal based at least in part on the hybrid control signal, and one
or more LEDs configured to receive the LED drive signal and
illuminate in response to the user-selected color and the
user-selected brightness, where the hybrid control signal comprises
an analog component and a digital component, and permits the color
ratio at varying intensities to be controlled with a level of
resolution that is greater than the level of resolution provided by
an analog control signal alone and the level of resolution provided
by a digital control signal alone.
[0038] In an embodiment, the hybrid control signal generator
comprises a microcontroller configured to generate a digital value
responsive to the amplitude and a PWM waveform responsive to the
duty cycle, and a digital to analog converter (DAC) configured to
enable a conversion of the digital value to an analog signal
according to the PWM waveform. In another embodiment, the hybrid
control signal generator comprises a microcontroller configured to
generate a digital value responsive to the amplitude and a PWM
waveform responsive to the duty cycle, a digital to analog
converter (DAC) configured to convert the digital value to an
analog signal, and a switch configured to modulate the analog
signal according to PWM waveform. In a further embodiment, the
hybrid control signal generator comprises a microcontroller
configured to generate a first PWM waveform, a low-pass filter
configured to average the first PWM waveform to approximate an
analog signal having the amplitude, where the microcontroller is
further configured to generate a second PWM waveform having the
duty cycle, and the hybrid control signal generator further
comprises a switch configured to modulate the averaged first PWM
waveform with the second PWM waveform. In a yet further embodiment,
the hybrid control signal generator comprises a microcontroller
configured to generate a digital value for predetermined intervals
and a digital to analog converter (DAC) configured to convert the
digital value to an analog signal during the predetermined
intervals, where the digital value is based on the amplitude and
the predetermined intervals based on the duty cycle.
[0039] Other embodiments relate to a lighting system comprising a
plurality of modules, where each module is associated with one or
more LEDs and a processor, a two-wire communication network
configured to address each of the plurality of modules and provide
power to each of the plurality of modules, a user interface
configured to acquire user inputs responsive to a user-selected
color and a user-selected brightness for the plurality of modules,
a power supply including a rectifier circuit and a bridge circuit,
where the power supply is configured to modify an input voltage of
a power source to produce a data encoded power signal responsive to
a polarity of the input voltage and responsive to the acquired user
inputs. The power supply outputs the data encoded power signal over
the two-wire communication network and the processor of an
addressed module is configured to receive the data encoded power
signal over the two-wire communication network and decode the data
encoded power signal to provide decoded data comprising a color
ratio and an intensity level. The processor is further configured
to determine a first amplitude and a first duty cycle of a hybrid
control signal in response to the color ratio at the intensity
level. The lighting system further comprises a hybrid control
signal generator configured to generate the hybrid control signal
having the first amplitude and the first duty cycle, an LED driver
configured to receive the hybrid control signal and generate an LED
drive signal based at least in part on the hybrid control signal,
where the one or more LEDs of the addressed module are configured
to receive the LED drive signal and illuminate responsive to the
user-selected color and the user-selected brightness, where the
hybrid control signal comprises an analog component and a digital
component, and permits the color ratio at varying intensities to be
controlled with a level of resolution that is greater than the
level of resolution provided by an analog control signal alone and
the level of resolution provided by a digital control signal
alone.
[0040] In an embodiment, the hybrid control signal generator
comprises a microcontroller configured to generate a pulse width
modulation (PWM) waveform having a second duty cycle based at least
in part on the first amplitude, and a low-pass filter configured to
average the PWM waveform, the microcontroller further configured to
turn the PWM waveform ON and OFF at predetermined intervals that
are based at least in part on the first duty cycle. In another
embodiment, components of the low-pass filter are selected so that
a frequency of the PWM waveform is outside of the pass band of the
low-pass filter and a frequency of the hybrid control signal is
within the pass band.
[0041] For purposes of summarizing the disclosure, certain aspects,
advantages and novel features of the embodiments have been
described herein. It is to be understood that not necessarily all
such advantages may be achieved in accordance with any particular
embodiment of the invention. Thus, the inventions may be embodied
or carried out in a manner that achieves or optimizes one advantage
or group of advantages as taught herein without necessarily
achieving other advantages as may be taught or suggested
herein.
BRIEF DESCRIPTION OF THE DRAWINGS
[0042] Throughout the drawings, reference numbers are re-used to
indicate correspondence between referenced elements. The drawings,
associated descriptions, and specific implementation are provided
to illustrate embodiments and not to limit the scope of the
disclosure.
[0043] FIG. 1 illustrates an exemplary lighting system, according
to certain embodiments.
[0044] FIG. 2 is a block diagram of an exemplary lighting system,
according to certain embodiments.
[0045] FIG. 3 is a block diagram of an exemplary lighting
controller, according to certain embodiments.
[0046] FIG. 4 is an exemplary schematic diagram of a rectifier
circuit, according to certain embodiments.
[0047] FIG. 5 depicts an exemplary power waveform, according to
certain embodiments.
[0048] FIG. 6 depicts an exemplary waveform of the transistor gate
signal for a rectifier circuit, according to certain
embodiments.
[0049] FIG. 7 depicts an exemplary waveform of another transistor
gate signal for the rectifier circuit, according to certain
embodiments.
[0050] FIG. 8 depicts an exemplary rectified power waveform,
according to certain embodiments.
[0051] FIG. 9 is an exemplary schematic diagram of a bridge
circuit, according to certain embodiments.
[0052] FIG. 10 depicts an exemplary waveform of the transistor gate
signal for a bridge circuit, according to certain embodiments.
[0053] FIG. 11 depicts an exemplary waveform of another transistor
gate signal for the bridge circuit, according to certain
embodiments.
[0054] FIG. 12 depicts an exemplary power/data waveform without
data, according to certain embodiments.
[0055] FIG. 13 depicts an exemplary power/data waveform with data,
according to certain embodiments.
[0056] FIG. 14 is an exemplary schematic diagram of a
rectifier/bridge circuit, according to certain embodiments.
[0057] FIG. 15 is an exemplary schematic diagram of circuitry for
phase detect, timing generation and drivers, according to certain
embodiments.
[0058] FIG. 16 is an exemplary schematic diagram of a bias circuit,
according to certain embodiments.
[0059] FIG. 17A comprising 17A1-17A4 and 17B comprising 17B1-17B4
are exemplary circuit diagrams for a lighting controller, according
to one embodiment.
[0060] FIG. 18 is a block diagram of an exemplary lighting
controller, according to other embodiments.
[0061] FIG. 19 is an exemplary schematic diagram of a rectifier
circuit, according to other embodiments.
[0062] FIG. 20 is exemplary schematic diagram of a rectifier
circuit, according to yet other embodiments.
[0063] FIG. 21 depicts an exemplary power waveform, according to
other embodiments.
[0064] FIG. 22 depicts an exemplary waveform of the transistor gate
signal for a rectifier circuit, according to other embodiments.
[0065] FIG. 23 depicts an exemplary waveform of transistor gate
signal for the rectifier circuit, according to yet other
embodiments.
[0066] FIG. 24 depicts an exemplary rectified power waveform,
according to other embodiments.
[0067] FIG. 25 depicts an exemplary power/data waveform without
data, according to other embodiments.
[0068] FIG. 26 depicts an exemplary power/data waveform with data,
according to other embodiments.
[0069] FIG. 27 is an exemplary schematic diagram of a line voltage
control node, according to certain embodiments.
[0070] FIG. 28 is a block diagram of an exemplary line voltage
control node, according to certain embodiments.
[0071] FIG. 29 depicts a first exemplary output waveform to control
dimming of a Line Voltage device, according to certain
embodiments.
[0072] FIG. 30 depicts a second exemplary output waveform to
control dimming of a Line Voltage device, according to certain
embodiments.
[0073] FIG. 31 depicts a third exemplary output waveform to control
dimming of a Line Voltage device, according to certain
embodiments.
[0074] FIG. 32 is an exemplary schematic diagram of a wireless line
voltage control node, according to certain embodiments.
[0075] FIG. 33 is a block diagram of an exemplary transmitter for a
wireless line voltage control node, according to certain
embodiments.
[0076] FIG. 34 is a block diagram of an exemplary receiver for a
wireless line voltage control node, according to certain
embodiments.
[0077] FIG. 35 is a block diagram of an exemplary lighting system
for a wireless line voltage control node, according to certain
embodiments.
[0078] FIG. 36 is a block diagram of an exemplary lighting system
for a wireless line voltage control node, according to other
embodiments.
[0079] FIG. 37 is a block diagram of an exemplary wired low voltage
control node, according to certain embodiments.
[0080] FIG. 38 is a block diagram of an exemplary wireless low
voltage control node, according to certain embodiments.
[0081] FIG. 39 is a block diagram of a low voltage decoder,
according to certain embodiments.
[0082] FIG. 40 illustrates an exemplary lighting system for
controlling and reassigning lighting zones using a remote device,
according to certain embodiments.
[0083] FIG. 41 depicts a remote device, according to certain
embodiments.
[0084] FIG. 42 is a block diagram of an exemplary remote device,
according to certain embodiments.
[0085] FIG. 43 is a block diagram of an exemplary lighting
controller comprising a remote operator interface panel, according
to certain embodiments.
[0086] FIG. 44 is a block diagram of an exemplary transceiver for a
lighting controller with a remote operator interface panel,
according to certain embodiments.
[0087] FIG. 45 is a block diagram of an exemplary transceiver for a
remote operator interface panel, according to certain
embodiments.
[0088] FIG. 46 is a block diagram of an exemplary optical reader,
according to certain embodiments.
[0089] FIG. 47 illustrates an exemplary lighting system controlled
remotely, according to certain embodiments.
[0090] FIG. 48 illustrates another exemplary lighting system
controlled remotely, according to certain embodiments.
[0091] FIG. 49 illustrates an exemplary lighting system with a
master/slave configuration, according to certain embodiments.
[0092] FIG. 50 illustrates an exemplary lighting system with a
master/slave configuration, according to other embodiments.
[0093] FIG. 51 is a block diagram of an exemplary two-wire to
chassis protocol converter, according to certain embodiments.
[0094] FIG. 52 illustrates an exemplary lighting system with a
wireless master/slave configuration, according to certain
embodiments.
[0095] FIG. 53 is a block diagram of an exemplary transmitter for a
wireless two-wire chassis protocol converter, according to certain
embodiments.
[0096] FIG. 54 is a block diagram of an exemplary receiver for a
wireless two-wire chassis protocol converter, according to certain
embodiments.
[0097] FIG. 55 is a block diagram of an exemplary lighting system
for a wireless two-wire chassis protocol converter with multiple
slave chassis, according to certain embodiments.
[0098] FIG. 56 is a flowchart of an exemplary process for encoding
data bits onto a power signal for lighting modules.
[0099] FIG. 57 is a flowchart of an exemplary process for assigning
zones to addressable lighting modules in a networked lighting
system, according to certain embodiments.
[0100] FIG. 58 is a flowchart of an exemplary process for modifying
assigned zones in a lighting system using a remote controller,
according to certain embodiments.
[0101] FIG. 59 depicts an exemplary power waveform illustrating
ON/OFF voltages for colored LEDs, according to certain
embodiments.
[0102] FIG. 60 depicts an exemplary power waveform illustrating
ON/OFF voltages for colored LEDs, according to other
embodiments.
[0103] FIG. 61 is a block diagram of an exemplary single channel
lighting module, according to certain embodiments.
[0104] FIG. 62 is an exemplary schematic diagram of a single
channel lighting module, according to certain embodiments.
[0105] FIG. 63 is a block diagram of an exemplary multichannel
lighting module, according to certain embodiments.
[0106] FIG. 64 is an exemplary schematic diagram of a multichannel
lighting module, according to certain embodiments.
[0107] FIG. 65 is a front view of an exemplary lighting controller
chassis, according to certain embodiments.
[0108] FIG. 66 is a back view of an exemplary lighting controller
chassis, according to certain embodiments.
[0109] FIG. 67 is a block diagram of an exemplary hysteretic
driver, according to certain embodiments.
[0110] FIG. 68 is an exemplary analog input waveform for a
hysteretic LED driver that results in approximately full (100%)
brightness of the LED, according to certain embodiments.
[0111] FIG. 69 illustrates an exemplary analog input waveform for a
hysteretic LED driver that results in approximately half (50%)
brightness of the LED, according to certain embodiments.
[0112] FIG. 70 illustrates an exemplary PWM input waveform for a
hysteretic LED driver that results in approximately full (100%)
brightness of the LED, according to certain embodiments.
[0113] FIG. 71 illustrates an exemplary PWM input waveform for a
hysteretic LED driver that results in approximately half (50%)
brightness, according to certain embodiments.
[0114] FIG. 72 is a block diagram of an exemplary lighting control
system to control color and brightness of LED lighting, according
to certain embodiments.
[0115] FIG. 73 illustrates an exemplary hybrid control waveform for
a hysteretic LED driver that results in approximately quarter (25%)
brightness, according to certain embodiments.
[0116] FIG. 74 is a block diagram of an exemplary hybrid control
waveform generator, according to certain embodiments.
[0117] FIG. 75 is a block diagram of an exemplary hybrid control
waveform generator, according to certain embodiments.
[0118] FIG. 76 is a block diagram of an exemplary hybrid control
waveform generator, according to certain embodiments.
[0119] FIG. 77 illustrates an exemplary hybrid control waveform for
a hysteretic LED driver, according to certain embodiments.
[0120] FIG. 78 is a block diagram of an exemplary hybrid control
waveform generator, according to certain embodiments.
[0121] FIG. 79 illustrates an exemplary hybrid control waveform for
a hysteretic LED driver, according to certain embodiments.
[0122] FIG. 80 is a block diagram of an exemplary hybrid control
waveform generator, according to certain embodiments.
[0123] FIG. 81 illustrates a filter response for an exemplary low
pass filter for a hybrid control waveform generator, according to
certain embodiments.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT
[0124] The features of the inventive systems and methods will now
be described with reference to the drawings summarized above.
[0125] FIG. 1 illustrates an exemplary lighting system 100. The
lighting system 100 comprises a lighting controller housing 102
connected to a plurality of lighting fixtures or modules 104
through a two-wire interface. The lighting controller housing 102
houses a lighting controller including a power supply and user
interface panel, as described in further detail below. The lighting
fixtures 104 are grouped into zones 106.
[0126] In the example illustrated in FIG. 1, zone 1 106a comprises
lighting fixture 1 104a, which provides illumination to a portion
of the house exterior. Zone 2 106b comprises lighting fixtures 2,
3, 4 104b, 104c, 104d, respectively, which illuminate the path,
while zone 3 106c comprises lighting fixtures 5, 6, 7, 104e, 104f,
104g, respectively, which provide accent lighting for the tree. In
other embodiments, the lighting system 100 can be configured with
more or less zones 106 and/or with more or less lighting fixtures
104 in each zone 106.
[0127] Typically, the lighting fixtures 104 in each zone 106 turn
ON or OFF together, but unlike some traditional lighting systems,
each zone 106 can be controlled independently of the other zones
106. In one example for the lighting system 100 illustrated in FIG.
1, zone 1 106a turns ON at dusk and turns OFF at dawn to illuminate
the front door of the house. Zone 2 106b turns ON at dusk and turns
OFF at 9 PM to illuminate the path. Finally, zone 3 turns on at 7
PM and turns OFF at 10 PM to provide accent lighting in the
yard.
[0128] In one embodiment, the lighting system 200 is a residential
outdoor lighting system. In other embodiments, the lighting system
200 is used for outdoor commercial purposes to illuminate the
outside of hotels, golf courses, amusement parks, and the like, and
for indoor commercial purposes to illuminate hotel interiors,
office-building interiors, airport terminals, and the like. In
further embodiments, the lighting system 200 is used to illuminate
housing developments. In yet further embodiments, the lighting
system 200 is used to illuminate artwork in residences, in museums,
or the like. Many possibilities exist for the lighting system 200
to one skilled in the art from the disclosure herein. The lighting
functions ON/OFF include a plurality of lighting functions, such
as, for example, timing control, dimming, brightness, color, hue,
zone allocation, intensity, and the like.
[0129] FIG. 2 is a block diagram of an exemplary lighting system
200 comprising a lighting controller 202 and a plurality of
lighting modules 204. The lighting controller 202 comprises a power
supply 208 and an operator interface 210, which includes a fixture
programming port 212. A lighting controller housing houses the
power supply 208 and the operator interface 210. The size of the
lighting controller housing depends on the size of the power supply
208 and the operator interface 210 contained within it. In an
embodiment, the lighting controller housing has a height that
ranges from approximately 11 inches to approximately 15 inches, a
width that ranges from approximately 7 inches to approximately 9
inches, and a thickness that ranges from approximately 5 inches to
approximately 7 inches. The lighting controller 202 electrically
couples to the lighting modules 204 through a two-wire path
carrying a power/data signal. The lighting modules 204 electrically
connect in parallel to the two-wire path and are grouped into M
zones 206. In the illustrated embodiment, zone 1 comprises three
lighting modules 204, zone 2 comprises a single lighting module
204, and zone 3 comprises two lighting modules 204. Further, the
lighting controller 202 controls up to M zones 206, where in the
illustrated embodiment, zone M includes N lighting modules 204.
Each zone 206 can be independently energized such that the lighting
modules 204 in each zone 206 can turn ON or OFF independently of
the lighting modules 204 in the other zones 206.
[0130] Controller 202 is shown housing the power supply 208, the
operator interface 210, and the fixture programming port 212. In
other embodiments, the power supply 208, the operator interface
210, and the fixture programming port 212 may be separate devices
or any two of the power supply 208, the operator interface 210, and
the fixture programming port 212 may be housed in the same
housing.
[0131] FIG. 3 is a block diagram of an exemplary lighting
controller 300 comprising a power supply 302 and an operator
interface panel 308. The power supply 302 receives AC power from a
primary AC power source 306 and addresses/data/commands from the
operator interface panel 308 and provides a control signal to a
plurality of lighting fixtures 304 through the two-wire path
336.
[0132] The operator interface panel 308 comprises operator controls
310, such as selection buttons, knobs, and the like, which the user
uses to input the desired lighting effects to the lighting system
200, and displays and indicators 312 to provide feedback to the
user. The operator interface panel 308 further comprises a computer
314 and its associated memory 316. The microprocessor 314
interfaces with the operator controls 310 to send the
addresses/data/commands to the power supply 302 and interfaces with
the displays and indicators 312 to display information received
from the power supply 302. The operator interface 308 can be
buttons, virtual icons, or buttons on a touch screen, voice
controlled, or any user interface recognizable to an artisan from
the disclosure herein.
[0133] The computer 314 comprises, by way of example, processors,
program logic, or other substrate configurations representing data
and instructions, which operate as described herein. In other
embodiments, the processors can comprise controller circuitry,
processor circuitry, processors, general-purpose single-chip or
multi-chip microprocessors, digital signal processors, embedded
microprocessors, microcontrollers and the like. The memory 316 can
comprise one or more logical and/or physical data storage systems
for storing data and applications used by the computer 314. The
memory 316 comprises, for example, RAM, ROM, EPROM, EEPROM, and the
like.
[0134] The operator interface panel 308 further comprises a fixture
programming port 318 to provide unique addresses, a lighting group,
and/or zone number to each of the plurality of lighting fixtures
304, and a logic power supply 320 to provide a low voltage, such as
+5 volts, for example, for the digital logic components of the
operator interface panel 308.
[0135] The power supply 302 comprises a primary AC transformer 322,
current sensing circuitry 324, phase detect and timing circuitry
326, driver circuitry 328, a synchronous fullwave rectifier 332,
and a bridge 334. The power supply 302 further comprises a low
power transformer 346 to provide a low voltage, such as 9 VAC, for
example, to a logic power supply which creates a regulated DC
voltage for the digital logic components of the power supply 302
and biasing circuitry 330 to provide the proper voltage levels to
operate transistors in the rectifier 332 and the bridge 334.
[0136] The primary AC transformer 322 receives a primary AC power
signal from the primary AC power source 306 and transforms the
primary AC signal into lower voltage AC signal. In an embodiment,
the primary AC signal is approximately a 120 volt 60 Hz power
waveform. In other embodiments, the primary AC signal can be an
approximately 110 volts 60 Hz, 220 volt 50 Hz, 220 volt 60 Hz, 230
volts 60 Hz, 240 volts 50 Hz, or the like, power waveform. In an
embodiment, the primary AC transformer 322 is a primary AC to 12
VAC transformer 322, and transforms the primary AC signal into an
approximately 12 VAC RMS power signal. In other embodiments, the
transformer 322 is a primary AC transformer with several taps. In
an embodiment, the transformer has taps at approximately 11 VAC up
to approximately 14 VAC. In other embodiments, the transformer 322
transforms the AC signal into an approximately 24 VAC.
[0137] In an embodiment, the transformer 322 is a high wattage
transformer, such as a 300 watt transformer, or the like, for
example, in order to supply sufficient power to illuminate the
plurality of lighting modules 304. The output of the transformer
322 electrically connects to the current sensing circuitry 324. The
current sensing circuitry 324 senses the amount of current in the
output of the transformer 322. The phase detect and timing
circuitry 326 receives a signal proportional to the sensed current
from the current sensing circuitry 324 and shuts off the power
supply 302 when the sensed current exceeds a threshold. For
example, if there is a short between the wires of the two-wire path
336, a 300 watt transformer can supply a large amount of power in
the form of heat in a very short time. When the sensed current
exceeds a threshold, the lighting controller 300 shuts off the
power before the heat generated causes damage to the lighting
system 200.
[0138] The phase detect and timing circuitry 326 further receives
data and commands from the processor 314 and the power waveform
from the transformer 322, and provides timing signals to the driver
circuit 328. The timing signals control the driver circuitry 328 to
encode a data signal onto the power signal by varying the polarity
of the power waveform, as will be further discussed herein.
[0139] Further, the output of the transformer 322 electrically
connects to the synchronous fullwave rectifier 332, which rectifies
the power signal. The fullwave rectifier 332 electrically connects
to the bridge 334 and the fullwave rectifier 332 and the bridge 334
electrically connect to the driver circuitry 328. Both the fullwave
rectifier 332 and the bridge 334 receive drive signals from the
driver circuitry 328. The bridge 334 receives the rectified power
signal and outputs a control signal to the lighting fixtures 304.
The control signal comprises a data encoded power waveform, which
provides power to illuminate the lighting fixtures 304 and
address/data/commands to individually control the lighting fixtures
304.
[0140] FIG. 4 is an exemplary schematic diagram of a synchronous
rectifier circuit 400, according to an embodiment. The rectifier
circuit 400 comprises a primary AC to 12 VAC transformer 402, a
first transistor Q1 404, a second transistor Q2 406, a third
transistor Q3 408, and a fourth transistor Q4 410. The primary AC
to 12 VAC transformer 402 receives a primary AC power signal and
outputs an approximately 12 VAC RMS power waveform having a first
power waveform AC1 and a second power waveform AC2. FIG. 5
illustrates an exemplary 12 VAC RMS power waveform 500 having a
peak-to-peak voltage of between approximately +16.97 volts to
approximately -16.97 volts.
[0141] In an embodiment, the transistors Q1 404, Q2 406, Q3 408, Q4
410 are metal-oxide-semiconductor field-effect transistors
(MOSFETs) with an integral body diode. The MOSFETs with the
integral body diode advantageously function as a substantially
loss-less switch when their gates are enabled at the appropriate
point in time when their diodes would be conducting. For example, a
MOSFET having a resistance of 1 milliohm conducting a current of 25
amps would attenuate a signal across it by approximately 25
millivolts. The synchronous rectifier 400 selectively turns on the
MOSFETs when their body diodes would be conducting to create a
highly efficient power supply 302.
[0142] In other embodiments, the transistors Q1 404, Q2 406, Q3
408, Q4 410 are P-channel or N-channel MOSFETs with or without an
integral body diode. In yet other embodiments, transistors, such as
Bipolar Junction Transistors (BJTs), Isolated Gate Bipolar
Transistors (IGBTs), or the like, can be used.
[0143] In another embodiment, each transistor Q1 404, Q2 406, Q3
408, Q4 410 comprises more than one transistor connected in
parallel. In another embodiment, multiple MOSFETs may be packaged
in a single module.
[0144] The first transistor Q1 404 is coupled in series with the
second transistor Q2 406 across AC1 and AC2, such that a drain of
the first transistor Q1 404 connects to the first power waveform
AC1, and a drain of the second transistor Q2 406 connects to the
second power waveform AC2. Further, a source of first transistor Q1
404 connects to a source of the second transistor Q2 406 and forms
a third power waveform GROUND.
[0145] The third transistor Q3 408 is coupled in series with the
fourth transistor Q4 410 across AC1 and AC2, such that a source of
the third transistor Q3 408 connects to the first power waveform
AC1, and a source of the fourth transistor Q2 410 connects to the
second power waveform AC2. Further, a drain of the third transistor
Q3 408 connects to a drain of the fourth transistor Q4 410 and
forms a fourth power waveform V-FULLWAVE.
[0146] The series combination of the first transistor Q1 404 and
the second transistor Q2 406 electrically couple in parallel with
the series combination of the third transistor Q3 408 and fourth
transistor Q4 410, such that the drain of the first transistor Q1
404 electrically couples to the source of the third transistor Q3
408, and the drain of the second transistor Q2 406 electrically
couples to the source of the fourth transistor Q4 410.
[0147] Each transistor is associated with a gate signal and the
gate signals electrically couple to an output of a comparator
comparing the first and second power waveforms, AC1 and AC2, via
driver circuitry. The gates of the second transistor Q2 406 and the
third transistor Q3 408 enable when the first power waveform AC1 is
greater than the second power waveform AC2. FIG. 6 depicts an
exemplary waveform 600 of the transistor gate signal for the gates
of the second transistor Q2 406 and the third transistor Q3 408,
according to an embodiment. Referring to FIGS. 5 and 6, the gate
signal Vgs (Q2, Q3) is enabled when AC1 is greater than AC2.
[0148] Further, the gates of the first transistor Q1 404 and the
fourth transistor Q4 410 enable when the second power waveform AC2
is greater than the first power waveform AC1. FIG. 7 depicts an
exemplary waveform 700 for the gates of the first transistor Q1 404
and the fourth transistor Q4 410, according to an embodiment.
Referring to FIGS. 5 and 7, the gate signal Vgs (Q1, Q4) is enabled
when AC2 is greater than AC1.
[0149] The rectifier 400 full wave rectifies a 12 VAC RSM signal
creating a the third power waveform GROUND and the fourth power
waveform V-FULLWAVE. The rectified 12 VAC RMS signal, V-FULLWAVE,
has a peak voltage of approximately 16.97 volts, which is
approximately the same as the peak voltage of the power waveform at
the output of the transformer 402. The small loss in signal is due
to exemplary, but finite conduction of the transistors Q1 404, Q2
406, Q3 408, Q4 410 when their gates are enabled. FIG. 8 depicts an
exemplary rectified 12 VAC RMS signal 800, according to an
embodiment. As illustrated in FIG. 8, the rectifier 400 outputs a
non-inverted 12 VAC RMS power waveform 800 when AC1 is greater than
AC2 and outputs an inverted 12 VAC RMS waveform 800 when AC2 is
greater than AC1.
[0150] Referring to FIG. 4, a current sensing element 412, such as
a current transformer, magnetically couples to the wire/trace
carrying the 12 VAC RMS power waveform. In one embodiment, the
current transformer 412 magnetically couples to the wire/trace
carrying the power waveform AC2. In another embodiment, the current
transformer 412 magnetically couples to the wire/trace carrying the
power waveform AC1. Current flowing through wire/trace carrying
AC2, in the illustrated embodiment, produces a magnetic field in
the core of the current transformer 412, which in turn induces a
current in the winding wound around the core of the current
transformer 412. The induced current is proportional to the current
of the power waveform AC2, in the illustrated embodiment, or to the
current of the power waveform AC1, in another embodiment. The
current transformer 412 outputs signals, Current Sense1 and Current
Sense2, proportional to current flowing through the power waveforms
AC1 or AC2. The signals Current Sense1 and Current Sense2 are used
to determine when the current flowing in the power waveforms AC1 or
AC2 is greater than a threshold value, such that power supply 302
can be disabled before damage to the circuitry occurs. Accordingly,
the rectifier 400 of FIG. 4 advantageously produces the V-FULLWAVE
waveform 800 of FIG. 8 with minimal power loss and correspondingly,
minimal heat generation.
[0151] FIG. 9 is an exemplary schematic diagram of a bridge circuit
900, according to an embodiment. The bridge 900 comprises a fifth
transistor Q5 904, a sixth transistor Q6 906, a seventh transistor
Q7 908, and an eighth transistor Q8 910. The bridge 900 receives
the rectified power waveforms V-FULLWAVE and GROUND from the
rectifier 400. In the illustrated embodiment, V-FULLWAVE is an
exemplary rectified 12 VAC RMS signal as shown in FIG. 8.
Advantageously, in a disclosed embodiment, the bridge 900
selectively outputs the rectified power waveforms V-FULLWAVE,
GROUND with either a positive polarity or a negative polarity. By
doing so, data or intelligence can be added to the presently
described power signal. Thus, the rectifier 400 and the bridge 900
combine to produce a power signal with embedded data or logic.
[0152] The positive or negative polarity of V-FULLWAVE is, for
example, the control signals, LIGHTING CONTROL1, LIGHTING CONTROL2
on the two-wire path to the lighting modules 304. LIGHTING CONTROL1
and LIGHTING CONTROL2 comprise addresses/data/commands encoded
within the power waveform V-FULLWAVE, to provide
addresses/data/commands and power to the lighting modules 304.
[0153] In an embodiment, the transistors Q5 904, Q6 906, Q7 908, Q8
910 are metal-oxide-semiconductor field-effect transistors
(MOSFETs) with an integral body diode. As described above, the
MOSFETs with the integral body diode advantageously function as an
almost or substantially loss-less switch when their gates are
enabled at the appropriate point in time when their diodes would be
conducting.
[0154] In other embodiments, the transistors Q5 904, Q6 906, Q7
908, Q8 910 are either P-channel or N-channel MOSFETs with or
without an integral body diode. In yet other embodiments,
transistors, such as Bipolar Junction Transistors (BJTs), Isolated
Gate Bipolar Transistors (IGBTs), or the like, can be used.
[0155] In another embodiment, each transistor Q5 904, Q6 906, Q7
908, Q8 910 comprises more than one transistor connected in
parallel. In another embodiment, multiple MOSFETs may be packaged
in a single module.
[0156] The fifth transistor Q5 904 is coupled in series with the
sixth transistor Q6 906 across V-FULLWAVE and GROUND, such that a
drain of the fifth transistor Q5 904 connects to the power waveform
V-FULLWAVE, and a source of the sixth transistor Q6 906 connects to
the power waveform GROUND. Further, a source of the fifth
transistor Q5 904 connects to a drain of the sixth transistor Q6
906 and forms the first control signal, LIGHTING
POWER/CONTROL1.
[0157] The seventh transistor Q7 908 is coupled in series with the
eighth transistor Q8 910 across V-FULLWAVE and GROUND, such that a
drain of the seventh transistor Q7 908 connects to the power
waveform V-FULLWAVE, and a source of the eighth transistor Q8 910
connects to the power waveform GROUND. Further, a source of the
seventh transistor Q7 908 connects to a drain of the eighth
transistor Q8 910 and forms the second control signal, LIGHTING
POWER/CONTROL2.
[0158] The series combination of the fifth transistor Q5 904 and
the sixth transistor Q6 906 electrically couple in parallel with
the series combination of the seventh transistor Q7 908 and eighth
transistor Q8 910, such that the drain of the fifth transistor Q5
904 electrically couples to the drain of the seventh transistor Q7
908, and the source of the sixth transistor Q6 906 electrically
couples to the source of the eighth transistor Q8 910.
[0159] Each transistor Q5 904, Q6 906, Q7 908, Q8 910 is associated
with a gate signal. The gate signals electrically couple, via
driver circuitry, to a control signal comprising data from the
processor 314 associated with the operator interface panel 308 and
the output of the comparator comparing the power waveforms AC1,
AC2. The gates of the fifth transistor Q5 904 and the eighth
transistor Q8 910 are enabled when the control signal is in a first
state. When the gates of the fifth transistor Q5 904 and the eighth
transistor Q8 910 are enabled, the bridge 900 outputs the power
waveforms V-FULLWAVE and GROUND having a first polarity on the
two-wire path as signals LIGHTING POWER/CONTROL1 and LIGHTING
POWER/CONTROL2. The gates of the sixth transistor Q6 906 and the
seventh transistor Q7 908 are enabled when the control signal is in
a second state. When the gates of the sixth transistor Q6 906 and
the seventh transistor Q7 908 are enabled, the bridge 900 outputs
the power waveforms V-FULLWAVE and GROUND having a second polarity
on the two-wire path as signals LIGHTING POWER/CONTROL1 and
LIGHTING POWER/CONTROL2.
[0160] For example, in one embodiment, when the gates of the fifth
transistor Q5 904 and the eighth transistor Q8 910 are enabled, the
signals LIGHTING POWER/CONTROL1 and LIGHTING POWER/CONTROL2
comprise the power waveforms V-FULLWAVE and GROUND having a
positive polarity. Further, when the gates of the sixth transistor
Q6 906 and the seventh transistor Q7 908 are enabled, signals
LIGHTING POWER/CONTROL1 and LIGHTING POWER/CONTROL2 comprise the
power waveforms V-FULLWAVE and GROUND having a negative
polarity.
[0161] In another embodiment, the polarities can be reversed, such
that the signals LIGHTING POWER/CONTROL1 and LIGHTING
POWER/CONTROL2 comprise power waveforms V-FULLWAVE and GROUND
having a negative polarity when gates of the fifth transistor Q5
904 and the eighth transistor Q8 910 are enabled and comprise power
waveforms V-FULLWAVE and GROUND having a positive polarity when the
gates of the sixth transistor Q6 906 and the seventh transistor Q7
908 are enabled.
[0162] As discussed above, the gate signals electrically couple,
via driver circuitry, to a control signal comprising data from the
processor 314 associated with the operator interface panel 308 and
the output of the comparator comparing the power waveforms AC1,
AC2. When there is no data present, the control signal follows the
output of the comparator comparing the power waveforms AC1,
AC2.
[0163] FIG. 10 depicts an exemplary waveform 1000 of the transistor
gate signal for the gates of the fifth transistor Q5 904 and the
eighth transistor Q8 910 with no data present. As shown in FIGS. 5
and 10, the gate signal Vgs (Q5, Q8) is enabled when AC1 is greater
than AC2.
[0164] FIG. 11 depicts an exemplary waveform 1100 of the transistor
gate signal for the gates of the sixth transistor Q6 906 and the
seventh transistor Q7 908 with no data present. As shown in FIGS. 5
and 11, the gate signal Vgs (Q5, Q8) is enabled when AC2 is greater
than AC1.
[0165] FIG. 12 depicts an exemplary bridge output waveform 1200
when there is no data present from the processor 314, in one
embodiment. As illustrated in FIGS. 10, 11, and 12, the bridge 900
outputs V-FULLWAVE with a positive polarity when the gates of the
fifth transistor Q5 904 and the eighth transistor Q8 910 are
enabled and outputs V-FULLWAVE with a negative polarity when the
gates of the sixth transistor Q6 906 and the seventh transistor Q7
908 are enabled, generating approximately a sine wave. As shown,
without data on the power signal for the lights, the rectifier 400
and the bridge 900 take the 12 VAC RMS output of the transformer
402, which is illustrated as its 16.97 VAC peak-to-peak waveforms
AC1 and AC2 in FIG. 5, fullwave rectify it, and change it back to
its original form using substantially or almost loss-less
circuitry. However, as described herein, the same rectifier 400 and
bridge 900 accept control signals from the processor 314 according
to user programming to selectively control one or more fixtures
104, 204, 304 in one or more zones 106, 206. The control signals
activate the gates with the same or substantially similar almost
loss-less process in a manner that embeds logic or data on the
power signal 1200 of FIG. 12.
[0166] For example, when the control signal controlling the
transistor gates comprises data from the processor 314 associated
with the operator interface panel 308, the bridge 900 encodes the
data onto the signals LIGHTING POWER/CONTROL1 and LIGHTING
POWER/CONTROL2 such that the bridge 900 outputs V-FULLWAVE having
one polarity when the control signal is in a first state and
outputs V-FULLWAVE having the opposite polarity when the control
signal is in the second state. FIG. 13 depicts an exemplary
power/data waveform 1300 with data, according to an embodiment.
FIG. 13 illustrates start bits 1302 comprising 1, 1, followed by
data bits 1304 comprising 0, 1, 0, 1, 1. In other embodiments,
other configurations of start bits can be used and opposite
polarities can be used to represent the 0 and 1 data bits. For
instance, the control signal may change state at the peaks or any
point of V-FULLWAVE as opposed to at the point V-FULLWAVE is zero.
In summary, the bridge 900 is used synchronously with the VAC power
waveform from the transformer 302 to select either a positive or a
negative peak or half-cycle of the power waveform and apply the
selected half-cycle to the output signals, LIGHTING POWER/CONTROL1
and LIGHTING POWER/CONTROL2 to encode data within the power
waveform for transmission to the lighting modules 304.
[0167] In an embodiment where the transformer 402 produces
approximately a 12 VAC 60 hertz power waveform, the data rate is
approximately 120 bits per second. In another embodiment, the
lighting modules 304 comprise a comparator comparing the signals
LIGHTING POWER/CONTROL1, LIGHTING POWER/CONTROL2 to detect the data
and a full wave rectifier to rectify the signals LIGHTING
POWER/CONTROL1, LIGHTING POWER/CONTROL2 to provide power to the
lighting elements.
[0168] In an embodiment, the transistors Q5 904, Q6 906, Q7 908, Q8
910 are turned on at the zero crossing of the controls signal
because advantageously, the lighting modules 304 draw less power.
At that time, there is less voltage or current flowing and less EMI
noise is generated. In other embodiments, the transistors Q5 904,
Q6 906, Q7 908, Q8 910 are turned on and off at other than the zero
crossing of the control signal and/or more frequently than every
half cycle of the incoming power.
[0169] Another advantage of sending the data as either a positive
polarity or a negative polarity rectified power wave form is that
there is no DC bias on the two-wire data/power path. If a DC bias
is present, moisture seeping through the wires can produce unwanted
galvanic corrosion.
[0170] FIG. 14 is an exemplary schematic diagram of a
rectifier/bridge circuit 1400, according to an embodiment, which is
also capable of producing a power signal with embedded data the
same or similar to those disclosed above. The rectifier/bridge
circuit 1400 comprises a primary AC to 24 VAC center-tapped
transformer 1402, a current transformer 1412, a fifth transistor Q5
1404, a sixth transistor Q6 1406, a seventh transistor Q7 1408, and
an eighth transistor Q8 1410. The current transformer 1412 senses
the current in the center tap of the transformer 1402 as described
above with respect to FIG. 4.
[0171] The primary AC to 24 VAC transformer 1402 receives a primary
AC power signal and outputs an approximately 12 VAC RMS between
each end tap and the center tap. This waveform comprises a power
waveform having the first power waveform AC1 and the second power
waveform AC2. Referring to FIG. 5, the exemplary 12 VAC RMS power
waveform 500 has a peak-to-peak voltage of between approximately
+16.97 volts to approximately -16.97 volts. Further, the center tap
of transformer 1402 electrically couples to one wire of the
two-wire path and forms the signal LIGHTING POWER/CONTROL2.
[0172] In an embodiment, the transistors Q5 1404, Q6 1406, Q7 1408,
Q8 1410 are metal-oxide-semiconductor field-effect transistors
(MOSFETs) with an integral body diode. In other embodiments, the
transistors Q5 1404, Q6 1406, Q7 1408, Q8 1410 are either P-channel
or N-channel MOSFETs with or without an integral body diode. In
another embodiment, each transistor Q5 1404, Q6 1406, Q7 1408, Q8
1410 comprises more than one transistor connected in parallel. In
another embodiment, multiple MOSFETs may be packaged in a single
module.
[0173] The transistors Q5 1404, Q6 1406, Q7 1408, Q8 1410 are
coupled in series such that a source of the fifth transistor Q5
1404 connects to a source of the eighth transistor Q8 1410, a drain
of the eighth transistor Q8 1410 connects to a drain of the sixth
transistor Q6 1406 and couples to the other wire of the two-wire
path and forms the signal LIGHTING POWER/CONTROL1, and a source of
the sixth transistor Q6 1406 connects to a source of the seventh
transistor Q7 1408. The series combination of the transistors Q5
1404, Q8 1410, Q6 1406, Q7 1408 connects to the power waveforms
AC1, AC2 such that a drain of the fifth transistor Q5 1404
electrically connects to AC1 and a drain of the seventh transistor
Q7 1408 electrically connects to AC2.
[0174] Each transistor Q5 1404, Q6 1406, Q7 1408, Q8 1410 is
associated with a gate signal. The gate signals electrically
couple, via driver circuitry, to the control signal comprising data
from the processor 314 associated with the operator interface panel
308 and the output of the comparator comparing the power waveforms
AC1, AC2, as described above with respect to FIG. 9.
[0175] As shown in FIG. 14, one of the wires in the two-wire path
to the lighting modules is the center tap of the transformer 1402.
Depending on whether the gates of transistors Q5 1404 and Q8 1410
or Q6 1406 and Q7 1408 are enabled, the positive half-cycle or the
negative half-cycle of the power waveform AC1, AC2 is sent on the
other wire of the two-wire path to the lighting modules 304. In
this manner, the data from the controller 314 can be encoded within
the power waveform sent to the lighting modules 304. The
rectifier/bridge 1400 can transmit the same data and power to the
lighting modules 304 as the combination of the rectifier 400 and
the bridge 900, but advantageously with fewer MOSFETs.
[0176] FIG. 15 is an exemplary schematic diagram of circuitry 1500
comprising phase detect circuitry, timing generation circuitry,
driver circuitry, and over current protection circuitry, according
to certain embodiments. The circuitry 1500 comprises a comparator
1502, MOSFET drivers 1504, 1506, 1508, 1510, a computer 1512, a
modulator 1514, a difference amplifier 1518, and a latching
comparator 1516.
[0177] The comparator 1502 receives the power waveforms AC1, AC2
and electrically couples an output to the gates of the transistors
Q1 404, Q2 406, Q3 408, Q4 410 in the rectifier 400 via the drivers
1504, 1506. The power waveforms AC1, AC2 received by the comparator
1502 have been preconditioned as is known to one of skill in the
art to be within the acceptable input voltage range for the
comparator 1502. The comparator 1502 compares AC1 and AC2 and, in
one embodiment, outputs a positive pulse when AC1 is greater than
AC2 and outputs a ground or negative pulse when AC2 is greater than
AC1. While the input to the comparator is a sine wave, as shown in
FIG. 5, the output is a square wave. The output of the comparator
1502 couples to the input of the inverting driver 1504, and the
input of the non-inverting driver 1506.
[0178] The output of the non-inverting driver 1506 couples to the
gates of transistors Q2 406 and Q3 408 on the rectifier 400. The
waveform 600, in FIG. 6, illustrates an example of the transistor
gate signal for the gates of the second transistor Q2 406 and the
third transistor Q3 408. Referring to FIGS. 5 and 6, the output of
the comparator, which is the input to the driver 1506, is positive
and the gate signal Vgs (Q2, Q3) is enabled when AC1 is greater
than AC2. Further, the output of driver 1504 is low and the
transistors Q1 404 and Q4 410 are off when AC1 is greater than
AC2.
[0179] The output of the inverting driver 1504 couples to the gates
of transistors Q1 404 and Q4 410 on the rectifier 400. The waveform
700, in FIG. 7, illustrates an example of the transistor gate
signal for the gates of the first transistor Q1 404 and the fourth
transistor Q4 410. Referring to FIGS. 5 and 7, the output of the
comparator 1502, which is the input to the inverting driver 1504,
is negative or ground, and the gate signal Vgs (Q1, Q4) is enabled
when AC2 is greater than AC1. Further, the output of driver 1506 is
low and the transistors Q2 406 and Q3 408 are off when AC2 is
greater than AC1.
[0180] The modulator 1514 receives the output of the comparator
1502 and receives a data signal from the computer 1512. The data
signal comprises addresses/data/commands from the operator
interface panel 308. In an embodiment, computer 1512 is computer
314. In another embodiment, computer 314 and computer 1512 are
different computers. The computer 1512 comprises, by way of
example, those devices or structures similar to computer 314.
[0181] An output of the modulator 1514 connects to the input of
inverting driver 1508 and to the input of non-inverting driver
1510. The modulator 1514 passes the output of the comparator 1502
to the drivers 1508, 1510 when no data is present. The signal on
the two-wire path to the lighting modules 304 is the sine wave
1200, shown in FIG. 12, when no data is present.
[0182] The output of the non-inverting driver 1510 couples to the
gates of transistors Q5 904, 1404 and Q8 910, 1410 on the bridge
900 or the rectifier/bridge 1400. The waveform 1000, in FIG. 10,
illustrates an example of the transistor gate signal for the gates
of the fifth transistor Q5 904, 1404 and the eighth transistor Q8
910, 1410. Referring to FIGS. 5 and 10, the gate signal Vgs (Q5,
Q8) is enabled when AC1 is greater than AC2 and data is absent.
[0183] The output of the inverting driver 1508 couples to the gates
of transistors Q6 906, 1406 and Q7 908, 1408 on the bridge 900 or
the rectifier/bridge 1400. The waveform 1100, in FIG. 11,
illustrates an example of the transistor gate signal for the gates
of the sixth transistor Q6 906, 1406 and the seventh transistor Q7
908, 1408. Referring to FIGS. 5 and 11, the gate signal Vgs (Q6,
Q7) is enabled when AC2 is greater than AC1 and data is absent.
[0184] As shown, without data on the power signal for the lights,
the rectifier/bridge 1400 takes the center tap of the transformer
1402, as one wire of the two-wire path to the lighting fixtures
104, 204. Depending on whether Q5 1404 and Q8 1410, or Q6 1406 and
Q7 1408 are enabled, the rectifier/bridge 1400 sends the positive
half-cycle or the negative half-cycle of the 12 VAC RMS output of
the transformer 1402, which is illustrated as its 16.97 VAC
peak-to-peak waveforms AC1 and AC2 in FIG. 5 on the other wire of
the two-wire path, using substantially or almost loss-less
circuitry. However, as described herein, the same rectifier/bridge
1400 accepts control signals from the processor 314 according to
user programming to selectively control one or more fixtures 104,
204 in one or more zones 106, 206. The control signals activate the
gates with the same or substantially similar almost loss-less
process in a manner that embeds logic or data on the power signal
1200 of FIG. 12.
[0185] When data is present the modulator 1514 functions as a
selective inverter, in an embodiment. The data signal inverts the
signal between the comparator 1502 and the drivers 1508, 1510. For
example, when the data is high, the modulator 1514 acts as an
inverter and inverts the signal from the comparator 1502 before the
signal is received by the drivers 1508, 1510. When the data is low,
the modulator 1514 passes the output of the comparator 1502 to the
drivers 1508, 1510. This permits the phase of the signals LIGHTING
POWER/CONTROL1, LIGHTING POWER/CONTROL2 output from the bridge 900
or rectifier/bridge 1400 on the two-wire path to the lighting
modules 304 to be adjusted on a half-cycle basis to encode the data
within the power waveform. Referring to FIG. 13, the waveform 1300
illustrates an example of a data encoded power waveform comprising
start bits 1302 comprising 1, 1, followed by data bits 1304
comprising 0, 1, 0, 1, 1.
[0186] Referring to FIG. 15, the difference amplifier 1518 receives
the signals, CURRENT SENSE1, CURRENT SENSE2, from the current
transformer 412, 1412, which are proportional to the current
flowing out of the transformer 402. The difference amplifier 1518
subtracts CURRENT SENSE1, CURRENT SENSE2 to create a single ended
current protection signal. The latching comparator 1516 receives
the output of the difference amplifier 1518 and compares the
current protection signal to a reference voltage or threshold. The
output of the latching comparator 1516 couples to an enable signal
common to the drivers 1504, 1506, 1508, 1510. When the peak voltage
of the current protection signal exceeds the threshold, the output
of the latching comparator 1516 disables the drivers 1504, 1506,
1508, 1510 to prevent an overcurrent event from damaging the
circuitry.
[0187] Further, processor 1512 receives the latched output of the
latching comparator 1516 and the latching comparator 1516 receives
a reset signal from the processor 1512. In an embodiment, the
processor 1512 can reset the latching comparator 1516. In another
embodiment, the processor 1512 can alert the user to the
overcurrent event through communication with the processor 314. The
processor 314 could then display the information on the display
312.
[0188] FIG. 16 is an exemplary schematic diagram of a bias circuit
1600, according to an embodiment. In embodiments of the rectifier
400, the bridge 900, and the rectifier/bridge 1400, the sources of
some of the transistors Q1-Q8 are electrically connected to one of
the two AC outputs, AC1, AC2, of the transformer 402, 1402 or to
the rectified power waveform V-FULLWAVE. When the transistor or
MOSFET is turned on, nominally the gate voltage should be
approximately 5 volts +/- about 4 volts to approximately 10 volts
+/- about 5 volts more positive than the source voltage, for proper
operation, as is known to one of skill in the art from the
disclosure herein. However, this is a higher voltage than is
present at the output of the transformer 402, 1402. The bias
circuitry 1600 functions to provide the transistors Q1-Q8 in the
rectifier 400, the bridge 900 and the rectifier/bridge 1400 with
the higher gate voltage.
[0189] The bias circuit 1600 receives the power waveforms AC1, AC2
from the transformer 402, 1402 and generates the power waveforms
AC1++, AC2++ that are at a higher DC level than AC1, AC2, but
follow the AC1, AC2 waveforms, respectively. For example, AC1++ and
AC2++ may have a DC offset of about 10 volts to about 20 volts
above AC1, AC2, as they move up and down with AC1, AC2. AC1++,
AC2++ power the MOSFET driver integrated circuits 1508, 1510 that
provide the gate signals for the MOSFETs Q5 904, Q6 406, Q7 908, Q8
910 in the bridge 900 and the MOSFETs Q5 1404, Q6 1406, Q7 1408, Q8
1410 in rectifier/bridge 1400.
[0190] The bias circuit 1600 comprises capacitors C1 1602, C2 1604,
resistors R1 1606, R2 1608, and diodes D1 1610, D2 1612, D3 1614,
D4 1616. AC2 electrically couples to an anode of diode D1 1610 and
the series combination of diode D1 1610 and resistor R1 1602
half-wave rectify AC2 with respect to AC1 and capacitor C1 1602
stores the voltage. An anode of diode D2 1612 couples to an end of
capacitor C1 1602. Diode D2 1612 is a zener or clamping diode and
clamps the voltage at the clamping value. In an embodiment, diode
D2 1616 is an +18 volt zener diode. A cathode of diode D2 1612
provides the power waveform AC1++.
[0191] Similarly, AC1 electrically couples to an anode of diode D4
1616 and the series combination of diode D4 1616 and resistor R2
1608 half-wave rectify AC1 with respect to AC2 and capacitor C2
1604 stores the voltage. An anode of diode D3 1614 couples to an
end of capacitor C2 1604. Diode D3 1614 is a zener or clamping
diode and clamps the voltage at the clamping value. In an
embodiment, diode D3 1614 is an +18 volt zener diode. A cathode of
diode D3 1614 provides the power waveform AC2++. In other
embodiments, diodes D2 1612, D3 1614 can have clamping values at
other than +18 volts.
[0192] The bias circuit 1600 further receives the power waveform
AC1 from the transformer 402 and V-FULLWAVE from the rectifier 400
and generates the power waveform V-FULLWAVE++. V-FULLWAVE++ is
approximately AC1 half-wave rectified and at a DC level that is no
lower than approximately one diode drop below V-FULLWAVE.
V-FULLWAVE powers the MOSFET driver integrated circuits 1504, 1506
that provide the gate signals for the MOSFETs Q1 404, Q2 406, Q3
408 Q4 410 in the synchronous rectifier 400.
[0193] The bias circuit further comprises capacitors C3 1618, C4
1620, C5 1622, resistor R3 1624, and diodes D5 1626, D6 1628, D7
1630, D8 1632. AC1 electrically couples to a first end of capacitor
C3 1618 and a cathode of diode D5 1626. A second end of capacitor
C3 1618 connects to a first end of capacitor C4 1620, an anode of
diode D5 1626 and an anode of diode D6 1628. A second end of
capacitor C4 1620 and a cathode of diode D6 1628 couple to an anode
of diode D7 1630 and a cathode of diode D8 1632. Capacitors C3
1618, C4 1620, diode D5 1626, and diode D6 1628 form a charge pump
circuit using the power waveform AC1. An anode of diode D8 1632
electrically couples to V-FULLWAVE and clamps the AC signal passing
through the capacitors C3 1618, C4 1620 at approximately one diode
drop below V-FULLWAVE at the cathode of diode D8 1632. The series
combination of diode D7 1630 and resistor R3 1624 half-wave
rectifies the clamped V-FULLWAVE signal with respect to V-FULLWAVE
and capacitor C5 1622 stores the voltage. An end of capacitor C5
1622 couples to an end of resistor R3 1624 and provides the power
waveform V-FULLWAVE++.
[0194] FIGS. 17A1-17A4 and 17B1-17B4 are exemplary circuit diagrams
for a lighting controller 1700, according to one embodiment. FIGS.
17A1 and 17A3 are an example of a rectifier circuit 1710 where the
MOSFETs 1712, 1714, 1716, 1718 of FIG. 17A1 electrically couple in
parallel with the MOSFETs 1713, 1715, 717, 1719 having the
corresponding gate signals Gate5, Gate6, Gate7, Gate8 of FIG. 17A3
for increased current drive. FIGS. 17A2 and 17A4 are an example of
a bridge circuit 1720 where the MOSFETs 1722, 1724, 1726, 1728 of
FIG. 17A2 electrically couple in parallel with the MOSFETs 1723,
1725, 1727, 1729 having the corresponding gate signals Gate1,
Gate2, Gate3, Gate4 of FIG. 17A4 for increased current drive. FIGS.
17B1-17B4 are examples of a bias circuit 1730, driver circuit 1740,
phase detection circuit 1750, timing generation circuit 1760, and a
current protection circuit 1770.
[0195] FIG. 18 is a block diagram of another exemplary lighting
controller 1800 controlling lighting devices 1804 and comprising a
power supply 1802 and the operator interface panel 308. The
operator interface panel 308 comprises the operator controls 310,
the displays and indicators 312, the computer 314, the memory 316,
the fixture programming port 318, and the logic power supply 320
and operates as described above with respect to FIG. 3 to provide
addresses/data/commands to the power supply 1802. The architecture
of the power supply 1802 is similar to the architecture of the
power supply 302 except that the power supply 1802 does not have
the transformer 322 to transform the primary line voltage to a
secondary AC voltage. Instead, the power supply 1802 drives the
bridge and encoding circuitry from the primary line voltage.
Further, the lighting devices 1804, described further herein, are
powered by the primary line voltage.
[0196] The power supply 1802 comprises current sensing circuitry
1824, phase detect and timing circuitry 1826, driver circuitry
1828, a synchronous fullwave rectifier 1832, and a bridge 1834. The
power supply 1802 further comprises a low power transformer 1846 to
provide a low voltage, such as 9 VAC, for example, to a logic power
supply which creates a regulated DC voltage for the digital logic
components of the power supply 1802, and biasing circuitry 1830 to
provide the proper voltage levels to operate transistors in the
rectifier 1832 and the bridge 1834.
[0197] Similar to the power supply 302 illustrated in FIG. 3, the
power supply 1802 receives AC power from the primary power source
306 and addresses/data/commands from the operator interface panel
308 and provides a control signal to a plurality of lighting
fixtures 1804 through a two-wire path 1836. However, unlike the
power supply 302, the primary power source 306 is electrically
coupled to the power supply circuitry without being transformed to
a lower voltage by the primary AC to 12 VAC transformer 322. In
addition, while the lighting modules 304 operate at a low voltage
signal, such as 12 VAC, for example, the lighting modules 1804
operate at approximately the primary AC power level, such as 120
VAC, for example.
[0198] In an embodiment, the primary AC signal is approximately a
120 volt 60 Hz power waveform. In other embodiments, the primary AC
signal can be an approximately 110 volts 60 Hz, 220 volt 50 Hz, 220
volt 60 Hz, 230 volts 60 or 50 Hz, 240 volts 60 or 50 Hz, or the
like, power waveform.
[0199] The primary AC power source 306 electrically connects to the
current sensing circuitry 1824. The current sensing circuitry 1824
senses the amount of current in the output of the primary AC power
source 306. The phase detect and timing circuitry 1826 receives a
signal proportional to the sensed current from the current sensing
circuitry 1824 and shuts off the power supply 1802 when the sensed
current exceeds a threshold, as described above.
[0200] The phase detect and timing circuitry 1826 further receives
data and commands from the processor 314 and the power waveform
from the primary AC power source 306, and provides timing signals
to the driver circuit 1828. The timing signals control the driver
circuitry 1828 to encode a data signal onto the power signal by
varying the polarity of the power waveform, as will be further
discussed herein.
[0201] Further, the primary AC power source 306 electrically
connects to the synchronous fullwave rectifier 1832, which
rectifies the power signal. The fullwave rectifier 1832
electrically connects to the bridge 1834 and the fullwave rectifier
1832 and the bridge 1834 electrically connect to the driver
circuitry 1828. Both the fullwave rectifier 1832 and the bridge
1834 receive drive signals from the driver circuitry 1828. The
bridge 1834 receives the rectified power signal and outputs a
control signal to the lighting fixtures 1804. The control signal
comprises a data encoded power waveform, which provides power to
illuminate the lighting fixtures 1804 and address/data/commands to
individually control the lighting fixtures 1804.
[0202] FIG. 19 is a schematic diagram of an exemplary synchronous
rectifier circuit 1900 configured to operate in the power supply
1802. The rectifier circuit 1900 comprises a first switching device
Q1 1904, a second switching device Q2 1906, a third switching
device Q3 1908, and a fourth switching device Q4 1910. The
rectifier circuit 1900 is similar to the rectifier circuit 400 in
FIG. 4, but without the primary AC to 12 VAC transformer 402.
[0203] The rectifier circuit 1900 receives the primary AC power
signal having a first power waveform AC1 and a second power
waveform AC2. In one embodiment, the primary AC power signal is
approximately 120 VAC and FIG. 21 illustrates an exemplary 120 VAC
RMS power waveform 2100 having a peak-to-peak voltage of between
approximately +169.7 volts to approximately -169.7 volts.
[0204] In an embodiment, the switching devices Q1 1904, Q2 1906, Q3
1908, Q4 1910 are metal-oxide-semiconductor field-effect
transistors (MOSFETs) with an integral body diode, as described
above with respect to FIG. 4. The synchronous rectifier 1900
selectively turns on the MOSFETs when their body diodes would be
conducting to create a highly efficient power supply 1802.
[0205] In other embodiments, the switching devices Q1 1904, Q2
1906, Q3 1908, Q4 1910 are P-channel or N-channel MOSFETs with or
without an integral body diode. In yet other embodiments,
transistors, such as Bipolar Junction Transistors (BJTs), Isolated
Gate Bipolar Transistors (IGBTs), or the like, can be used. In
further embodiments, switching devices such as triode for
alternating current devices (triacs), silicon-controlled rectifiers
(SCRs), and the like can be used. In another embodiment, each
switching device Q1 1904, Q2 1906, Q3 1908, Q4 1910 comprises more
than one transistor connected in parallel. In another embodiment,
multiple MOSFETs may be packaged in a single module.
[0206] The first switching device Q1 1904 is coupled in series with
the second switching device Q2 1906 across AC1 and AC2 to form a
third power waveform GROUND and the third switching device Q3 1908
is coupled in series with the fourth switching device Q4 1910
across AC1 and AC2, to form a fourth power waveform V-FULLWAVE, as
described above with respect to FIG. 4. Also, as described above
with respect to FIG. 4, the series combination of the first
switching device Q1 1904 and the second switching device Q2 1906
electrically couple in parallel with the series combination of the
third switching device Q3 1908 and fourth switching device Q4
1910.
[0207] Each switching device Q1 1904, Q2 1906, Q3 1908, Q4 1910 is
associated with a gate signal and the gate signals electrically
couple to an output of a comparator comparing the first and second
power waveforms, AC1 and AC2, via driver circuitry as described
herein. The gates of the second switching device Q2 1906 and the
third switching device Q3 1908 enable when the first power waveform
AC1 is greater than the second power waveform AC2. FIG. 22 depicts
an exemplary waveform 2200 of the gate signal for the gates of the
second switching device Q2 1906 and the third switching device Q3
1908, according to an embodiment. Referring to FIGS. 21 and 22, the
gate signal Vgs (Q2, Q3) is enabled when AC1 is greater than
AC2.
[0208] Further, the gates of the first switching device Q1 1904 and
the fourth switching device Q4 1910 enable when the second power
waveform AC2 is greater than the first power waveform AC1. FIG. 23
depicts an exemplary waveform 2300 for the gates of the first
switching device Q1 1904 and the fourth switching device Q4 1910,
according to an embodiment. Referring to FIGS. 21 and 23, the gate
signal Vgs (Q1, Q4) is enabled when AC2 is greater than AC1.
[0209] The rectifier 1900 full wave rectifies the primary AC
signal, such as, for example, a 120 VAC RMS signal, creating a
third power waveform GROUND and the fourth power waveform
V-FULLWAVE. The rectified 120 VAC RMS signal, V-FULLWAVE, has a
peak voltage of approximately 169.7 volts, which is approximately
the same as the peak voltage of the power waveforms AC1 and AC2 at
the input of the rectifier 1900. The small loss in signal is due to
exemplary, but finite conduction of the switching devices Q1 1904,
Q2 1906, Q3 1908, Q4 1910 when their gates are enabled. FIG. 24
depicts an exemplary rectified 120 VAC RMS signal 2400, according
to an embodiment. As illustrated in FIG. 24, the rectifier 1900
outputs a non-inverted 120 VAC RMS power waveform 2400 when AC1 is
greater than AC2 and outputs an inverted 120 VAC RMS waveform 2400
when AC2 is greater than AC1.
[0210] The waveforms illustrated in FIGS. 21-24 illustrate
embodiments where the primary AC power source 306 is approximately
120 VAC. In other embodiments, the primary AC power signal can be
an approximately 110 volts 60 Hz, 220 volt 50 Hz, 220 volt 60 Hz,
230 volts 50 or 60 Hz, 240 volts 50 or 60 Hz, or the like, power
waveform, and the RMS and peak-to-peak voltages will vary
correspondingly.
[0211] Referring to FIG. 19, a current sensing element 1912, such
as a current transformer, magnetically couples to the wire/trace
carrying the primary AC power waveform. In one embodiment, the
current transformer 1912 magnetically couples to the wire/trace
carrying the power waveform AC2. In another embodiment, the current
transformer 1912 magnetically couples to the wire/trace carrying
the power waveform AC1. As described above with respect to FIG. 4,
the current induced in the current transformer 1912 is proportional
to the current of the power waveform AC2, in the illustrated
embodiment, or to the current of the power waveform AC1, in another
embodiment. The current transformer 1912 outputs signals, Current
Sense1 and Current Sense2, which are proportional to current
flowing through the power waveforms AC1 or AC2. The signals Current
Sense1 and Current Sense2 are used to determine when the current
flowing in the power waveforms AC1 or AC2 is greater than a
threshold value, such that power supply 1802 can be disabled before
damage to the circuitry occurs. Accordingly, the rectifier 1900 of
FIG. 19 advantageously produces the V-FULLWAVE waveform 2400 of
FIG. 24 with minimal power loss and correspondingly, minimal heat
generation. In other embodiments, the current flowing in AC1 or AC2
can be sensed with Hall-Effect based current sensors, which sense
the magnet field produced by the current. In yet another
embodiment, current can be sensed by a current sense resistor.
[0212] FIG. 20 is a schematic diagram of another exemplary
rectifier circuit 2000 configured to operate in the power supply
1802. In the embodiment illustrated in FIG. 20, the rectifier 2000
is a diode-based rectifier comprising diodes D1 2004, D2 2006, D3
2008, and D4 2010. Because the current drawn at 120 VAC is
approximately one tenth of the current drawn at 12 VAC for the same
amount of power delivered, the diode-based rectifier 2000 provides
acceptable efficiency. The rectifier circuit 2000 rectifies the
primary AC power signal to produce similar gate and V-FULLWAVE
waveforms as illustrated in FIGS. 22-24. Because of the drop in
voltage (diode drop) associated with the diodes D1 2004, D2 2006,
D3 2008, D4 2010, the peak voltages may be approximately two diode
drops or approximately 1.4 V less that the peak voltages
illustrated in FIGS. 22-24.
[0213] Referring to FIG. 18, the bridge circuit 1834 receives the
rectified power waveforms V-FULLWAVE and GROUND from the rectifier
1900. In an embodiment, the bridge circuit 1834 is similar to the
bridge circuit 900 described herein with respect to FIG. 9. The
switching devices in the bridge circuit 1834 can be P-channel or
N-channel MOSFETs with or without integral body diodes, BJT's,
IGBTs, as described with respect to FIG. 9 and bridge circuit 900.
Because of the lower current, the switching devices in the bridge
circuit 1834 can also be triacs, SCRs, and the like.
[0214] In an embodiment where the primary AC power signal is a 120
VAC signal, V-FULLWAVE is an exemplary rectified 120 VAC RMS signal
depicted in FIG. 24. Advantageously, the bridge 1834 selectively
outputs a control signal comprising the rectified power waveforms
V-FULLWAVE, GROUND with either a positive polarity or a negative
polarity. By doing so, data or intelligence can be added to the
presently described power signal. Thus, the rectifier 1900 and the
bridge 1834 combine to produce a 120 VAC power signal with embedded
data, which provides power to illuminate the lighting fixtures 1804
and address/data/commands to individually control the lighting
fixtures 1804.
[0215] FIG. 25 depicts an exemplary bridge output waveform 2500
when there is no data present from the processor 314. As shown,
without data on the power signal for the lights 1804, the rectifier
1900 and the bridge 1834 take the 120 VAC RMS input signal, which
is illustrated as its 169.7 VAC peak-to-peak waveforms AC1 and AC2
in FIG. 21, fullwave rectify it, and change it back to its original
form. However, as described above with respect to rectifier 400 and
bridge 900, the rectifier 1900 and bridge 1834 accept control
signals from the processor 314 according to user programming to
selectively control one or more fixtures 1804 in one or more zones.
The control signals activate the gates of the rectifier 1900 and
bridge 1834 with the same or substantially similar process as
described above to embed logic or data on the power signal 2500 of
FIG. 25.
[0216] For example, when the control signal controlling the gates
of the switching devices comprises data from the processor 314
associated with the operator interface panel 308, the bridge 1834
encodes the data onto the signals LIGHTING POWER/CONTROL1 and
LIGHTING POWER/CONTROL2 by outputting V-FULLWAVE having one
polarity when the control signal is in a first state and outputting
V-FULLWAVE having the opposite polarity when the control signal is
in the second state. FIG. 26 depicts an exemplary power/data
waveform 2600 with data, according to an embodiment. FIG. 26
illustrates a start bit sequence 2602 comprising 1, 1, followed by
data bits 2604 comprising 0, 1, 0, 1, 1. This is similar to the
exemplary power/data waveform depicted in FIG. 13 except that the
positive peak waveform is approximately +169.7 V and the negative
peak waveform is approximately -169.7 V. In summary, the bridge
1834 is used synchronously with the 120 VAC power waveform to
select either a positive or a negative peak or half-cycle of the
120 VAC power waveform and apply the selected half-cycle to the
output signals, LIGHTING POWER/CONTROL1 and LIGHTING POWER/CONTROL2
to encode data within the power waveform for transmission to the
lighting modules 1804 over the two-wire path 1836. It should be
noted that in FIG. 26, the control signals are switched at the zero
crossing of the incoming line voltage waveform. It is also possible
to encode data by switching at a point other than the zero
crossing, or more frequently than once per half cycle of the
incoming line voltage.
[0217] FIG. 27 is an exemplary schematic diagram of a line voltage
control node system 2700. The line voltage control node 2702
receives the data encoded low voltage power signals LIGHTING
POWER/CONTROL1 and LIGHTING POWER/CONTROL2 from the two-wire path
336. In an embodiment, the low voltage power signals are
approximately 12 VAC. In other embodiments, the low voltage power
signals are approximately 11 VAC, approximately 14 VAC, and the
like.
[0218] The line voltage control node 2702 is assigned a lighting
zone via the operator interface panel 308 as described above. Based
on the information contained on the two-wire path 336 addressed to
the line voltage control node 2702, the line voltage control node
2702 controls line/high voltage lighting devices 2704. In an
embodiment, the devices 2704 are 120 VAC dimmable lighting
devices.
[0219] FIG. 28 is a block diagram of an exemplary line voltage
control node 2800 configured to dim the lighting device 2704. The
line voltage control node 2800 comprises a full wave rectifier
2802, a voltage regulator 2804, a conditioning circuit 2806, a
microcontroller 2810, a triggering optoisolator 2814, a detection
optoisolator 2816, and a triac 2818. The full wave rectifier 2802,
the voltage regulator 2804, the conditioning circuit 2806, the
microcontroller 2810 are the same or substantially similar to the
circuitry described herein with respect to FIGS. 61-64 for single
and multi-channel lighting modules 6100, 6200, 6300, 6400. In the
lighting modules 6100, 6200, 6300, 6400, the microcontroller
controls the LED driver to vary the brightness of the LED, whereas
in the line voltage control node 2800, the line voltage, and thus
the dimming function, is controlled via the conduction angle of the
triac 2818.
[0220] For safety, the 120 VAC line voltage signals are
galvanically isolated from the 12 VAC low voltage signals by the
triggering optoisolator 2814. The detection optoisolator 2816
senses the phase of the incoming line voltage signal so that the
triac 2818 can be triggered at the appropriate point in time. In
most embodiments the zero crossings of the 120 VAC line voltage
signal occurs at substantially the same time as the zero crossing
of the 12 VAC low voltage signal. However, in other embodiments,
the zero crossings of the high and low voltage signals may not
substantially coincide. For instance if a generator generates
either of the 12 VAC low voltage signal or the 120 VAC line voltage
signal, then the zero crossings would not substantially correspond
to those of the utility grid. Because of this, the detection
optoisolator 2816 is used to sense the actual zero crossing of the
line voltage signal and to send this information to the
microcontroller 2810. The triggering optoisolator 2814 can be, for
example, an MOC3021 available from Fairchild Optoelectronics Group
and the like. The detection optoisolator 2816 can be, for example,
a TLP620 from Toshiba and the like. The triac 2818 can be, for
example, a BTA208-800 from NXP Semiconductor and the like.
[0221] Once the zero crossing of the line voltage is known, the
microcontroller 2810 triggers the triac 2818 with a delay time
based at least in part on the desired output intensity of the 120
VAC lighting device 2704. FIGS. 29-31 are exemplary waveforms
depicting various output voltages usable to dim the lighting device
2704. The microcontroller 2810 creates output voltages
approximately equal to or less than the input line voltage by
delaying the triac trigger.
[0222] FIG. 29 depicts an output waveform 2900 having a very short
delay between the zero crossing and the trigger. Therefore, the
output waveform 2900 is almost equal to the input waveform. FIG. 30
depicts an output waveform 3000 having a trigger delay such that
the output waveform 3000 is approximately half of the input
voltage. FIG. 31 depicts an output waveform 3100 that is a small
percentage of the input voltage due to a larger delay of the
trigger signal.
[0223] The above embodiment has been described with respect to
dimming functionality for the lighting devices 2704. In other
embodiments of the line voltage control node 2800, a Z-wave device
and/or a relay device could be used for non-dimming applications.
For example, the line voltage control node 2800 could control
ON/OFF for a zone comprising a fountain or the like.
[0224] Referring to FIG. 28, the line voltage control node 2800
further comprises an optional user interface 2812 having buttons,
slide switches, or other forms of user controls to permit the user
to manually control the lighting device 2704, in addition to the
commands originating from the user interface panel 308.
[0225] The line voltage control node 2800 further comprises an LED
2808. In an embodiment, the LED 2808 is a low power LED not
intended for illumination. The LED 2808 has the ability to "flash
out" its serial number in a manner the same as or substantially
similar to that of lighting modules 4004 described in further
detail herein with respect to FIGS. 40-42.
[0226] FIGS. 27 and 28 illustrate embodiments of the line voltage
control node 2700, 2800 that is electrically connected (via wires)
to the data encoded 12 VAC two-wire path 336. FIGS. 32-36
illustrate embodiments of a wireless line voltage control node. The
wireless line voltage control node is substantially similar to the
wired line voltage control node 2700, 2800 except that the
connection from the 120 VAC node to the 12 VAC control signal 336
is wireless. This may be particularly useful to control an existing
lighting device to which there is no 12 VAC wiring run.
[0227] FIG. 32 is an exemplary schematic diagram of a wireless line
voltage control node 3200 comprising a 120 VAC interface wireless
receiver 3202 and a 12 VAC interface wireless transmitter 3204
communicating over a radio frequency (RF) wireless link. The 12 VAC
interface wireless transmitter 3204 is electrically connected to
the data encoded 12 VAC two-wire path 336 and receives control data
from the signals LIGHTING POWER/CONTROL 1 and LIGHTING
POWER/CONTROL2 via the two-wire path 336. The 12 VAC interface
wireless transmitter 3204 sends over the wireless link the control
commands to the 120 VAC interface receiver 3202. The 120 VAC
interface receiver 3202 is electrically connected to the 120 VAC
line voltage and the 120 VAC lighting device 2704, and receives the
control data over the wireless link from the 12 VAC interface
transmitter 3204. The 120 VAC interface receiver 3202 controls the
dimming level of the lighting device 2704 base at least in part on
the control data received from the 12 VAC interface transmitter
3204.
[0228] In other embodiments, the 12 VAC interface transmitter 3204
and the 120 VAC interface receiver 3202 can be replaced with
transceivers. This may be useful to facilitate acknowledgment and
retry algorithms to create a more robust link. For instance, the
transceiver 3204 attached to the 12 VAC two-wire path would decode
the signal on the 12 VAC line, and transmit its contents (if
appropriate) to the transceiver 3202 attached to the 120 VAC line.
The transceiver 3202, would in turn respond with an acknowledge
transmission, indicating that the signal was received and the
checksum was good. If the transceiver 3204 attached to the 12 VAC
line does not receive the acknowledge signal, it would again
transmit the command. This process could continue for a specified
number of retries.
[0229] FIG. 33 is a block diagram of an exemplary wireless control
node transmitter 3300 for the wireless line voltage control node
3200. The control node transmitter 3300 is assigned a lighting zone
via the operator interface panel 308 as described herein. In the
illustrated embodiment, the control node transmitter 3300 comprises
a full wave rectifier 3302, a voltage regulator 3304, a
conditioning circuit 3306, a microcontroller 3310, and a radio
frequency (RF) transmitter or transceiver 3320. The full wave
rectifier 3302, the voltage regulator 3304, the conditioning
circuit 3306, and the microcontroller 3310 are the same or
substantially similar to the circuitry described herein with
respect to FIGS. 61-64 for single and multi-channel lighting
modules 6100, 6200, 6300, 6400. In the lighting modules 6100, 6200,
6300, 6400, the microcontroller controls the LED driver to vary the
brightness of the LED, whereas the control node transmitter 3300
controls the RF transmitter or transceiver 3320.
[0230] The control node transmitter 3300 further comprises an
optional user interface 3312, which permits the user to manually
adjust the lighting devices 2704 from the location of the
transmitter 3300. Further, the user interface 3312 can also be used
to determine whether the RF link is operational.
[0231] The control node transmitter 3300 further comprises a low
power LED 3308, not intended for illumination. The LED 3308 has the
ability to "flash out" its serial number in a manner the same as or
substantially similar to that of lighting modules 4004 described in
further detail herein with respect to FIGS. 40-42.
[0232] FIG. 34 is a block diagram of an exemplary wireless control
node receiver 3400 for the wireless line voltage control node 3200.
In the illustrated embodiment, the control node receiver 3400
comprises a full wave rectifier 3402, a voltage regulator 3404, a
microcontroller 3410, a triggering optoisolator 3414, a detection
optoisolator 3416, a triac 3418, and a radio frequency (RF)
receiver or transceiver 3420. The full wave rectifier 3402, the
voltage regulator 3404, the microcontroller 3410, the triggering
optoisolator 3414, the detection optoisolator 3416, and the triac
3418 are the same or substantially similar to the circuitry
described herein for the wired line voltage control node 2700, 2800
with respect to FIGS. 27 and 28. The wired control nodes 2700, 2800
comprise circuitry to decode the data from the data encoded 12 VAC
two-wire path 336, whereas the wireless control node receiver 3400
receives the control information over the RF link through the RF
receiver or transceiver 3420. In addition, power for the
microcontroller 3410 and RF receiver 3420 is derived from the 120
VAC line voltage. A simple linear regulation approach is shown.
However, it should be noted that this is just one method to step
down the rectified line voltage, which is well over 100 V, to a
voltage acceptable to the microcontroller 3410. Other methods and
devices such as switching converters, for example, can also be used
as would be known to one of skill in the art from the disclosure
herein.
[0233] Whereas the optoisolators 2814, 2816 in the wired line
voltage control node 2800 were used for safety considerations,
galvanic isolation is optional for the control node receiver 3400
because there is no low voltage input. Therefore, in an embodiment,
the optoisolators 3414, 3416 are optional. Due to line voltage
surges and other disturbances, the optoisolators 3414, 3416 may be
useful to protect circuitry in the control node receiver 3400. The
dimming method of controlling the output voltage via the conduction
angle of the triac 2818 as described in the wired control node
2700, 2800 is the same as or substantially similar to the approach
used with the control node receiver 3400. In the control node
receiver 3400, the microcontroller 3410 delays the trigger signal
to the triac 3418 to control the output voltage used to dim the
lighting devices 2704.
[0234] The control node receiver 3400 further comprises an optional
user interface 3412 which permits the user to manually adjust the
lighting devices 2704 from the location of the control node
receiver 3400. Further, the user interface 3412 can also be used to
determine whether the RF link is operational.
[0235] The control node receiver 3400 further comprises a low power
LED 3408, not intended for illumination. The LED 3408 has the
ability to "flash out" its serial number in a manner the same as or
substantially similar to that of lighting modules 4004 described in
further detail herein with respect to FIGS. 40-42.
[0236] The above embodiment has been described with respect to
dimming functionality for the lighting devices 2704. In other
embodiments of the control node receiver 3400, a Z-wave device
and/or a relay device could be used for non-dimming applications,
such as zone control. For example, the wireless line voltage
control node 3200 could control ON/OFF for a zone comprising a
fountain or the like.
[0237] The wireless line voltage control node 3200 is assigned a
zone number so that it can be controlled by the signals LIGHTING
POWER/CONTROL 1 and LIGHTING POWER/CONTROL2 via the two-wire path
336. Because the wireless line voltage control node 3200 comprises
the receiver 3400 and the transmitter 3300, it is possible to have
multiple control architectures.
[0238] FIG. 35 is a block diagram of a first exemplary lighting
system 3500 for the wireless line voltage control node 3200. The
lighting system 3500 comprises a plurality of transmitters 3504a,
3504b . . . 3504n and a corresponding plurality receivers 3502a,
3502b . . . 3502n. Each receiver 3502 is paired to a corresponding
transmitter 3504 to avoid crosstalk with other receivers. Each
transmitter in the plurality of transmitters 3504 is assigned a
zone number. Since the transmitters 3504 electrically couple to the
12 VAC data encoded two-wire path 336, each transmitter 3504 can
"filter" the commands from the incoming data by determining the
zone associated with the command and send only those meant for its
corresponding receiver 3502 over the RF link.
[0239] FIG. 36 is a block diagram of a second exemplary lighting
system 3600 for the wireless line voltage control node 3200. The
lighting system 3600 comprises a transmitter 3604 and a plurality
receivers 3602a, 3602b . . . 3602n. Each receiver 3602a, 3602b . .
. 3602n is assigned a zone. The transmitter 3604 transmits all
commands it receives, without filtering them, because it does not
know which zone has been assigned to the receivers 3602. If
different zone numbers are assigned to the receivers 3602, then a
single transmitter 3604 could service multiple receivers 3602 by
sending every command it receives over the RF link. The "filtering"
would be done at each receiver 3602. Advantageously, the star
architecture embodiment illustrated in FIG. 36 avoids the user
having to purchase transmitters 3604 for each receiver 3602
deployed.
[0240] To utilize the star architecture approach illustrated in
FIG. 36, the user would assign a zone number to each receiver 3602
by entering the zone number into the receiver 3602. In a first
embodiment, the user could enter the zone number using the optional
user interface 3412 and LED 3408. In a second embodiment, the
receiver 3602 has a low voltage input provided to program the zone
number using the same or substantially similar method as is used to
program zone numbers in the single and multi-channel lighting
modules 6100, 6200, 6300, 6400 described herein with respect to
FIGS. 61-64. In a third embodiment, the receiver 3602 further
comprises dip switches and the user selects the settings on the dip
switches to program the receiver's zone number. In a fourth
embodiment, the receiver 3602 learns the zone number contained in
any command it receives as long as a "learn" button is selected on
the receiver 3602. In a fifth embodiment, the receiver 3602
receives a "teach zone" RF command that would be accepted for a
short time after power up. Other approaches can be thought of by
those skilled in the art from the disclosure herein.
[0241] In embodiment illustrated in FIG. 35, the zone number is
stored in each transmitter 3504 and the user would assign a zone
number to each transmitter 3504 by entering the zone number into
the transmitter 3504. One approach is to provide the transmitter
3504 with the low voltage input to program the zone number using
the same or substantially similar method as is used to program zone
numbers in the single and multi-channel lighting modules 6100,
6200, 6300, 6400 described herein with respect to FIGS. 61-64. In
other embodiments, any of the methods described above with respect
to programming the zone number in the receiver 3602 can be used for
the transmitter 3504.
[0242] Frequency of operation--In embodiments in the US, the most
common frequencies for the RF link communications would be the ISM
bands of 902-928 MHZ, 2.4 GHZ and 5.8 GHZ. Transmission in the
260-470 MHZ band is allowed but at a much lower power level. In
most of Europe, the bands would be 433 MHZ, 868 MHZ, and 2.4 GHZ.
In other embodiments, other frequency bands may be allowed
depending on the country.
[0243] Standards--In some embodiments, wireless standards such as
the various parts of 802.11 could be used. These can include, for
example, Zigbee.RTM., Bluetooth.RTM., and the like.
[0244] Pairing--As described herein, the embodiment illustrated in
FIG. 35 comprises at least a first transmitter 3504 and a first
receiver 3502 that are paired forming a first pair to reduce
crosstalk between the other receivers 3502 and transmitters 3504
not in the first pair. In an embodiment, pairing can be achieved by
embedding an address in the RF data that must match the address of
a particular receiver 3502 in order for the receiver 3502 to accept
the data. In another embodiment, each receiver/transmitter pair
3504/3502 may operate at a different frequency in the band. In an
embodiment comprising a direct sequence spread spectrum device,
each receiver/transmitter pair 3504/3502 may use a different
correlation key. In an embodiment comprising a frequency hopping
spread spectrum system, each receiver/transmitter pair 3504/3502
may use a different hopping sequence, speed, or set of frequencies.
In the embodiment illustrated in FIG. 36, pairing between the
transmitter 3604 and the plurality of receivers 3602a, 3602b . . .
3602n can be used to reduce crosstalk between the lighting system
3600 and another nearby lighting system.
[0245] The lighting controller 300 described with respect to FIGS.
3-17 transforms the line voltage, such as 120 VAC to a low voltage,
such as 12 VAC, to control low voltage devices 304. The lighting
controller 1800 described with respect to FIGS. 18-26 uses the line
voltage, such as 120 VAC, to control 120 VAC devices 1804, 2704.
The control nodes 2700, 2800, 3200 described with respect to FIGS.
27-36 permit the low voltage controller, such as the lighting
controller 300, to control 120 VAC devices 1804, 2704. In other
embodiments, a low voltage control node permits a high voltage
system, such as the lighting controller 1800 to control low voltage
devices 304, such as 12 VAC lighting devices 304. Both wired and
wireless embodiments of a low voltage control node are described
below with respect to FIGS. 37 and 38.
[0246] FIG. 37 is a block diagram of an exemplary wired low voltage
control node 3700. The low voltage control node 3700 electrically
couples to the two-wire path 1836 and receives the data encoded
line voltage power signals from the two-wire path 1836. In an
embodiment, the line voltage power signals are approximately 120
VAC 60 Hz. In other embodiments, the data encoded line voltage
power signals can be an approximately 110 VAC 60 Hz, 220 VAC 50 or
60 Hz, 230 VAC 50 or 60 Hz, 240 VAC 50 or 60 Hz, or the like.
[0247] The wired line voltage control node 3700 is assigned a
lighting zone via the operator interface panel 308 as described
herein. Based on the information contained on the two-wire path
1836 addressed to the low voltage control node 3700, the line
voltage control node 3700 controls 12 VAC devices 304. In an
embodiment, the 12 VAC devices 304 are dimmable lighting
devices.
[0248] The architecture of the wired low voltage control node 3700
is similar to the architecture of the wired line voltage control
node 2800 described in FIG. 28. The wired line voltage control node
2800 receives commands from the data encoded 12 VAC two-wire path
336 and provides lighting control over the 120 VAC line voltage
signals to 120 VAC devices 1804, 2704, whereas the wired low
voltage control node 3700 receives commands from the data encoded
120 VAC two-wire path 1836 and provides lighting control over the
12 VAC power lines to 12 VAC lighting devices 304. The triac 2818
in the line voltage control node 2800 receives the 120 VAC line
voltage, whereas a corresponding triac in the low voltage control
node 2700 receives the 12 VAC low voltage.
[0249] FIG. 38 is a block diagram of an exemplary wireless low
voltage control node 3800 comprising a 12 VAC interface wireless
receiver 3802 and a 120 VAC interface wireless transmitter 3804
communicating over an RF link. The 120 VAC interface wireless
transmitter 3804 electrically connects to the data encoded 120 VAC
two-wire path 1836 and receives control data via the two-wire path
1836. The 120 VAC interface wireless transmitter 3804 sends over
the wireless link the control commands to the 12 VAC interface
wireless receiver 3802. The 12 VAC interface wireless receiver 3802
electrically connects to the 12 VAC line voltage and the 12 VAC
lighting device 304, and receives the control data over the
wireless link from the 120 VAC interface wireless transmitter 3804.
The 12 VAC interface wireless receiver 3802 controls the dimming
level of the lighting device 304 based at least in part on the
control data received from the 120 VAC interface wireless
transmitter 3804.
[0250] In an embodiment, the architecture of the 12 VAC interface
wireless receiver 3802 is similar to the architecture of the
wireless line voltage control node receiver 3400, and the
architecture of the 120 VAC interface wireless transmitter 3804 is
similar to the architecture of the wireless line voltage control
node transmitter 3300. The wireless line voltage control node
transmitter 3300 receives the control commands from the 12 VAC
two-wire path 336 and transmits over the RF link an RF signal based
at least in part on the control commands. The wireless line voltage
control node receiver 3400 receives the RF signal over the RF link
and provides power control over the 120 VAC lines based on the
received commands to the 120 VAC lighting devices 2704. In a
complementary manner, the 120 VAC interface wireless transmitter
3804 receives the control commands from the 120 VAC two-wire path
1836 and transmits over the RF link an RF signal based at least in
part on the control commands. The 12 VAC interface wireless
receiver 3802 receives the RF signal over the RF link and provides
power control over the 12 VAC lines to 12 VAC lighting devices
304.
[0251] In other embodiments, the 120 VAC interface transmitter 3804
and the 12 VAC interface wireless receiver 3802 can be replaced
with transceivers, as described herein with respect to FIGS. 32-34.
In other embodiments, each 12 VAC interface wireless receiver 3802
can be paired with a corresponding 120 VAC interface wireless
transmitter 3804, as described herein with respect to FIG. 35. In
further embodiments, a plurality of 12 VAC interface wireless
receivers 3802 can be paired with one 120 VAC interface wireless
transmitter 3804 in a star architecture as described herein with
respect to FIG. 36.
[0252] FIG. 39 is a block diagram of an exemplary low voltage
decoder 3900 configured to permit the lighting controller 300 to
dim a lighting device 3916. In an embodiment, the lighting device
3916 comprises a wide variety of 12 VAC lighting devices, such as
incandescent lights, fluorescent lights, LEDs, and the like. The
low voltage controller 3900 comprises a full wave rectifier 3902, a
voltage regulator 3904, a conditioning circuit 3906, a
microcontroller 3910, and a triac 3918.
[0253] The full wave rectifier 3902, the voltage regulator 3904,
the conditioning circuit 3906, the microcontroller 3910 are the
same as or substantially similar to the circuitry described herein
with respect to FIG. 28 for the wired line voltage control node
2800 and as described herein with respect to FIGS. 61-64 for single
and multi-channel lighting modules 6100, 6200, 6300, 6400. In the
lighting modules 6100, 6200, 6300, 6400, the microcontroller
controls the LED driver to vary the brightness of the LED. Both the
line voltage control node 2800 and the low voltage controller 3900
control the triac conduction angle to control dimming. In the line
voltage control node 2800, the triac 2818 receives the 120 VAC line
voltage, whereas in the low voltage controller 3900 the triac 3918
receives the data encoded 12 VAC low voltage signals from the
two-wire path 336. Because the triac 3918 receives the low voltage
signal as opposed to a high voltage signal, no optical isolation is
used.
[0254] In a manner similar to that described in FIGS. 28-31, the
microcontroller 3910 triggers the triac 3918 with a delay time
based at least in part on the desired output intensity of the 12
VAC lighting device 3916. The microcontroller 3910 creates output
voltages approximately equal to or less than the input line voltage
by delaying the triac trigger.
[0255] In the embodiment illustrated in FIG. 39, the triac 3918 is
used as the dimming device. The triac 3918 can be, for example, a
BTA208-800 from NXP Semiconductor and the like. In other
embodiments, the dimming device can be, for example, MOSFETs,
Bipolar Junction Transistors (BJTs), and Insulated Bipolar
Transistors (IGBTs), and the like. In yet other embodiments, the
triac 3918 could be replaced with a relay to provide simple ON/OFF
control for a zone comprising a fountain, or the like.
[0256] The low voltage decoder 3900 further comprises an optional
user interface 3912 having buttons, slide switches, or other forms
of user controls to permit the user to manually control the
lighting device 3916, in addition to the commands originating from
the user interface panel 308.
[0257] The low voltage decoder 3900 further comprises an LED 3908.
In an embodiment, the LED 3908 is a low power LED not intended for
illumination. The LED 3908 has the ability to "flash out" its
serial number in a manner the same as or substantially similar to
that of lighting modules 4004 described in further detail herein
with respect to FIGS. 40-42.
[0258] FIG. 40 illustrates an exemplary lighting system 4000. The
lighting system 4000 comprises a lighting controller 4002 connected
to a plurality of lighting modules 4004 through a two-wire
interface. The lighting controller 4002 comprises the power supply
302 and the user interface panel 308, which is the same or similar
to that as described herein with respect to FIG. 3. The lighting
fixtures 4004 are grouped into zones 4006.
[0259] In the example illustrated in FIG. 40, zone 1 4006a
comprises lighting fixture 4004a, zone 2 4006b comprises lighting
fixtures 4004b, 4004c, 4004d, zone 3 4006c comprises lighting
fixtures 4004e, 4004f, 4004g, and zone 4 4006d comprises lighting
fixture 4004h. In other embodiments, the lighting system 4000 can
be configured with more or less zones 4006 and/or with more or less
lighting fixtures 4004 in each zone 4006. Additional fixtures need
not be wired to the end of the line. Instead, the user may elect to
"branch" or "T" connect another leg of lights anywhere along the
2-wire path.
[0260] The lighting system 4000 further comprises a remote device
4008 and a wireless receiver 4010 to send addresses/data/commands
to the lighting modules 4004. In an embodiment, the remote 4008 can
be a digital device, a smart phone, an iPhone, an application for a
smartphone, an application for an iPhone, or the like. The wireless
receiver 4010 wirelessly connects to the remote 4008 through radio
frequency (RF) transmissions and electrically connects through a
wire to the lighting controller 4002.
[0261] In an embodiment, the remote 4008 sends
addresses/data/commands to the receiver 4010 using a standard
wireless protocol, such as, for example, Zigbee.RTM. or
Bluetooth.RTM.. The receiver 4010, in an embodiment, operates in a
license or a license-free band of frequencies. Examples of
license-free bands in the United States are 270 MHz to 460 MHz; and
the Industrial, Scientific, and Medical Band, 902 MHz to 928 MHz,
and 2.4 GHz. The receiver 4010 can be a single or a dual-conversion
receiver disclosed with reference to wireless technology as is
known to one of skill in the art recognized from the disclosure
herein. Other communication possibilities, like cell phone,
applications for a cell phone or personal digital assistant (PDA)
or other personal computing device, optical, wired, satellite or
the like, can be used to communicate with the remote 4008.
[0262] The receiver 4010 receives the addresses/data/commands from
the remote 4008 and transmits them to the lighting controller 300
via wire or other communication medium. The lighting controller 300
receives the addresses/data/commands from the receiver 4010,
processes the commands and sends data and commands on the two-wire
path to the addressed lighting modules 4004, where the commands are
decoded and performed by the addressed lighting modules 4004.
[0263] For example, an operator can be standing in front of a
lighting module 4004 or a zone 4006 can turn the lighting modules
4004 ON or OFF, adjust the brightness, determine what hue from the
lights looks best, and the like. As the operator enters commands,
the commands are translated to allow the program at the lighting
controller 4002 to be responsive. The lighting controller 4002 then
sends data embedded in the power signal to the fixtures 4004 or the
zones 4006. Thus, the remote 4008 works interactively with the
power supply 302, for example, via the receiver 4010, to mix the
red, green, and blue coefficients of any particular lighting module
4004 or group of lighting modules 4006.
[0264] In another embodiment, the homeowner talks on the phone to a
remote programmer who enters the information in a computing device,
such as a browser or application, which through known Internet or
other communication protocols, updates the lighting module
behavior. Although disclosed with reference to several embodiments,
a skilled artisan would know from the disclosure herein many
possible interactive methods of using remote computing devices to
program module behavior.
[0265] FIG. 41 depicts an embodiment of the remote device 4008. In
one embodiment, the remote 4008 is a key fob type device. In
another embodiment, the remote 4008 is a larger hand-held device.
The remote 4008 comprises a display 4102 to provide operator
feedback and input buttons 4104 to receive operator input.
[0266] FIG. 42 is a block diagram of an exemplary remote device
4008, according to an embodiment. The remote 4008 comprises a photo
diode 4202, an RF transmitter 4204, a battery 4206, a voltage
regulator 4208, an operator interface 4210, a display 4212, and a
computer 4214 with associated memory (not shown). In an embodiment,
the operator interface 4210 comprises buttons, knobs, and the like,
although touch screen, voice or other user interaction could be
implemented. The photo diode 4202 optically couples to the lighting
module 4004 and electrically communicates to the processor 4214.
The processor 4214 also electrically communicates with the operator
interface 4210, the display 4212 and the RF transmitter 4204.
[0267] In an embodiment, the photo diode is a PDB-C134 available
from Advanced Photonix Inc., or the like. A phototransistor could
also be used, but would have a slower response time. The RF
transmitter 2004 can be a CC1050 available from Texas Instruments,
or the like.
[0268] The computer 4214 comprises devices similar to those
disclosed in the foregoing.
[0269] The battery 4206 provides a power signal to the voltage
regulator 4208, which provides the proper power waveform to power
the circuitry within the remote 4008, as is known to one of skill
in the art from the disclosure herein.
[0270] Often, the lighting fixtures 4004 are assigned their address
or their lighting zone 4006 before they are placed in a location.
The fixture programming port 318 on the operator interface panel
308 can be used to program an address and/or zone 4006 into the
lighting module 4004. Once the fixtures are located, such as in the
ground, mounted to a wall, or the like, it can be cumbersome to
disconnect or uninstall the fixture 4004 to bring it proximate to
the fixture programming port 318 for zone reallocation. In an
embodiment, the optical interface between the lighting modules 4004
and the remote 4008 can advantageously be used to change the
lighting group 4006 of the fixtures 4004 without disconnecting or
uninstalling it.
[0271] In an embodiment, the lighting modules 4004 comprise at
least one light emitting diode (LED). The user sends a command to
the lighting controller 300 to instruct every lighting module 4004
to flash or strobe its address using its at least one LED by
selecting the appropriate button or knob on the remote's operator
interface 4210.
[0272] Each lighting module 4004 comprises a unique address in
addition to a group or zone number. In one embodiment, the lighting
module address comprises a 16-bit address, having approximately
65,000 unique values. Other embodiments of the lighting module
address can have more or less bits. Commands from the remote 4008
can target a specific lighting module 4004 using the unique address
or a group of lighting modules 4004 using a zone address to turn
the module 4004 ON/OFF, dim, brighten, adjust the color, adjust the
hue, adjust the intensity, or the like.
[0273] As described above, the remote 4008 transmits the command to
the wireless receiver 4010 using the wireless protocol. The
wireless receiver 4010 receives the command and electrically
converts the signal, which is then electrically sent to the power
supply 302. In an embodiment, the receiver 4010 converts the RF
signal to a baseband signal. The power supply 302 receives and
interprets the command, and electrically sends a command to the
lighting modules 4004 over the two-wire path to flash their
addresses. For example, the LED could turn ON to represent a 1
address bit and turn OFF to represent a 0 address bit.
[0274] The user selects a lighting module 4004 to assign to a
different zone 4006 by pointing the remote 4008 at the selected
lighting module 4004 such that the photo diode 4202 receives the
optical address from the flashing LED. The photo diode 4202
converts the optical address into an electrical signal and sends
the address to the processor 4214.
[0275] In an embodiment where the remote 4008 is a smart phone
comprising a camera, an iPhone comprising a camera, an application
for a smartphone comprising a camera, an application for an iPhone
comprising a camera, or the like, the camera receives the optical
address from the flashing LED. The smartphone or iPhone and
associated circuitry known to one of skill in the art from the
disclosure herein converts the optical address into an electrical
signal and sends the address to the processor 4214.
[0276] The processor 4214 sends the address to the RF transmitter
4204, where it is up converted and transmitted via an antenna 4216
on the remote 4008 to the wireless receiver 4010. The wireless
receiver 4010 receives the RF transmission, down converts it, and
transmits the address to the lighting controller 300. The power
supply 302 in the lighting controller 300 receives the address and
transmits a command to the selected lighting module 4004 to change
its zone 4006. When the selected lighting module 4004 receives and
executes the command, the lighting modules 4004 stop flashing their
addresses.
[0277] Alternatively, in another embodiment, the module 4004 is
numbered and the operator manually enters the number into the
remote 4008. In yet another embodiment, where the remote 4008 is a
smart phone comprising a camera, an iPhone comprising a camera, an
application for a smartphone comprising a camera, an application
for an iPhone comprising a camera, or the like, the address of the
module 4004 is bar coded and the smartphone or iPhone camera reads
the bar code from the module 4004.
[0278] In another embodiment, the lighting modules 4004 comprise a
photo diode and the remote 4008 comprises an LED in addition to the
RF transmitter 4204, the operator interface 4210, the display 4212,
the processor 4214, the voltage regulator 4208 and the battery
4206. The remote 4008 optically sends commands and data by flashing
or strobing its LED, which are received by the photo diode in the
lighting module 4004, similar to the way a TV receives a signal
from a handheld TV remote. The flashing would typically be so
rapid, that it would not be perceived by the human eye. The remote
4008 also transmits data and commands to the RF receiver 4010 using
the wireless protocol, which in turn sends the messages via wire to
the lighting controller 300, as described above.
[0279] Referring to FIG. 3, the lighting controller 300 comprises
the user interface panel 308 electrically coupled to the power
supply 302 and mechanically attached to the chassis. In other
embodiments, the user interface panel 308 can be remoted
wirelessly. FIG. 43 is a block diagram of an exemplary lighting
controller 4300 comprising a remote operator interface panel 4308,
a power supply 302, and a pair of RF transceivers 4302, 4304
providing an RF communication link between the remote panel 4308
and the power supply 302. In an embodiment, the RF communication
protocol is implemented so that the remote user interface panel
4308 functions the same as the integral user interface panel 308.
The panel RF transceiver 4304 electrically connects to the panel
4308 and the chassis RF transceiver 4302 electrically connects to
the power supply 302 in the chassis.
[0280] In an embodiment, the panel transceiver 4304 comprises an
integrated battery 4306 to power the user interface panel 4308,
permitting the user interface panel 4308 to be carried around for
remote operation. In another embodiment, the user interface panel
4308 can be powered by a power supply at the remote location, via
an adapter 4306, such as if it is permanently mounted indoors,
remote from the power supply 302.
[0281] As illustrated in FIG. 43, the user interface panel 4308 is
separated from the chassis/power supply 302, and the two are linked
via an RF link between the panel RF transceiver 4304 and the
chassis RF transceiver 4302. In an embodiment, the protocol used by
the chassis RF transceiver 4302 emulates the user interface panel
4308 and the protocol used by the panel RF transceiver 4304
emulates the power supply 302. Thus, the communication between the
remote user interface 4308 and the chassis/power supply 302 is the
same or substantially similar to the communication between the
integral user interface panel 308 and the chassis/power supply 302.
This allows retrofitting into lighting controllers that were
previous hardwired.
[0282] In addition to the RF circuitry, the transceivers 4302, 4304
also comprise processors. FIG. 44 is a block diagram of an
exemplary panel transceiver 4400 for a remote operator interface
panel 4450 and FIG. 45 is a block diagram of an exemplary chassis
transceiver 4500 for a lighting system chassis 4550.
[0283] The panel RF transceiver 4400 comprises an RF transceiver
4402, a microcontroller 4404, address selection circuitry 4408, a
battery/adapter 4406, and a voltage regulator 4410. The
microcontroller 4404 electrically couples to the address selection
circuitry 4408 and the RF transceiver 4402, and the battery/adapter
4406 electrically couples to the voltage regulator 4410. The
operator interface panel 4450 comprises a microcontroller 4414 and
a voltage regulator 4420. The microcontroller 4414 communicates
with the microcontroller 4404 in the panel transceiver 4400 and the
voltage regulator 4420 electrically couples to the battery/adapter
4406.
[0284] Similarly, the chassis RF transceiver 4500 comprises an RF
transceiver 4502, a microcontroller 4504, address selection
circuitry 4508, and a voltage regulator 4510. The microcontroller
4504 electrically couples to the address selection circuitry 4508
and the RF transceiver 4502. The chassis 4550 comprises a
microcontroller 4514 and pre-regulated power circuitry 4506. The
chassis microcontroller 4514 communicates with the microcontroller
4504 in the chassis transceiver 4500 and the pre-regulated power
circuitry 4506 electrically couples to the voltage regulator
4510.
[0285] In an embodiment, a common hardware platform for the
microcontrollers 4404, 4414, 4504, 4514 is used. In other
embodiments, RF circuitry with no intelligence interfaces with the
microcontrollers 4414, 4514.
[0286] The address selection circuitry 4408, 4508 provides an
address selection input to the respective transceivers 4404, 4504.
The address selection circuitry 4408, 4508 allows the transceivers
4404, 4504 to communicate with each other while rejecting any RF
information meant for others. In a first embodiment, the address
selection circuitry 4408, 4508 is a dial or one or more DIP
switches, which are settable by the user. In a second embodiment,
the address of the user interface panel transceiver 4404 is set
using a display on the panel 4450 for user interface panel firmware
that is aware of the RF transceiver 4404. Once the address is set
in the panel RF transceiver 4404, it could be "taught" to the
chassis RF transceiver 4504. In a further embodiment, the chassis
RF transceiver 4504 further comprises a "learn button", and while
the learn button is in a first state, the chassis RF transceiver
4504 learns the address of any valid message received. In yet other
embodiments, one of the transceivers 4404, 4504 enters the learn
mode for a time period after power up. Other addressing scheme
embodiments may be possible by those skilled in the art from the
disclosure herein.
[0287] There are considerations of frequency of operation, wireless
standards, and pairing to avoid crosstalk for the RF communication
link between the transceivers 4400, 4500 which are the same as or
similar to those discussed herein with respect to FIGS. 32-36 for
the RF communications for the wireless line voltage control node
3200.
[0288] FIG. 46 is a block diagram of an exemplary optical reader
4600 configured to read the flashing address of the selected
lighting device 4004 in order to change the zone number of an
installed lighting device without wiring modifications to
previously installed lighting. The method of changing the zone
number of an installed lighting device is the same as or similar to
the method described herein with respect to FIGS. 40-42 in the
lighting system 4000 using the remote 4008. The remote 4008, in one
embodiment as previously described, comprises the optical reception
circuitry 4202 and RF transmitter circuitry 4204 and wirelessly
transmits the optically received address to the receiver 4010,
which electrically couples to the lighting controller 4002. The
remote 4008, in another embodiment as previously described,
comprises a smartphone or other intelligent device with a camera
where the camera is used to capture the flashing address, which is
transmitted to the lighting controller 4002 via the receiver
4010.
[0289] Whereas, in an embodiment, the optical reader 4600
electrically connects to an intelligent electronic device 4650,
such as a smartphone, tablet PC, or the like, through its headset
jack, and sends the received address to an application running in
the intelligent electronic device 4650. The intelligent electronic
device 4650 then sends the address to the lighting controller via a
router and WiFi module, such as lighting controller 4702, router
4708, and WiFi.RTM. module 4710 as described herein with respect to
FIG. 47. The application resides in the intelligent electronic
device/smartphone 4650 and is configured to change the zone number
of a previously installed light 4004, 4704 without wiring
modifications. In an embodiment, the application is a proprietary
application. In another embodiment, the intelligent electronic
device/smartphone 4650 may communicate to the controller 4002, 4702
via ad hoc or other peer to peer communication protocol.
[0290] Referring to FIG. 46, the optical reader 4600 comprises a
photodiode 4602, a band pass amplifier 4604, a microcontroller
4606, an optional low pass filter 4608, a full wave rectifier and
filter 4610, a voltage regulator 4612, and an optional battery
4614. The full wave rectifier and filter 4610, the voltage
regulator 4612, and the battery 4614 comprise power supply options
for the optical reader 4600. Power can be derived from either
rectifying, filtering, and regulating an audio signal from the
intelligent electronic device/smartphone headset circuitry, or from
the battery 4614. For instance, prior to reading the data, the
application could power the optical reader 4600 by sending a
constant tone, such as 1 kHz or the like, for example, of high
volume audio to the headset jack. The optical reader 4600
rectifies, filters, boosts if needed, and regulates the audio
signal into a power source for the rest of the optical reader
circuitry. In situations where the user has disabled the headset
volume, the battery 4614 can supply power to the optical reader
circuitry. Examples of the battery 4614 are a CR2032 lithium coin
cell and the like.
[0291] Once powered, the optical reader 4600 would look for a valid
optical transmission signal, verify the checksum, and then send the
information to the application via the microphone input of the
headset jack. The flashing light from the lighting module 4004 is
incident upon the photodiode 4602, which outputs a current in
response to the light. The band pass amplifier 4604 amplifies the
current, converts the amplified current into a voltage signal, and
filters the voltage signal to pass only the frequencies of
interest.
[0292] In one embodiment, the amplifier 4604 has sufficient gain to
"square up" the filtered voltage signal so that it can be input
directly into a digital input of the microcontroller 4606. In
another embodiment, filtered voltage signal is input into a
comparator input of the microcontroller 4606, which squares the
signal. In a further embodiment, the filtered voltage signal is
input into an analog input of the microcontroller 4606, read by an
on-board ND converter, and processed. The microcontroller 4606
receives the optical data as a digital signal and verifies its
validity via a checksum. Once a valid message is received, the
optical reader 4600 sends an audio frequency signal based on the
valid message to the microphone input of the intelligent electronic
device/smartphone 4650.
[0293] The audio frequency signal can be modulated using AM, FM,
FSK, OOK or any other modulation technique. In one embodiment, the
optical reader 4600 frequency shift keys (FSK) an audio frequency
signal into the microphone of the intelligent electronic
device/smartphone 4650. A logic zero comprises 1000 Hz signal and a
logic one comprises 1500 Hz signal, for example. In another
embodiment, ON-OFF key modulation (00K) can be used. A logic one
comprises a tone of 1 kHz and a logic zero comprises silence, for
example. In another embodiment, the microcontroller 4606 sends each
received bit to the intelligent electronic device/smartphone 4650
without validating the message and application validates the
message.
[0294] FIG. 47 illustrates an exemplary lighting system 4700
controlled remotely, according to an embodiment. The lighting
system 4700 comprises a lighting controller 4702, and a plurality
of lighting modules 4704 configured into a plurality of zones 4706.
In the illustrated embodiment, zone 1 4706a comprises one lighting
fixture 4704a; zone 2 4706b comprises three lighting fixtures
4704b, 4704c, 4704d, and zone 3 4706c comprises three lighting
fixtures 4704f, 4704g, 4704h. The lighting controller 4702
comprises the power supply 302 and the operator interface 308. The
lighting controller 4702 sends the data encoded power waveform to
the plurality of lighting modules 4704 on the two-wire path, as
described above.
[0295] The lighting system 4700 further comprises a wireless module
4710, which electrically couples, via wire or other mediums, to the
lighting controller 4702. The wireless module 4710 communicates
wirelessly to devices, such as a smartphone 4714, a laptop computer
4716, and other devices that have WiFi.TM. connection capability
using a peer to peer communication mode such as ad hoc. In this
communication mode, custom software, firmware, applications,
programs, or the like, are written for both the wireless module
4710 and the communicating device 4714, 4716. In an embodiment,
this proprietary communication approach is not constrained by
conventional standards, such as the 802.11 standard and its
versions, for example.
[0296] The user can send commands from the smart phone 4714, the
laptop computer 4716, or other communicating devices within the
range of the wireless module 4710 to remotely control the lighting
system 4700. For example, the user can send commands to turn
ON/OFF, adjust the brightness, adjust the color, adjust the hue,
and the like for the lighting system 4700, a zone 4706, or a
specific lighting module 4704 from the remote device 4714, 4716. In
an embodiment, the user views the web page being served by the
wireless module 4710 by, for example, opening up the Internet
Explorer.RTM. or other web browser on the smartphone 4714 or the
laptop 4716. The user then interacts with the web page to control
the lighting system 4700. In another embodiment, the web page is
served from the computer in the lighting controller 4702, and the
wireless module 4710 provides the RF connectivity.
[0297] The wireless module 4710 wirelessly receives the commands
using the ad hoc or other peer to peer protocol, electrically
converts the signal and sends the lighting commands, via wire, to
the lighting controller 4702. In an embodiment, the module 4710
converts the signal to base band. The lighting controller 4702
receives the commands and sends the message to the addressed
lighting modules 4704 or the lighting modules 4704 in the specified
zones 4706 via the two-wire path.
[0298] In another embodiment, the lighting system further comprises
a wireless router 4708 and the wireless module 4710 is a WiFi.TM.
enabled device. WiFi.TM. enabled wireless devices, such as laptops
or computers 4716, 4720, smartphones 4714, WiFi.TM. enabled
automobiles 4722, or the like, communicate with the router 4708
using a standard communication protocol, such as 802.11. In other
embodiments, a device, such as a computer 4718 is electrically
connected, via wire or a cable, to the router 4708. The user uses
the devices 4714, 4716, 4718, 4720, 4722 to send commands to the
lighting system 4700. The devices 4714, 4716, 4718, 4720, 4722 send
the commands through the router 4708 using a standard router
protocol. The router 4708 connects to the World Wide Web 4712 using
an Internet Service Provider (ISP) and an Internet connection. In
another embodiment, the smartphone 4714 communicates through the
Internet using a general packet radio service (GPRS) protocol.
[0299] In one embodiment, the wireless module 4710 comprises the
router 4708. In another embodiment, the lighting controller 4702
comprises the router 4708.
[0300] The devices 4714, 4716, 4718, 4720, 4722 access the WiFi.TM.
enabled wireless module 4710 through its Internet Protocol (IP)
address. The module 4710 sends the commands to the lighting
controller 4702, where the lighting controller sends the command to
the lighting modules 4704 through the two-wire path. In this
manner, a user can access the lighting system 4700 from anywhere
there is an Internet connection.
[0301] In a further embodiment, the module 4710 comprises an
Ethernet module for communication using an Ethernet protocol via an
Ethernet cable between the controller 4702 and the router 4708
and/or between two controllers 4702. Examples of Ethernet modules
are model MDL-2CE available from Texas Instruments or the like.
[0302] FIG. 48 illustrates another exemplary lighting system 4800
controlled remotely. The lighting system 4800 comprises the
plurality of lighting fixtures 4704 configured in the one or more
zones 4706 and the lighting controller 4802. The lighting
controller 4802 sends the data encoded power waveform to the
plurality of lighting devices 4704 over the two-wire path, as
described herein.
[0303] The lighting system 4800 further comprises a mobile carrier
network module 4804, which electrically couples, via wire or other
mediums, to the lighting controller 4802. The module 4804
communicates to the World Wide Web (WWW) 4712 via a mobile
carrier's network. Depending on the location and carrier, various
standards, such as GPRS, GSM, and CDMA, and the like may apply. A
suitable GPRS and GSM module, for example, is model number
MTSMC-G-F4 available from Multitech Systems Inc. and the like. A
suitable CDMA module, for example, is model MTSMC-C1-IP-N3
available from Multitech Systems Inc.
[0304] The lighting controller 4802 can be accessed by devices,
such as laptops or computers 4720, smartphones 4714, web-enabled
automobiles 4722, or the like, in communication with the WWW 4712
from any location. Further, the lighting controller 4802 can be
accessed by a wireless router 4708 in communication with the WWW
4712 via an Internet service provider (ISP). Local devices, such as
laptops or computers 4716, typically in proximity to the wireless
router 4708 and typically communicating with the router 2708 using
a standard communication protocol, such as 802.11 can also access
the lighting controller 4802. In other embodiments, a device, such
as the computer 4718 is electrically connected, via wire or a
cable, to the router 4708. In one embodiment, the lighting
controller 4802 comprises the router 4708.
[0305] The user uses the devices 4714, 4716, 4718, 4720, 4722 to
send commands to the lighting system 4800. In a first embodiment,
firmware either inside the lighting controller 4802 or in the
module 4804 serves up a webpage. As long as the module 4804 can be
found on the World Wide Web 4712, that webpage could be accessed by
devices with a web browser, thus allowing control of the lighting
controller 4802. This is similar to the control provided by the
WI-FI module 4710 discussed herein with respect to FIG. 47.
[0306] In a second embodiment, an application is provided for
application-enabled devices, such as the control devices 4714,
4716, 4718, 4720, 4722. The user interacts with the application,
and the application communications with the module 4804 via the
World Wide Web 4712. In an embodiment, the application is written
for various platforms, such as iPhone, Android, or the like.
[0307] In a third embodiment, a web based application 4806 is
hosted on a server on the World Wide Web 4712. In an embodiment,
this application 4806 is larger/more complex than could be stored
in the lighting controller 4802 or the module 4804. The user
interacts with this webpage 4806 using devices comprising a web
browser and the application 4806 communicates with the lighting
controller 4802.
[0308] There are some practical considerations when using mobile
carrier networks. Most mobile carriers actually have far fewer IP
addresses than they do subscribers. This is because at any given
point in time, only a fraction of the subscribers is interacting
with the web. Therefore, after some time of inactivity, a mobile
device will typically lose its IP address. If the mobile device
goes online again, the network will issue a new (different) IP
address. Furthermore, many times the IP addresses used by mobile
carriers are private, not public, meaning they cannot be reached
using the World Wide Web 4712. The significance of this is that if
a user wants to connect with a device on a carrier's network, they
must know the IP address of that device.
[0309] Understanding that people want to use their networks to
communicate with, and control devices, most carriers have
workarounds for this problem. For instance, they often allow
companies to set up special servers that have access to the private
IP address of the devices they sell. This sort of "proxy" server
would itself have a fixed IP address and would be easily accessible
from anyone on the WWW 4712. The server would use an authentication
technique or password to allow a user in communication with it, to
access only those remote (private IP) nodes associated with the
users account. In a sense, the server is a "conduit" to reach the
private IP device.
[0310] This approach may be combined with any of the three
embodiments described above. For the third embodiment, the server
may be the same device that hosts the application 4806.
[0311] FIG. 49 is a block diagram of an exemplary lighting system
4900 with a master/slave configuration, according to an embodiment.
The lighting system 4900 comprises a first lighting controller 4902
and at least a second lighting controller 4952. Lighting Controller
4902 operates as a master controller and comprises a power supply
4908, an operator interface 4910, and a fixture programming port
4912. Lighting Controller 4952 operates as a slave to the master
controller 4902 and comprises a power supply 4958 and a slave
control panel 4960. The slave control panel 4960 comprises the
processor 314 and support circuitry, such as the memory 316, the
logic power supply 320, and the display and indicators 312. In an
embodiment, the slave control panel 4960 may not have the fixture
programming port 4912 and the operator interface devices, such as
the buttons and knobs 310. In other embodiments, the slave
controller 4952 is electrically the same as or similar to the
master controller 4902.
[0312] Each lighting controller 4902, 4952 electrically connects to
a plurality of lighting modules 4904 and to a WiFi.TM. enabled
module 4914, 4964, respectively. In the illustrated embodiment,
master controller 4902 electrically connects to lighting modules
4904a, 4904b, 4904c, and up to 4904n, and electrically connects to
module 4914. Slave controller 4952 electrically connects to
lighting modules 4904d, 4904e, 4904f, and up to 4904m, and
electrically connects to module 4964.
[0313] In one embodiment, the WiFi.TM. enabled modules 4914, 4964
communicate with each other through an ad hoc or other peer to peer
protocol, as described above with respect to FIG. 47. In another
embodiment, the WiFi.TM. enabled modules 4914, 4964 can communicate
with each other through a router 4708, also as described above with
respect to FIG. 47.
[0314] For example, a user may have a lighting system 4900 that
uses more than one lighting controller 4902 to control the lighting
modules 4904. This may be caused by the transformer 322, 402 not
being able to supply enough power to illuminate the plurality of
lighting modules 4904. In this case, the user would connect some of
the lighting modules to a first controller 4902 and others to a
second controller 4952. In one embodiment, the first and second
controllers 4902, 4952 each control the lighting modules 4904
associated with it, independent of the other controller 4902,
4952.
[0315] However, in another embodiment, the program to control all
of the lighting modules 4904 executes in one lighting controller
4902, which acts as the master controller and communicates with the
slave controller 4952. The master controller 4902 sends commands
for the slave controller 4952 to the module 4914. Module 4914
communicates wirelessly with the module 4964 and module 4964
receives the commands from the module 4914 and sends the commands
to the slave controller 4952. The slave controller 4952 receives
the commands and sends the commands to the addressed lighting
modules 4904 associated with it. Advantageously, the user can
access all of the lighting modules 4904 by entering commands from
the operator interface 4910 on the master controller 4902 or by
communicating to the IP address of only the master controller 4902
instead of having to access two lighting controllers 4902, 4952.
Another advantage is the reduced cost of the slave controller 4952,
which does not include the buttons and knobs 310, the fixture
programming port 4912, and other features not being used in the
slave controller 4952.
[0316] In another embodiment, the lighting system 4000, 4700, 4900
further comprises a motion detector. The motion detector may be
battery powered and communicate with the receiver/modules 4010,
4710, 4914. When the motion detector senses motion, it could send a
message to the lighting controller 4002, 4702, 4902, which then
turns ON the appropriate lighting modules 4004, 4704, 4904, as
programmed by the user. In one embodiment, the motion detector
receives power over the two-wire path connecting the plurality of
lighting modules 4004, 4704, 4904.
[0317] In another embodiment, the data sent to the lighting
controllers 300, 4002, 4702, 4902 is encrypted. In one embodiment,
a proprietary encryption scheme is used. In another embodiment, a
standard encryption protocol, such as TCP/IP, IPX/SPX, OSI, DLC,
SNAP, exclusive or, and the like, is used to encode the data and
commands.
[0318] FIG. 50 illustrates an exemplary lighting system 5000 with a
master/slave configuration. The lighting system 5000 comprises a
master lighting controller 5002, a slave chassis 5004, a two-wire
to chassis protocol converter 5006, and a plurality of lighting
modules. In an embodiment, the master lighting controller 5002
comprises an operator interface panel 308 while the slave chassis
5004 does not. In this embodiment, the master lighting controller
5002 controls lighting fixtures 1-6 in lighting zones 1-3 through
data encoded power signals sent over a two-wire path from the
master lighting controller 5002, and the slave chassis 5004
controls lighting fixtures 7-12 in zones 4-6 through data encoded
power signals sent over a two-wire path from the slave chassis
5004. The two-wire to chassis protocol converter 5006 receives the
commands for all of the lighting fixtures 1-12 in the lighting
system 5000 from the master lighting controller 5002 over the
master lighting controller's two-wire path and relays the commands
to the slave chassis 5004 The protocol converter 5006 permits the
user to add one or more slave chassis 5004 to the lighting system
5000 thereby increasing the number of lighting devices in the
lighting system 5000 without firmware modification, network
communication cables between master and slave controllers, and the
like. In an embodiment, all of the lighting modules are programmed
from the master lighting controller 5002 comprising the operator
interface panel 308.
[0319] In the embodiment illustrated in FIG. 50, the lighting
modules attached to the slave chassis 5004 comprise different zones
than those attached to the master lighting controller 5002. In
other embodiments, the slave chassis 5004 can control lighting
device belonging to the same zone(s) as those controlled by the
master lighting controller 5002. For example, the user may have
more lights in a single zone than can be powered by the master
lighting controller transformer. The protocol converter 5006 allows
additional lights, belonging to the same zone, to be electrically
connected to the two-wire path from the slave chassis 5004. All of
the lights in the zone could turn on together. In another
embodiment, more than one protocol converter 5006 and corresponding
slave chassis 5004 can be controlled by one master lighting
controller 5002. In a further embodiment, a cascade or serial
arrangement can be used such that a second protocol converter 5006
attaches to the slave chassis' output to control another slave
chassis 5004. In a further embodiment, multiple protocol converters
5006 and slave chassis 5004 can be chained to the output of the
previous slave chassis 5004, while maintaining one point of control
at the master lighting controller 5002.
[0320] FIG. 51 is a block diagram of an exemplary two-wire to
chassis protocol converter 5100 comprising a full wave rectifier
5102, a voltage regulator 5104, a conditioning circuit 5106, a
microcontroller 5108, an optoisolator 5110, and a transceiver 5112.
The two-wire to chassis protocol converter 5100 receives the data
encoded 12 VAC power signal from the master lighting controller
5002. The full wave rectifier 5102, the voltage regulator 5104, the
conditioning circuit 5106, and the microcontroller 5110 are the
same as or substantially similar to the circuitry described herein
with respect to in FIGS. 61-64 for single and multi-channel
lighting modules 6100, 6200, 6300, 6400. In the lighting modules
6100, 6200, 6300, 6400, the microcontroller controls the LED
driver, whereas the microcontroller 5108 of the protocol converter
5100 takes each command and "translates" it into a command that the
slave chassis 5004 understands, mimicking the operator interface
panel 308 that would have been in that chassis. The commands are
transmitted by the transceiver 5112 to the slave chassis 5004. In
an embodiment, the communication physical layer comprises an RS485
transceiver 5112. In other embodiments other physical layers such
as RS232, parallel data, controller area network (CAN) Bus, and the
like can be used.
[0321] In an embodiment, optical isolation between the
microcontroller 5108 and the RS485 transceiver 5112 is provided by
the optoisolator 5110 to correct for differential voltage between
the master lighting controller 5002 and the slave chassis 5004. If
that voltage were to exceed the common mode voltage range of the
transceiver 5112, communication could fail. In an embodiment, the
RS485 transceiver 5112 is powered from the slave chassis 5004 and
the rest of the converter circuitry 5102, 5104, 5106, 5108, is
powered from the data encoded two-wire path from the master
controller 5002.
[0322] In another embodiment, the two-wire protocol converter is
wireless. FIG. 52 illustrates an exemplary lighting system 5200
with a wireless master/slave configuration. The lighting system
5200 comprises a master lighting controller 5202, a slave chassis
5204, a wireless two-wire to chassis protocol converter comprising
a transmitter portion 5206 and a receiver portion 5208, and a
plurality of lighting modules. In this embodiment, the master
lighting controller 5202 controls lighting fixtures 1-6 in lighting
zones 1-3 through data/power signals sent over a two-wire path from
the master lighting controller 5202, and the slave chassis 5204
controls lighting fixtures 7-12 in zones 4-6 through data/power
signals sent over a two-wire path from the slave chassis 5204. The
transmitter portion 5206 of the wireless two-wire to chassis
protocol converter receives the commands for all of the lighting
fixtures 1-12 in the lighting system 5200 from the master lighting
controller 5202 over the master lighting controller's two-wire path
The transmitter portion 5206 broadcasts the commands over an RF
communication link. The receiver portion 5208 of the wireless
two-wire to chassis protocol converter receives the commands over
the RF communication link, decodes the commands, and instructs the
slave chassis to output the commands on its two-wire path.
Advantageously, the wireless protocol converter 5206, 5208 does not
need proximity to the slave chassis 5204, as does the wired
protocol converter 5006, 5100. In addition, multiple receiver
portions 5208 that are within the RF transmission range of the
transmitter portion 5206 can receive commands and send the commands
to their corresponding slave chassis 5204.
[0323] FIG. 53 is a block diagram of an exemplary transmitter
portion 5300 for the wireless two-wire chassis protocol converter.
The transmitter portion 5300 comprises a full wave rectifier 5302,
a voltage regulator 5304, a conditioning circuit 5306, a
microcontroller 5308, and a transmitter 5310. The circuitry is
similar to wireless line voltage control node transmitter 3300
described herein with respect to FIG. 33, except that the
transmitter portion 5300 transmits every command it receives from
the master lighting controller 5202.
[0324] FIG. 54 is a block diagram of an exemplary receiver portion
5400 for the wireless two-wire chassis protocol converter. The
receiver portion 5400 comprises a receiver/transceiver 5402, a
voltage regulator 5404, a microcontroller 5408, and a transceiver
5412. The voltage regulator 5404 receives power from the power
source in slave chassis 5204 that would have powered the operator
interface panel 308. The receiver/transceiver 5402 receives the
commands via the RF link and sends the information to the
microcontroller 5408. The microcontroller 5408 instructs the slave
chassis 5204 via the transceiver 5412 to output the commands over
its two-wire path to the lighting modules. In an embodiment, the
communication physical layer comprises an RS485 transceiver 5412.
In other embodiments other physical layers such as RS232, parallel
data, controller area network (CAN) Bus, and the like can be
used.
[0325] The receiver portion 5400 further comprises an optional user
interface 5406 in case configured to provide manual control at the
slave chassis 5204, and an LED 5410 for feedback such as health and
power, as described herein.
[0326] Similar to the wireless line voltage control node 3200
described herein with respect to FIGS. 34-36, the wireless two-wire
chassis protocol converter 5206, 5208 supports a system where a
single transmitter portion 5300 can be linked with one or more
receiver portions 5400 as are in range. Each receiver portion 5400
is linked to a separate slave chassis 5204, thus making it possible
to expand the number of lights under control of the master lighting
controller 5402 to very large numbers. Such an embodiment is
illustrated in FIG. 55.
[0327] FIG. 55 is a block diagram of an exemplary lighting system
5500 for a wireless two-wire chassis protocol converter comprising
a transmitter portion 5504 and one or more receiver portions 5502a,
5502b . . . 5502n. The transmitter portion 5504 electrically
couples to the data encoded two-wire signal from the master
lighting controller 5202. Each receiver 5502a, 5502b, . . . 5502n
electrically couples to a corresponding slave chassis 5506a, 5506b
. . . 5506n and each slave chassis 5506a, 5506b, . . . 5506n
electrically couples to one or more lighting modules. The
transmitter portion 5504 receives commands from the master lighting
controller 5202 and broadcasts the commands over an RF link to the
plurality of receiver portions 5502. Each receiver portion 5502a,
5502b . . . 5502n instructs its corresponding slave chassis 5506a,
5506b . . . 5506n to output its commands on its two-wire path.
[0328] In another embodiment, there can be a one-to-one pairing
between transmitter portions 5504 and receiver portions 5502 of the
wireless two-wire protocol converter.
[0329] As discussed above with respect to the RF communications for
the wireless line voltage control node in FIGS. 32-36, there are
considerations of frequency of operation, wireless standards, and
pairing to avoid crosstalk for the RF communication link.
[0330] FIG. 56 is a flowchart of an exemplary process 5600 for
encoding data onto a power signal for lighting modules 304, 4004,
4704, 4904. Beginning at block 5610, the process 5600 rectifies an
AC power signal to form a secondary VAC power waveform.
[0331] At block 5620, the process 5600 encodes the data onto the
rectified power signal by controlling the polarity of the rectified
power signal, such that at least a portion of the rectified power
waveform with a first polarity represents a 1-data bit 1304, 2604
and at least portion of the rectified power waveform with a second
polarity represents a 0-data bit 1304, 2604.
[0332] At block 5630, the process 5600 sends the data encoded power
waveform through the two-wire path to the lighting modules 304,
4004, 4704, 4904. The addressed lighting modules 304, 4004, 4704,
4904 decode the commands and perform the lighting functions, such
as turn ON/OFF, dim/brighten, change color/hue, and the like.
[0333] Looking at the process 5600 in more detail, at block 5611
the lighting controller 300, 4002, 4702, 4902 receives the primary
AC power signal. At block 5612, the process 5600 transforms the
primary AC power signal into a secondary VAC power signal. In an
embodiment, the secondary VAC power signal is between approximately
11 VAC and 14 VAC. The process 5600 determines the phase of the
secondary AC power signal at block 5613. At blocks 5614 and 56515,
the process 5600 sends the secondary AC power waveform onto
V-FULLWAVE when the phase is positive and sends the inverted
secondary AC power waveform onto V-FULLWAVE when the phase is
negative to generate the rectified secondary VAC power
waveform.
[0334] At block 5621, the process transmits the data stream as well
as the phase information, to an encoder/modulator. The data stream
comprises addresses, data, and commands. The bridge circuit 900
passes the rectified secondary power waveform onto the two-wire
path to the lighting modules 304, 4004, 4704, 4904 when the data
bit 1304, 2604 from the data stream has a first state. Further, the
bridge circuit inverts the rectified secondary waveform when the
data bit 1304, 2604 has a second state. When no data is present,
the bridge circuit reconstructs the sine wave of the secondary VAC
power waveform from the rectified secondary waveform and sends the
reconstructed secondary VAC power waveform.
[0335] At block 5631, the process 5600 transmits the data enhanced
power signal from the lighting controller 300, 4002, 4702, 4902 to
the plurality of lighting fixtures 304, 4004, 4704, 4904 on the
two-wire path. The addressed lighting modules 304, 4004, 4704, 4904
receive the data encoded power waveform. An embodiment of a
lighting module 304, 4004, 4704, 4904, its functionality, and its
operation, is disclosed in FIGS. 13-55 and accompanying disclosure
of U.S. application Ser. No. 12/564,840, filed Sep. 22, 2009,
entitled "Low Voltage Outdoor Lighting Power Source and Control
System", and are incorporated herein by reference. Other
embodiments are described below in FIGS. 61-64.
[0336] This waveform is first scaled and filtered, and is then
passed through a comparator to determine the phase of the incoming
signal which is used to decode the data bits 1304, 2604 and perform
the requested command. The data encoded power waveform is also
rectified and used to power the lighting module. It should be noted
that it is possible to store energy in the lighting module such
that no power is being supplied at those instances in time when the
actual bits of data are received.
[0337] FIG. 57 is a flowchart of an exemplary process 5700 for
assigning zones 106, 206, 4006, 4706, 4906 to addressable lighting
modules 104, 204, 4004, 4704, 4904 in the networked lighting system
100, 200, 4000, 4700, 4900, according to an embodiment. In one
embodiment, the user assigns the zone numbers into each lighting
fixture 300, 4002, 4702, 4902 through the fixture programming port
212, 318, 4912. In one embodiment, the zone numbers comprise 8 bits
and there can be up to 256 zones 106, 206, 4006, 4706, 4906. In
other embodiments, the zone numbers comprise more or less than 8
bits and there can be more or less than 256 zones 106, 206, 4006,
4706, 4906.
[0338] At block 5702 and 5704, the lighting controller periodically
queries the programming port attempting to detect a lighting
fixture that has been connected. At block 5706, the lighting
controller has detected a light fixture on the programming port and
has presented the Lighting Fixture Programming screen to the user
via the operator interface panel 210, 308, 4910 on the lighting
controller 300, 4002, 4702, 4902. Next, at block 5708, the user
enters the zone number of the lighting fixture 104, 204, 4004,
4704, 4904 to be added to the entered zone 106, 206, 4006,
4706.
[0339] At block 5710, the process 5700 sends a command to assign
the lighting fixture 104, 204, 4004, 4704, 4904 to the entered zone
106, 206, 4006, 4706, 4906.
[0340] At block 5712, the user is notified that the programming has
completed and he removes the fixture from the programming port.
[0341] FIG. 58 is a flowchart of an exemplary process 5800 for
modifying assigned zones 4006 in the lighting system 4000 using the
remote controller 4008/optical reader 4600, according to an
embodiment. At block 5802 and referring to FIGS. 40 and 46, the
user selects the change zone selection on the remote device 4008,
4600 and enters the new zone number.
[0342] At block 5804, the remote device 4008, 4600 transmits the
zone change request to the receiver 4010 via RF. The receiver 4010
sends the zone change request, via wire or other medium, to the
lighting controller 4002 at block 5806. At block 5808, the lighting
controller 4002 sends a command to the lighting modules 4004 via
the two-wire path to begin flashing their addresses. The command is
encoded onto the power waveform supplying power to the lighting
modules 4004. After receiving the command, each lighting module
4004 flashes its address using an LED on the lighting fixture
4004.
[0343] At block 5810, the user directs the remote device 4008, 4600
to the selected lighting fixture 4004. The selected lighting
fixture 4004 is the lighting fixture that the user wants to rezone.
At block 5812, the remote device 4008, 4600 receives the address of
the selected lighting fixture, via the optical path. The remote
device 4008, 4600 sends the address of the selected lighting module
4004 to the receiver 4010 via RF at block 5814.
[0344] At block 5816, the receiver 4010 sends the selected address
to the lighting controller 4002 via a wired path. The lighting
controller 4002 receives the selected address and sends a command
to the selected lighting fixture 4004 via the two-wire path. The
command is encoded onto the power waveform sent via the two-wire
path.
[0345] At block 5820, the lighting fixture 4004 decodes the command
and changes it zone 4006 to the new zone address.
[0346] In an embodiment, the lighting fixtures 104, 204, 4004,
4704, 4904 are advantageously constructed with a drive circuit,
supervising functions, communication reception, and the like,
within the fixture 104, 204, 4004, 4704, 4904 on a single printed
circuit board to lessen the need for water tight splices, sealing,
and other reliability concerns.
[0347] In another embodiment, the command protocol supports queued
commands as well as immediate commands. The queued commands allow
synchronized changes across multiple lighting groups or zones 106,
206, 4006, 4706, 4906. Several different queued commands could be
sent to different lighting zones 106, 206, 4006, 4706, 4906. The
lighting module 104, 204, 4004, 4704, 4904 remember the command but
do not act on it until an "apply queued" command is received.
[0348] In a further embodiment, an accessory device having an
optical sensor monitors the lighting fixtures when the fixtures are
flashing or strobing their addresses. The accessory device reads
the address and displays the address to the user. This is useful
because while the fixtures would be marked with their address, the
marking could be worn off or not visible after installation.
[0349] In a yet further embodiment, the lighting controller takes
inventory of the lighting modules attached by sending, either one
by one for each of the possible 65,000 unique addresses, or for a
particular range of addresses, a command to turn ON lighting
modules. Then the lighting controller monitors the current after
the command is sent to determine whether a fixture responded to the
command. Finally, the controller compiles a list of the fixture
addresses detected to be presented to the user.
[0350] In another embodiment, the power supply has a detachable
front panel with a slot designed to accept the accessory device.
When the accessory device is installed, the user detaches the front
panel, now powered and in communication with the accessory device,
and walks around the yard. The user can perform more complex remote
operations using the larger display and operator interface of the
front panel. These operations relay back to the power supply via
the RF transmitter of the accessory device. In this embodiment, the
power supply comprises a second microcontroller to receive the RF
commands and act on them.
[0351] In another embodiment, the lighting controller comprises two
microcontrollers, where a first microcontroller is located in the
power supply chassis and a second microcontroller is located in the
operator panel. The two microcontrollers communicate via a wired
link while the operator panel is installed in the power supply.
When the operator panel is removed from the power supply chassis,
the two microcontrollers communicate via a wireless link. In one
embodiment, the operator panel is battery powered and portable. In
another embodiment, a small plug-in power supply powers the
operator panel. In this case, the panel could be mounted in a
location that is more convenient for the user to access, such as a
house's interior wall, for example, rather than the typical and
less convenient exterior wall.
[0352] For years, landscape lighting systems have consisted of
large, bulky and heavy transformers wired to 12 VAC incandescent
bulbs. Typically, the transformer also has a timer either built
into its enclosure, or next to it. The timer is used to switch
power to the transformer ON and OFF to control all of the lights
simultaneously. Recently, LEDs have begun to be used in landscape
lights, but simply as long-life replacements for the incandescent
bulbs that have historically been used.
[0353] In contrast, in an embodiment of the present disclosure, a
lighting fixture receives the polarity controlled, sinusoidal power
signal from the lighting controller 202, 300, 4002, 4702, 4902,
4952, decodes and performs the encoded commands, and uses the
signal for power. In another embodiment, historical landscape
lights could be fitted with special circuitry to receive this
communications signal and use the information to control some
aspect of the light.
LED Lighting
[0354] In a further embodiment, the light fixture comprises and
controls LEDs of white, red, green, and blue color, or any subset.
To control individual LED brightness levels, the controller
receives a target brightness level. The brightness level is applied
to the particular LED after several correction factors. First, the
lighting controller applies the temperature correction factor. As
the temperature of the printed wiring board of the lighting module
increases, the light output of the LED changes. The relative color
change depends on the color of the LED. If color mixing is done, an
individual temperature correction factor is applied to each color
LED or the overall hue will change as temperature changes. Second,
the lighting controller applies an aging correction factor. The
lighting module determines how many total hours of use of each LED
and under the type of driving conditions. As LEDs age, their light
output decreases. If color mixing is done, an individual age
correction factor is applied to each LED or the overall hue will
change as the LEDs age. The third correction factor is a
temperature throttling factor that cuts back power to all LEDs when
the printed circuit board temperature exceeds a predetermined
threshold.
[0355] In yet a further embodiment, the lighting fixture uses a
pulse width modulation (PWM) signal to dim the LEDs, where the PWM
signal is synchronized to the incoming AC power signal. The
synchronization is important to prevent the detrimental effect high
PWM frequencies have on dimming linearity while maintaining a
frequency high enough to avoid the visible flickering of the LEDs
due to the PWM.
[0356] In addition to color correction for temperature and aging,
other embodiments of the lighting module provide color correction
based at least in part on input voltage. Different color LEDs have
different forward voltage drops, and when driven with buck
converters whose input is a full wave rectified waveform, the
conduction angle is based at least in part on the forward drop of
the LED and the input voltage. Therefore, a given ratio of
intensities as determined by the PWM driver among red, green, and
blue LEDs is only valid for a specific input voltage. As the input
voltage changes, the conduction angle of all the colors change, but
in varying amounts, thereby distorting the color ratio and changing
the hue. This may occur in lighting module embodiments that drive
the buck converter with a full wave rectified waveform, thereby
allowing the LEDs to turn on and off at twice the line frequency.
Advantageously, this approach does not use filter capacitors to
maintain the voltage in between peaks of the incoming rectified
signal. Filter capacitors are typically electrolytic capacitors due
to high value required, and can exhibit life expectancies shorter
than the other components in the system. Some are rated as low as
approximately 1000 hours at elevated temperatures, which is usually
the case for an LED fixture. At typical LED fixture can function
approximately 50,000 hours or more. As a result, lighting fixtures
without filter capacitors may be preferable in certain embodiments,
which then may subject to distorted color ratios and changing hues
based at least in part on the input voltage.
[0357] The following example discusses a red, green, blue (RGB) LED
fixture comprising three LEDs for each color, red, green, and blue.
Other embodiments may comprise different numbers and colors of
LEDs. Typical forward voltage drops for a red LED are approximately
2.2 V, for a green LED are approximately 3.5 V, and for a blue LED
are approximately 3.2 V. Therefore, the string of three red LEDS
will turn on at an input voltage of approximately 6.6 V, the string
of three green LEDs will turn on at an input voltage of
approximately 10.5 V, and the string of three blue LEDs will turn
on at an input voltage of at approximately 9.6 V.
[0358] FIG. 59 depicts a first exemplary power waveform 5900
illustrating ON/OFF voltages for these colored LEDs receiving
approximately a rectified 14 VAC, 60 Hz waveform. FIG. 60 depicts a
second exemplary power waveform 6000 illustrating ON/OFF voltages
for these colored LEDs receiving approximately a rectified 11 VAC,
60 Hz waveform. Table 1 shows the relative ratios of red, green,
and blue ON time, normalized for the red LED for the waveforms 5900
(14 VAC), 6000 (11 VAC).
TABLE-US-00001 TABLE 1 RED Vin (normalized) GREEN BLUE 11 VAC 1
0.73 0.80 14 VAC 1 0.83 0.88
[0359] As indicated in TABLE 1, the ratio of the colors has changed
due to the change in the input voltage. In some embodiments, the
result of uncorrected color based on input voltage could be one
color for lights close to the transformer where the voltage is
still relatively high, and a different color further done the run
of wire where the voltage has dropped slightly due to the load
along the line.
[0360] A first embodiment to correct color based at least in part
on the input voltage prevents the LEDs from turning on until the
instantaneous input voltage of the sine wave input exceeds the
largest forward voltage drop of all the LED colors in the lighting
fixture. In the above example, that would be the approximately 10.5
V drop of the three green LEDs. Most likely, in this embodiment,
there is not a point on the input sine wave where one of the colors
is on, but the others are not.
[0361] A second embodiment uses an ND channel of the lighting
fixture microcontroller to measure the input voltage, and then
adjust the color ratio of all the LEDs to compensate for the color
distortion that occurs as the input voltage varies. Input voltage
could be scale factor, along with temperature and aging described
herein.
[0362] FIG. 61 is a block diagram of an exemplary single channel
lighting module 6100 that can be used with the lighting controller
202, 300, 4002, 4702, 4902, 4952 capable of encoding data on the
low voltage power line. The lighting module 6100 comprises a bridge
rectifier 6102, a conditioning circuit 6104, a voltage regulator
6106, a microcontroller 6108, a temperature sensor 6110, an LED
driver 6112, and one or more lamps 6120. In the illustrated
embodiment, the lamps 6120 comprise LEDs 6120. In other
embodiments, the lamps 6120 can be other light emitting devices,
such as, for example, incandescent bulbs, florescent bulbs, or the
like.
[0363] The bridge rectifier 6102 receives the encoded power wave
forms, LIGHTING CONTROL1 and LIGHTING CONTROL2 from the bridge 900
or the bridge/rectifier 1400. The bridge rectifier 6102 comprises a
plurality of diodes, such as, for example, Schottky Rectifiers,
part number SBR2A40P1 available from Diodes Inc., or the like. The
bridge rectifier 6102 converts an input signal of any polarity into
a DC signal to power the other circuits on the lighting board. This
DC signal is fed into the LED Driver 6112, which can be a driver
integrated circuit, part number AL8805 available from Diodes Inc.,
or an equivalent. The driver integrated circuit uses an efficient
Buck Switching topology to generate a regulated output current,
which is used to power the LED(s) 6120. In an embodiment, the LED
6120 can be a high-power LED, such as, for example, a CREE XP-E or
an equivalent.
[0364] The DC voltage output from the bridge rectifier 6102 is also
used to create a regulated logic supply voltage from the voltage
regulator 6106. In an embodiment, the voltage regulator 6106 can be
a 3-Volt regulator, such as, for example, part number TPS71530
available from Texas Instruments, or the like. The voltage
regulator 6106 supplies power to the microcontroller 6108, such as,
for example, part number PIC16F1824 available from Microchip
Technology, or the like. The microcontroller 6108, and firmware
that resides inside it, comprise a receiver for the data being sent
from the lighting controller 202, 300, 4002, 4702, 4902, 4952. A
conditioning network comprising a plurality of resistor and
capacitors couples data from the power supply 302 to the
microcontroller's comparator input while simultaneously limiting
current into the microcontroller 6108. The output of the comparator
(within the microcontroller 6108) is used to determine the nature
of the data. The microcontroller 6108 then generates a signal 6130,
which is coupled to the LED Driver 6112. This signal 6130 is used
to vary the intensity of the light 6120 based on data received from
the power supply 302.
[0365] In an embodiment, part of the data received is an address
that is used to determine if the information being sent is intended
for this light 6120, as each light will have a unique address. In
other embodiments, it is also possible for certain commands to be
intended for lighting "groups". A group may be defined as a certain
type of light, for instance, a path light, or a group may be all
lights in a certain location. In yet other embodiments, commands
may be intended for all lights 6120. Therefore, using this
addressing technique, commands may affect an individual light, a
group of lights, or all lights. In another embodiment, the power
supply 302 communicates an intensity pattern to the light 6120.
This could be a pre-orchestrated pattern of varying intensities,
for example. In an embodiment, the pattern may be "canned" or
preset inside the lighting fixture, or for the details of it to be
communicated from the lighting controller 202, 300, 4002, 4702,
4902, 4952. This feature may be useful, for example, for lighting
"effects" which may be synchronized to music.
[0366] The output of the comparator (within the microcontroller
6108) also contains the phase information for the incoming power
signal, LIGHTING CONTROL1, LIGHTING CONTROL2. In an embodiment,
this is important because the brightness of the LED 6120 is
determined by a pulse width modulation (PWM) waveform from the
microcontroller 6108. Unless this PWM waveform is synchronized with
the incoming power, visible "flickering" may be seen as these two
signals (power and PWM) are "mixed". Therefore, it is important for
the microcontroller 6108 to know the phase of the incoming power,
and periodically reset a PWM counter in order to synchronize the
PWM signal to the power signal.
[0367] In another embodiment, the microcontroller 6108 protects the
light 6100 from overheating. In general, high-power LEDs 6120
generate heat. In an embodiment, the lighting fixture 6100
comprises the temperature sensor 6110 on the printed circuit board
of the lighting fixture 6100. The temperature sensor 6110 can be,
for example, part number MCP9700 available from Microchip
Technology, or the like. The temperature sensor's output is an
analog voltage, which is read by an ND converter in the
microcontroller 6108. The microcontroller 6108 uses this
information to "throttle back" the power to the LED 6120 when the
temperature rises above threshold temperature. In an embodiment,
the threshold temperature is chosen to keep the internal junction
temperature of the LED 6120 within its rated specification. The
throttling is achieved the same way the intensity variation is
achieved, as described above.
[0368] Although this embodiment illustrates a single LED, other
embodiments of the lighting fixture 6100 drive a plurality of LEDs
6120.
[0369] FIG. 62 is an exemplary schematic diagram of a single
channel lighting module 6200, according to one embodiment.
[0370] Other embodiments of lighting devices, such as lighting
device 1804, can be used with the lighting controller 1800 which
encodes data on the primary AC power line. The architecture of the
lighting module 1804 can be similar to the low voltage version
6100, 6200 disclosed above but using components that are rated at a
voltage sufficiently higher than the line voltage. For example,
diodes D1, D2, D3, D4 with sufficient ratings are 1N4007 silicon
rectifier diodes from Diodes Inc., and the like. In another
example, the zener diode clamping circuit (shown in FIG. 62)
preceding the linear regulator U2 should be appropriately sized to
handle the larger input voltage. In other embodiments, other
methods to step down the rectified line voltage to a voltage usable
by the microcontroller U3, such as switching converters and the
like, can be used. Further, the conditioning circuit R3, R4, R5,
R9, C5 should be modified to scale the input voltage for use by the
microcontroller U3. An example of the LED Driver U1 that can accept
a high input voltage is the AL9910 from Diodes Inc. Because of the
high input voltage, this device uses an external MOSFET rather than
an integral MOSFET as described in the AL8805 for the low voltage
case.
[0371] In other embodiments of the line voltage LED fixture, an
optional power factor correction IC can be placed between the full
wave bridge D1, D2, D3, D4 and the rest of the circuit. A suitable
device, for example, is an UCC28810 IC available from Texas
Instruments, or the like. Advantageously, these devices drive the
power factor of nonlinear loads, such as LED drivers, closer to
unity.
[0372] In a further embodiment, the line voltage LED fixture 6100,
6200 comprises an LED driver U1 that could be controlled from a
microcontroller U3 having an input comprising a scaled and
conditioned version of the input voltage. The microcontroller U3
deciphers the encoded data, and affects the LED driver U1
accordingly.
[0373] FIG. 63 is a block diagram of an exemplary multichannel
lighting module 6300, which receives the polarity controlled,
sinusoidal power signal from the lighting controller 202, 300,
4002, 4702, 4902, 4952, decodes and performs the encoded commands,
and uses the signal for power. The lighting module 6300 comprises a
bridge rectifier 6302, a conditioning circuit 6304, a voltage
regulator 6306, a microcontroller 6308, a temperature sensor 6310,
a plurality of LED drivers 6312, 6314, 6316, 6318, and one or more
LEDs 6320, 6322, 6324, 6326. Each LED 6320, 6322, 6324, 6326 may
comprise one or more LEDs. The illustrated embodiment is a four
channel lighting module 6300, although other embodiments may have
more or less than four channels.
[0374] The bridge rectifier 6302, the conditioning circuit 6304,
and the voltage regulator 6306 are similar in construction and
operation to the bridge rectifier 6102, the conditioning circuit
6104, and the voltage regulator 6106 of the single channel lighting
fixture 6100, respectively, as described above.
[0375] The four channel embodiment 6300 approximately quadruples
the LEDs 6120 and LED driver 6112 on the single-channel embodiment
6100 with respect to the LEDs 6320, 6322, 6324, 6326 and the LED
drivers 6312, 6314, 6316, 6318 for the four channel lighting
fixture 6300. Thus each LED 6320, 6322, 6324, 6326 and each LED
driver 6312, 6314, 6316, 6318 is similar in construction and
operation to the LED 6120 and LED driver 6112 of the single channel
lighting fixture 6100, respectively, as described above. Similarly,
the microcontroller 6308 is similar in construction and operation
to the microcontroller 6108 of the single channel lighting fixture
6100, as described above, except the microcontroller 6308 controls
multiple channels instead of a single channel. In conjunction with
the microcontroller 6308, the LED drivers 6312, 6314, 6316, 6318
allow independent brightness control to four separate channels of
LEDs. In a similar manner to microcontroller 6108, which generates
the signal 6130 to control the intensity of LED 6120,
microcontroller 6306 generates signals 6330, 6332, 6334, and 6336
to control the intensities of LEDs 6320, 6322, 6324, and 6326,
respectively. Each string of LEDs 6320, 6322, 6324, 6326 may
comprise one or more LEDs. In other embodiments, this approach
could be used to add more channels, or to change the number of LEDs
in each string. In yet other embodiments, each LED 6320, 6322,
6324, 6326 may comprise several LED dies in a single package with a
single lens, such as, for example, the CREE MC series of LEDs or
the like.
[0376] Like the single-channel embodiment 6100, the lighting
fixture 6300 uses the microcontroller 6308 to receive information
from the lighting controller 202, 300, 4002, 4702, 4902, 4952 and
vary the LED intensity based on this information. Since each of the
four channels can be independently controlled, the commands to a
four-channel lighting fixture 6300 contain intensity level
information for each of the four channels.
[0377] Advantageously, in the multi-channel embodiment 6300, each
channel may comprise a different color LED 6320, 6322, 6324, 6326.
For instance, if the first channel comprises one or more white
LEDs, the second comprises one or more red LEDs, the third
comprises green LEDs and the fourth comprises blue LEDs, then a
plurality of lighting colors could be generated by mixing the
intensities in the correct ratios. For example, the white channel
could create a brighter white light for general lighting needs, or
slightly "wash out" the color created by the red, blue, and green
LEDs. This allows the user to formulate any color of light desired,
and to vary that color, either abruptly, or by a gradual blending
technique. Outdoor lights could also be modified to match a
particular season or holiday. For instance, red, white, and blue
colored lights could be use on the 4th of July; red and green
lights could be used around Christmas; and orange lights could be
used for Halloween and Thanksgiving.
[0378] In another embodiment, the multi-channel lighting fixture
6300 allows the user to adjust the shade of a white light. Perhaps,
for example, the user is more of a "purest" and simply prefers
white lights. The term "white" encompasses a wide range of shades
from the more "blue" cool whites, to the more "yellow" warm whites.
White LEDs by their nature are cool white. This is because a white
LED is actually a blue LED with phosphor coating that glows white.
For most people this is acceptable, but for some, a warmer white
may be desired. If one of the three channels were populated with a
red or yellow LED, then by varying the intensity of that channel,
the user could vary the warmth, or color temperature as it is
technically called, of the light. This is also important because
different color temperatures are better at illuminating certain
subject hues than others.
[0379] Control of individual lights or individual channels of LEDs
within a single light is advantageous. Even more advantageous is to
be able to achieve this control using the same set of wires that
deliver power to the light. Lastly, integrating all of the decoder
circuitry 6302, 6304, 6306, 6308, the driver circuitry 6312, 6314,
6316, 6318, and the temperature throttling 6310 on a single printed
circuit board within the lighting fixture 6300, results in a highly
integrated, self-contained intelligent light fixture 6300, which is
no harder to install than a tradition landscape light.
[0380] FIG. 64 is an exemplary schematic diagram of a multichannel
lighting module 6400, according to one embodiment.
Color and Brightness Control of LED Lighting
[0381] LED-based lighting may comprise any of red, green, blue
(RGB), red, green blue, white (RGBW), white, amber, cyan,
red-orange, and the like, LEDs. A problem in the design of
LED-based lighting is the resolution to maintain a specific or
selected color while simultaneously dimming the light.
[0382] While the LEDs are ON, they produce light that acts as a
continuous analog signal. The lighting modules provide the LED
drivers with a signal, which is used by the LED drivers to create
an LED drive signal to cause the LEDs, when optically mixed, to
produce the specific or selected color of light at a specific or
selected intensity. In an embodiment, the resolution of the control
over the color and brightness of the LED is the smallest amount of
change or discrete step in the signal provided to the LED driver
that affects a change in the output of the LED. For example, if the
intensity can be changed from 50% to 51%, then the resolution or
resolution of intensity control is 1%. If the intensity can be
changed from 50% to 50.1%, then the resolution or resolution of
intensity control is 0.1%. A signal with 0.1% resolution has
greater resolution than a signal with 1% resolution. The signal
with 0.1% resolution can control the color and intensity of the LED
with greater precision than the signal with 1% resolution. In an
embodiment, the resolution is the number of output levels a signal
can be quantized to. In another embodiment, a signal with greater
resolution has greater granularity than a signal with less
resolution, where granularity is the relative size, scale, level of
detail, or depth of penetration that characterizes an object or
activity.
[0383] The following example uses RED, GREEN, and BLUE LEDs to
illustrate the resolution issue of maintaining a lighting color and
dimming the intensity of LED-based lighting. It is well understood
that LED-based lighting may also comprise different combinations of
colored LEDs.
[0384] In an embodiment, a lighting system controls the brightness
of individual RED, GREEN, and BLUE LEDs with approximately 1%
accuracy in order to mix the LED colors and create various hues.
While accuracy of approximately 1% may provide a precise level of
control to create specific hues, it is insufficient when both color
mixing and overall dimming are simultaneously provided.
[0385] For example, color X is defined as RED LED driven at 84%
brightness, GREEN LED driven at 27% brightness and BLUE LED driven
at 3% brightness, which results in an RGB ratio of 28:9:1. The user
is pleased with the hue of color X, but would like to dim the light
to, for example, 10% of the overall brightness. Mathematically, to
achieve this, the lighting controller would drive the RED LED at
8.4% brightness, drive the GREEN LED at 2.7% brightness, and drive
the BLUE LED at 0.3% brightness. However, because the resolution is
approximately 1%, rounding occurs. The lighting controller would
drive the RED LED at 8% brightness, drive the GREEN LED at 3%
brightness, and drive the BLUE LED at 0% brightness.
[0386] The desired RGB ratio of 28:9:1 for color X has changed to
8:3:0 due to dimming. The new RGB ratio creates an approximately
10% error in the balance of the RED and GREEN LEDs and eliminates
the BLUE LED from the color mix. This example illustrates that the
lighting system changes the hue of the LED-based lighting as the
user dims the lighting because the RGB ratio changes due to the
limited resolution of control.
[0387] Color mixing systems, in certain embodiments, use pulse
width modulation (PWM) to control the brightness of the individual
colors. While many microcontrollers can generate PWM waveforms with
resolutions of approximately 0.1% or better, there may be other
factors that prevent or inhibit this same level of control at the
LED-based lighting output. Drivers or driver circuits that are used
to drive the LEDs can prevent or inhibit driving the LEDs with
greater resolution.
[0388] Linear regulators are a simple way to reduce the voltage of
a DC supply but linear regulators waste energy as they operate by
dissipating energy as heat. For efficiency reasons, high power
LEDs, such as those used for lighting, are driven using switching
regulators in certain embodiments.
[0389] A buck converter is a voltage step down and current step up
switching regulator. When the input voltage is higher than the
forward voltage of the string of LEDs, a switching regulator having
a buck topology is often used to drive the LEDs. Furthermore,
because of their simplicity, hysteretic buck regulators or
converters, such as, for example, an AL8807 from Diodes
Incorporated, or the like, are commonly used to drive LEDs with a
relatively constant current.
[0390] These LED drivers comprising hysteretic buck regulators or
converters use a high-frequency switched signal to drive a
relatively constant current through the LED at frequencies from
approximately a few tens of kilohertz up to approximately a
megahertz. In a hysteretic converter, the exact frequency of this
high frequency signal depends on several factors, such as component
values, input and output voltages, and output current, for example.
Further, it takes a few cycles of this high-frequency signal to
"ramp-up" and for the LED to turn ON. Again, the exact number of
cycles to ramp-up and turn ON the LED depends on several factors,
such as the component values, the input and output voltages, and
the output current, for example.
[0391] This high frequency signal which drives the relatively
constant current through the LEDs is switched ON and OFF based at
least in part on the PWM signal that is input to the LED driver.
The PWM signal that is input to the driver is generated by a
microcontroller or microprocessor and is used to control the RGB
ratios in color mixing for LED-based lighting, as described
above.
[0392] Because the PWM input signal to the LED driver cannot be
narrower than a few cycles of the high frequency signal used to
drive the LED (due to the ramp-up and turn ON), the PWM input
signal loses resolution through the LED driver.
[0393] In other words, the period of the high-frequency waveform
that the LED driver is using to drive the LED is the "building
block". If 50% brightness is desired, the lighting system may drive
the LED with 10 of these periods, then stop driving the LED for the
next 10 periods, and so on until the desired brightness
changes.
[0394] For example, consider a PWM signal with 0.1% resolution
controlling a hysteric LED driver operating at approximately 250
kHz so that the waveform the LED driver uses to drive the LED has a
period of approximately 4 microseconds. The narrowest pulse that
could be sent into the PWM input of the LED driver to achieve
accurate control would be about 20 microseconds. This approximately
20 microsecond pulse would correspond to approximately 0.1% of full
brightness of the lighting system. A pulse width 1000 times greater
(1/0.1%) would correspond to 100% brightness, or 20
milliseconds.
[0395] Unfortunately, a signal with an approximately 20 millisecond
period corresponds to a 50 Hz signal, which when input into the LED
driver may result in visual flicker.
[0396] Further, it is common for the hysteretic buck converter to
be supplied power directly from a full wave bridge without the use
of bulky, unreliable storage capacitors. For instance, in the
example of a 12 VAC input power signal and the AL8807 LED driver,
the LED driver is turning ON for approximately 4-5 milliseconds
then OFF for approximately 3-4 milliseconds for each half-wave of
the input power. The LED driver turns ON when the full wave
rectified signal goes above approximately 7V, which is the minimum
operating voltage of the part. This corresponds to a frequency of
approximately 120 Hz for a 60 Hz input signal.
[0397] The combination of the 120 Hz incoming power modulation and
the 50 Hz PWM control signal modulation would result in
cross-modulation components which may cause even more visual
flicker.
[0398] In summary, the operating frequency of the LED driver limits
how narrow the pulses of the PWM signal used at the PWM input of
the LED driver can be. Stated another way, the operating frequency
of the LED driver places a practical upper limit on the frequency
of the PWM signal used at the PWM input of the LED driver.
[0399] Additionally, the human eye's ability to perceive flicker
along with the incoming power frequency places a practical lower
limit on the PWM frequency that can be used. When taken together,
these two limits usually result in a resolution much worse than
0.1%. Thus, the full accuracy of the PWM input signal to the LED
driver is difficult to realize.
[0400] In some instances, increasing the operating frequency of the
LED driver permits the upper limit of the frequency of the PWM
input signal to be increased. However, this can create additional
problems. Electromagnetic emissions are much more of a concern at
these higher switching frequencies. Additionally, efficiency
usually suffers since the MOSFETs that do the switching spend a
greater percentage of time in their linear region.
[0401] A control method that increases resolution and operates with
LED drivers operating in the hundreds of kilohertz range, such as
100 kHz or 250 kHz, and the like, would be advantageous.
[0402] FIG. 67 is a block diagram of an exemplary hysteretic LED
driver 6700 that can be used to drive one or more LEDs electrically
coupled between SET and SW. A low value resistor, for instance 0.1
ohms, would typically be connected between the SET pin and the
positive power supply voltage. This allows the SET pin to monitor
the current through the LED when the FET turns on. SET is therefore
used to monitor the LED current and SW provides the high-frequency
signal to drive the LEDs. UVLO 6708 controls the minimum operating
voltage of the part.
[0403] A CTRL input comprises a dimming and ON/OFF control input
for the LED driver 6700, and in an embodiment, receives the PWM
input signal that operates the LED driver with increased
resolution. In an embodiment, PWM control and analog control are
used to create the PWM input signal.
[0404] In an embodiment, the LED driver 6112 associated with the
lighting module 6100, described above with respect to FIG. 61,
comprises the hysteretic LED driver 6700, and the signal 6130 from
the microcontroller 6108 comprises the PWM input signal. In another
embodiment, each of the LED drivers 6312, 6314, 6316, 6318
associated with the lighting module 6300, described above with
respect to FIG. 63, comprise the hysteretic LED driver 6700, and
the signals 6330, 6332, 6334, 6436 from the microcontroller U3 6308
comprises the PWM input signal.
PWM Control
[0405] Referring to FIG. 67, in an embodiment, the PWM input signal
electrically couples to the CTRL input where it is fed through a
PWM Dimming Control block 6702 into comparator 6704 which controls
a MOSFET switch 6706. The duty cycle of the PWM input signal
controls the ON/OFF states of the MOSFET switch and thereby the
current that the LED is driven with. Moreover, controlling the LED
drive current controls the brightness of the LED.
Analog Control
[0406] In an embodiment, the PWM Dimming Control block 6702 also
receives a control voltage VCTRLL and a reference voltage VREF. In
an embodiment where the LED driver comprises an AL8807 from Diodes
Incorporated, for example, the control voltage VCTRLL is an
approximately 0.45V signal, and the reference voltage VREF is an
approximately 2.5V signal. In other embodiments of LED drivers,
VREF may be more or less than 2.5V and VCTRLL may be more or less
than 0.45V.
[0407] For illustration purposes, in the embodiment of FIG. 67,
when the CTRL input drops below approximately 0.45V, the comparator
6704 receives approximately 0V, such that the MOSFET switch 6706
does not turn ON, thereby disabling the driver 6700. Voltages on
the CTRL input that are between approximately 0.45V and
approximately 2.5V are passed through to the comparator 6704.
Therefore, by driving a DC voltage into the CTRL input, the
brightness of the LED can be controlled because the switching point
(hysteresis) of the comparator 6704 can be controlled.
[0408] By controlling the voltage level of the PWM input signal,
the reference voltage at the output of the PWM DIMMING CONTROL 6702
supplied to the comparator 6704 can be controlled, and in turn, the
current supplied by the LED driver 6700 can be controlled, which
controls the brightness of the LEDs.
[0409] While the topology of FIG. 67 is just one example of a
hysteretic driver 6700, hysteretic drivers 6700 typically comprise
the comparator 6704 (often called the hysteresis comparator) which
controls the MOSFET switch 6706.
[0410] In summary, in an embodiment, hysteretic drivers 6700 can be
controlled with either an analog signal or a digital (PWM) signal.
In the analog approach, the current supplied by the driver 6700 is
regulated to less than 100% by applying a lower voltage than the
voltage that corresponds to 100% of the comparator reference. In
the PWM or digital approach, the comparator reference switches
between 2 states: 100% and 0%. The ratio of the time spent in these
states determines the average current through the LED. As long as
the frequency of the PWM signal is faster than the response of the
human eye, the brightness is perceived as the average
brightness.
Analog and PWM Control Signals
[0411] Embodiments of control signal generators generate a control
signal that allows a hysteretic driver to simultaneously operate in
both digital (PWM) and analog modes. Advantageously, when each mode
alone allows a resolution of approximately 1%, then these two
resolutions will compound resulting in a resolution approximately
0.01% (1% x 1%). Furthermore, approximately 1% control is
achievable using PWM control at driver frequencies as low as 50
kHz, while still avoiding the flicker described above.
[0412] FIGS. 68-72 comprise exemplary control waveforms to
illustrate how analog and digital control methods can be used
independently and then simultaneously in embodiments of the
hysteretic LED driver 6700.
[0413] Consider an analog controlled system. FIG. 68 is an
exemplary analog input waveform 6800 comprising an approximately
2.5V signal that when applied to the CTRL input results in
approximately full (100%) brightness of the LED for the analog
controlled system. FIG. 69 illustrates an exemplary analog input
waveform 6900 that when applied to the CTRL input results in
approximately half (50%) brightness of the LED for the analog
controlled system. The waveform 6900 has an approximately constant
level of approximately 1.25V, which is half of the 100% level of
approximately 2.5V of the waveform 6800.
[0414] Consider a PWM controlled system. FIG. 70 illustrates an
exemplary PWM input waveform 7000 that results in approximately
full (100%) brightness of the LED for the PMW controlled system.
The waveform 7000 comprises an approximately 2.5V signal having a
duty cycle of 100%. FIG. 71 illustrates an exemplary PWM input
waveform 7100 that results in approximately half (50%) brightness
for the PWM controlled system. The waveform 7100 comprises an
approximately 2.5V periodic signal having a period of approximately
2T, where the amplitude of the waveform 7100 is approximately 2.5V
for the first half of the period and approximately 0V for the
second half of the period, or in other words, has a 50% duty cycle.
The approximately half (50%) brightness can be achieved since half
of the time the driver 6700 is working at approximately 100%
brightness, and the other half of the time it is at approximately
0% brightness, which averages out to approximately 50%
brightness.
[0415] Consider an analog controlled and a PWM controlled or hybrid
controlled system. FIG. 72 illustrates a hybrid controlled lighting
module 7200 comprising a hybrid signal generator 7202, the
hysteretic LED driver 6700, and a string of one or more LEDs 7204.
In an embodiment, the LEDs 7204 comprise the LEDs 6120, 6320, 6322,
6324, 6326. The hybrid signal generator 7202 generates a hybrid
(analog and PWM) control waveform or signal which is received by
the LED driver 6700 and used to control the brightness and color
mixing of the LEDs 7204 with resolution provided by both analog and
PWM control.
[0416] FIG. 73 illustrates an exemplary hybrid control waveform
7300 for the hysteretic LED driver 6700 that results in
approximately quarter (25%) brightness. The waveform 7300 comprises
an approximately 1.25V periodic signal having a period of 2T, where
the amplitude of the waveform 7300 is approximately 1.25V for the
first half of the period and approximately 0V for the second half
of the period (50% duty cycle). The PWM aspect of the waveform 7300
enables the LED driver 6700 for approximately 50% of the time.
However, while the LED driver 6700 is ON, analog dimming is
employed, as evident from the voltage of the waveform 7300.
[0417] In an embodiment where the voltage to drive the LEDs 7204 to
100% brightness is approximately 2.5V, a voltage of approximately
1.25V drives the LEDs 7204 to approximately 50% brightness. When
the hybrid signal generator 7202 generates the waveform 7300, the
LED driver 6700 drives the LEDs 7204 at approximately 50% of
maximum while the LED driver 6700 is ON. The effective brightness
is therefore approximately 25% since the LEDs 7204 are being driven
at approximately 50% brightness for approximately 50% of the time
(0.50.times.0.50=0.25). This illustrates the compounding effect of
approximately simultaneous analog and PWM control of the LED driver
6700.
[0418] FIG. 73 illustrates just one example of a hybrid control
waveform having simultaneous or approximately simultaneous analog
and digital dimming with increased resolution. In other
embodiments, the lighting module 7200 can achieve various dimming
scenarios that do not alter or substantially alter the RGB ratio of
the desired hue by supplying a PWM waveform of varying duty cycle
and with varying amplitude.
Novel Control Signal Generators
Digital to Analog Converter Output Modulated by PWM Wave Form
[0419] FIGS. 74-76 illustrate embodiments of the hybrid signal
generator 7202 to generate hybrid control waveforms comprising one
or more of varying duty cycles and varying amplitudes.
[0420] FIG. 74 is a block diagram of an embodiment of a hybrid
control signal generator 7400 comprising a microcontroller 7402 and
a digital to analog converter (DAC) 7404. The DAC 7404 receives
digital data at a digital input and converts the digital data to an
analog signal, which is output at an analog output. The DAC 7404
includes an enable input that enables or disables the analog
output. The microcontroller 7402 is configured to output digital
data at a digital output and a PWM waveform at a PWM output. The
digital output of the microcontroller 7402 electrically couples to
the digital input of the DAC 7404 and the PWM output of the
microcontroller 7402 electrically couples to the enable input of
the DAC 7404.
[0421] The microcontroller 7402 outputs a digital value which is
converted to an analog signal and output by the DAC 7404. The
microcontroller 7402 further generates the PWM signal, which, as
the enable input to the DAC 7404, controls the analog output of the
DAC 7404. When the enable signal is active, the output of the DAC
7404 is approximately the analog signal as set by the
microcontroller 7402. When the enable signal is inactive, the
output of the DAC 7404 is approximately 0V. The output of the DAC
7404 is modulated by the PWM waveform supplied by the
microcontroller 7402. The output of the DAC 7404 is presented to
the LED driver 6700.
[0422] Thus, the hybrid control signal generator 7400 generates a
control waveform comprising a varying duty cycle and varying
amplitude where the duty cycle is based at least in part on the PWM
waveform from the microcontroller 7402 and the amplitude is based
at least in part on the digital data from the microcontroller
7402.
[0423] FIG. 75 is a block diagram of an embodiment of a hybrid
control signal generator 7500 comprising a microcontroller 7502, a
digital to analog converter (DAC) 7504, and a switch 7506. In an
embodiment, the switch 7506 comprises a transistor, such as a BJT
or a FET. The microcontroller 7502 comprises a digital output and a
PWM output and operates similar to the microcontroller 7402 as
described above with respect to FIG. 74. DAC 7504 comprises a
digital input, an enable input, and an analog output and operates
similar to the DAC 7404 as described above with respect to FIG.
74.
[0424] The digital output of the microcontroller 7502 electrically
couples to the digital input of the DAC 7504. The PWM output of the
microcontroller 7502 electrically couples to a gate or a base of
the switch 7506 and the analog output of the DAC 7504 electrically
couples to a collector or a source of the switch 7506. The enable
input is configured such that the DAC 7504 is always enabled, in an
embodiment.
[0425] The microcontroller 7502 outputs digital data to the digital
input of the DAC 7504. The DAC 7504 converts the digital data to an
analog signal and outputs the analog signal. The microcontroller
7502 further generates a PWM waveform, which is received at the
base or gate of the switch 7506. The analog output of the DAC 7504
is enabled through the enable input, but the analog output of the
DAC 7504 is pulled to ground via the collector or source of the
switch 7506 when the PWM waveform becomes active.
[0426] When the PWM waveform is inactive, the switch 7506 is open,
such that the transistor is OFF, and the DAC analog output signal
is presented to the LED driver 6700. In an embodiment, the PMW
waveform is active when it is a logic high and inactive when it is
a logic low. In another embodiment the PMW waveform is active when
it is a logic low and inactive when it is a logic high. The output
of the DAC 7504 is modulated by the PWM waveform generated by the
microcontroller 7502 and the amplitude of the output of the DAC
7504 is controlled by the digital data provided by the
microcontroller 7502.
[0427] Thus, the hybrid control signal generator 7500 generates a
control waveform comprising a varying duty cycle and varying
amplitude where the duty cycle is based at least in part on the PWM
waveform from the microcontroller 7502 and the amplitude is based
at least in part on the digital data from the microcontroller
7502.
[0428] In the embodiments illustrated in FIGS. 74 and 75, the DAC
7404, 7504 generates the analog waveform and the PWM signal from
the microcontroller 7402, 7502 is used to modulate this analog
waveform. In other embodiments, the microcontroller 7402, 7502
comprises the DAC 7404, 7504, the switch 7506 comprises an analog
switch, and the like. In an embodiment, the DAC 7404, 7504
comprises, for example, an MCP4728 available from Microchip
Technology, or the like. In an embodiment, the microcontroller
7402, 7502 comprises, for example, a PIC16F1847 available from
Microchip Technology, or the like. The switch 7506 comprises, for
example, a transistor, such as a FET 2N7002 available from Diodes
Inc., or the like.
PWM Waveform Modulated by PWM Waveform
[0429] If the microcontroller has multiple PWM channels, a first
PWM waveform may be used to create an analog waveform by low-pass
filtering (averaging) the first PWM waveform. When the cut-off
frequency of the low-pass filter is much less than the PWM
frequency of the first PWM waveform, the resulting signal will
approximate an analog DC signal. The level of this analog DC signal
can be controlled by the duty cycle of the first PWM waveform
generated by the microcontroller. Once this analog DC signal is
generated, it can be modulated by a second PWM waveform generated
by the microcontroller using various methods.
[0430] FIG. 76 is a block diagram of an exemplary hybrid control
signal generator 7600 comprising a microcontroller 7602, a switch
7606, a low-pass filter 7608, and a buffer circuit 7610. The
microcontroller 7602 comprises at least two PMW channels, indicated
by a PWM1 output and a PWM2 output and operates similar to the
microcontroller 7402, 7502 as described above with respect to FIGS.
74 and 75. In an embodiment, the switch 7606 comprises a
transistor, such as a BJT or a FET, an analog switch, and the
like.
[0431] In an embodiment, the low-pass filter 7608 comprises a
2-stage RC network, as illustrated in FIG. 76. In other
embodiments, other low-pass filters can be used, as is known to one
of skill from the disclosure herein. In an embodiment, the buffer
circuit 7610 comprises an operational amplifier, as illustrated in
FIG. 75. In other embodiments, other circuits can be used to buffer
or drive the output of the hybrid control signal generator 7600, as
is known to one of skill from the disclosure herein.
[0432] The PWM1 output of the microcontroller 7602 electrically
couples to an input of the low-pass filter 7608 and an output of
the low-pass filter 7608 electrically couples to an input of the
buffer circuit 7610. An output of the buffer circuit 7610
electrically couples to a source or emitter of the switch 7606 and
the PWM2 output of the microcontroller 7602 electrically couples to
a gate or base of the switch 7610.
[0433] The first PWM waveform from the PWM1 output of the
microcontroller 7602 is filtered by the low-pass filter 7608 to
approximate an analog signal where the amplitude of the analog
signal is responsive to the average of the amplitude of the first
PWM waveform. The buffer circuit 7610 buffers the output of the
low-pass filter 7608. The output of the buffer circuit 7610 is
modulated in response to the second PWM waveform from the PWM2
output of the microcontroller 7602 using the switch 7606. This is
described above with respect to the microcontroller 7502 and the
switch 7506 of FIG. 75. The output of the buffer circuit 7610
drives the LED driver 6700.
[0434] In embodiments where the low-pass filter 7608 comprises a
2-stage RC network, the output of the low-pass filter 7608 is
buffered by the buffer circuit 7610 because the 2-stage RC network
effectively raises the source impedance of the signal, which lowers
its drive capability. In other embodiments, when the input
impedance of the LED driver 6700 is high, the buffer circuit 7610
may be eliminated.
[0435] In an embodiment, the microcontroller 7602 comprises, for
example, a PIC16F1847 available from Microchip Technology, or the
like. The switch 7606 comprises, for example, a transistor, such as
a FET 2N7002 available from Diodes Inc., or the like.
Digital to Analog Converter Output Controlled by Digital Data
[0436] In an embodiment, a digital to analog converter is used to
generate the hybrid control signal using digital data from a
microcontroller. Advantageously, this solution uses fewer
components than the embodiments illustrated in FIGS. 74, 75, and
76.
[0437] FIG. 77 illustrates an exemplary hybrid control waveform
7700 for the hysteretic LED driver 6700 where the analog and PWM
components of the hybrid control waveform change at t=t5. FIG. 78
is a block diagram of an exemplary hybrid control signal generator
7800 comprising a microcontroller 7802 and a digital to analog
converter (DAC) 7804 that can be used to generate the hybrid
control signal 7700.
[0438] A digital output of the microcontroller 7802 electrically
couples to a digital input of the DAC 7804 and the microcontroller
7802 provides digital data to the DAC 7804. The microcontroller
7802 writes or sends new digital values to the DAC 7804 at
determined intervals to generate the hybrid control waveform
7700.
[0439] For example, to generate the hybrid control waveform 7700,
the microcontroller 7802 writes a digital value corresponding to a
DAC output of approximately 1.25V at t=t1, and a digital value
corresponding to a DAC output of approximately 0V at t=t2. At t=t3,
the microcontroller 7802 again writes a digital value corresponding
to the DAC output of approximately 1.25V, and at t=t4 the
microcontroller 7702 again writes a digital value corresponding to
the DAC output of approximately 0V. At this point, the user,
through the lighting controller 202, 300, 4002, 4702, 4902, 4952,
decides to change the intensity of the light. So at t=t5, the
microcontroller 7802 writes a digital value to the DAC 7804 that
causes the DAC 7804 to output a signal with a value of
approximately 0.75V. Then at t=t6, the microcontroller 7802 writes
a digital value corresponding to a DAC output of approximately 0V.
This process continues. The output of the DAC 7804 is presented to
the LED driver 6700.
[0440] The microcontroller 7802 writes the digital data at specific
time intervals in order for the desired outcome to occur. In an
embodiment, the time intervals between "writes" can vary, which
also affects the color and brightness of the LEDs 7204.
[0441] In contrast, the microcontrollers 7402, 7502, write the
digital data to the corresponding DAC 7404, 7504 and to the PWM
controller in the microcontroller 7402, 7502 once. These values do
not need to be re-written unless the user, through the lighting
controller 202, 300, 4002, 4702, 4902, 4952, changes the color
and/or brightness of the LED lighting 7204. And if the color and
the brightness changes, in an embodiment, a single pair of writes
to affect the changes is needed until there is another change.
Filtered PWM Waveform
[0442] In an embodiment, a PWM waveform from a microcontroller is
filtered and buffered to provide the hybrid control waveform. The
microcontroller provides a new PWM waveform with a different duty
cycle to change the hybrid control waveform. Advantageously, this
solution uses fewer components than the embodiments illustrated in
FIGS. 74, 75, and 76.
[0443] FIG. 79 illustrates an exemplary PWM waveform 7902 (Waveform
A) from a microcontroller that is filtered to provide a hybrid
control waveform 7900 (Waveform B). FIG. 80 is a block diagram of
an exemplary hybrid control waveform generator 8000 comprising a
microcontroller 8002, a low-pass filter 8008, and a buffer circuit
8010 that can be used to generate the hybrid control signal
7900.
[0444] A PWM output of the microcontroller 8002 electrically
couples to an input of the low-pass filter 8008 and an output of
the low-pass filter 8008 electrically couples to an input of the
buffer circuit 8010. An output of the buffer circuit 8010 provides
the hybrid control waveform 7900 for the LED driver 6700.
[0445] In an embodiment, the low-pass filter 8008 comprises a
2-stage RC low-pass filter. In other embodiments, other
configuration of low-pass filters 8008 can be used, as is known to
one of skill from the disclosure herein. In an embodiment, the
buffer circuit 8010 comprises an operational amplifier. In other
embodiments, other configurations of buffer circuits 8010 can be
used, as is known to one of skill from the disclosure herein.
[0446] Waveform A 7902 is an example of the PWM waveform generated
by the microcontroller 8002. To generate Waveform A, the
microcontroller 8002 writes digital data corresponding to, for
example, amplitude, period T2, and duty cycle (T1/T2), to the PWM
controller in the microcontroller 8002. Waveform A 7902 is averaged
by the low-pass filter 8008 and buffered by buffer circuit 8010 to
provide a PWM waveform with varying amplitude as the hybrid control
waveform 7900 (Waveform B). During the period in between the
pulses, both waveforms 7900, 7902 are at approximately 0V.
[0447] To generate the hybrid control signal 7900, for example, at
t=t1, the microcontroller 8002 generates the PWM Waveform A 7902
having an amplitude of approximately 2.5V and a duty cycle of
approximately 50% which corresponds to a low-pass filter output of
approximately 1.25V. At t=t2, the microcontroller 8002 writes new
digital data to its PWM peripheral corresponding to a low-pass
filter output of approximately 0V. At t=t3, the microcontroller
8002 again writes digital data to its PWM peripheral that causes
the microprocessor 8002 to generate the PWM Waveform A 7902 having
an amplitude of approximately 2.5V and a duty cycle of
approximately 50% and at t=t4, the microcontroller 8002 writes
digital data corresponding to a low-pass filter output of
approximately 0V.
[0448] This process continues until t=t5, where the user, through
the lighting controller 202, 300, 4002, 4702, 4902, 4952, decides
to change the intensity of the light. At t=t5 the microcontroller
8002 writes digital data with a new duty cycle corresponding to a
low-pass filter output of approximately 0.75V. At t=t6, the
microcontroller 8002 again writes digital data corresponding to a
low-pass filter output of approximately 0V. The times (t=t2, t4,
t6) when the PWM output of the microcontroller 7802 is OFF,
corresponding to a low-pass filter output of approximately 0V, are
chosen to provide the hybrid control signal 7900 with a period of
T4 and a duty cycle of T3/T4. The process continues.
[0449] FIG. 79 illustrates an exemplary hybrid control waveform
7900 with varying amplitude and an approximately constant period.
In other embodiments of the hybrid control signal generator 8000,
the microcontroller 8002 can write digital data at differing times
to generate the PWM waveform 7902 that when filtered, provides the
hybrid control waveform 7900 having varying amplitude and/or
varying modulation periods.
[0450] FIG. 81 illustrates an exemplary filter response 8100 for
the low-pass filter 8008. Referring to FIGS. 79 and 80, the PWM
output (Waveform A) 7902 has a period of T2, which corresponds to a
frequency of f2 and the hybrid control waveform (Waveform B) 7900
has a period of T4 corresponding to a frequency of f4. The values
of the components of the low-pass filter 8010 are chosen such that
the low-pass filter 8010 readily passes waveforms having the
frequency f4, and filters or averages waveforms having the
frequency f2.
[0451] Embodiments of the lighting systems 100, 200, 1800, 4000,
4300, 4700, 4800, 4900, 5000, 5200 further comprise the hybrid
controlled lighting module 7200 to control color and dimming of LED
lighting. Embodiments of the lighting controller 202, 300, 4002,
4702, 4902, 4952 further comprise any of the hybrid control signal
generators 7400, 7500, 7600, 7800, 8000. Embodiments of the
lighting modules 6100, 6200, 6300, 6400 comprise any of the hybrid
control signal generators 7400, 7500, 7600, 7800, 8000. Embodiments
of the microcontroller 6102, 6302 comprise any of the
microcontrollers 7402, 7502, 7602, 7802, 8002.
[0452] The embodiments disclosed herein illustrate non-limiting
examples of the concept of combining two control signals, each with
a limited control resolution, such that the combined control signal
has a resulting resolution with a much finer resolution than either
of the two control signals alone could achieve.
[0453] The examples herein describe the generation and use of a
hybrid control signal having an analog component and a digital
component in conjunction with a hysteretic buck converter. In other
embodiments, the two components of the hybrid control signal could
also both be analog, or both be digital. Furthermore, the driver
need not be a hysteretic buck topology driver, but may also be
buck, boost, buck-boost, single-ended primary-inductor converter
(sepic), linear, or various other driver types. Additionally, the
two control signals need not be combined prior to presenting them
to the converter, but may also be combined by the converter itself.
In such a design, the converter comprises more than one dimming
input.
[0454] Lastly, the concept of dimming a particular hue was used as
an example of one of the benefits associated with increased
resolution of control. However, even if dimming were not a
consideration, the techniques described could be used to give more
resolution for hue control, since the ratios of the colors to be
mixed can be controlled with greater precision.
Color Wheel Feature
[0455] Colored LED-based lighting, such as an RGB lighting fixture,
not only has the ability to render nearly any hue of light and/or
intensity using, for example, one or more of the hybrid control
signals described herein, it also has the ability to change that
hue autonomously if desired. In an embodiment, an intelligent RGB
lighting fixture receives a command, which comprises a starting
hue, an ending hue, and a transition time, where the transition
time is the time it takes the lighting fixture to transition from
the starting hue to the ending hue. When the lighting fixture
receives this command, it outputs the starting hue, and begins
transitioning from the starting hue to the ending hue, at a speed
that is based at least in part on the transition time.
[0456] In another embodiment, the command further comprises cycle
information. The cycle information may comprise additional
information such as whether after the ending hue is reached, the
lighting fixture should transition back to the starting hue, or
remain at the ending hue. The lighting fixture may, in a further
embodiment, be instructed to start at one hue and continually
transition through all possible hues perpetually.
[0457] This feature is useful when lighting fountains or water
features. For example, a user wants to illuminate a 3-tiered
fountain with three separate groups of lights, such that a first
group illuminates the lowest tier, a second group illuminates the
middle tier, and a third group illuminates the highest tier. He
could start each tier at a different hue, and instruct the lighting
fixtures to step or cycle though all hues with approximately the
same speed. This results in a visually appealing display since each
of the three fountain tiers is illuminated with a different color,
which is changing. This example shows the importance of specifying
a starting hue as well as a transition speed.
[0458] In an embodiment, for such a feature to be useful, it is
important for lighting fixtures of different groups, or lighting
fixtures of the same group to use a time base that is synchronous
among the lighting fixtures. When multiple fixtures using the same
or approximately the same time base are placed in this "color
wheel" mode, they would maintain synchrony with each other. In an
embodiment, accurate crystals or oscillators can be used in each
lighting fixture to minimize variations in each lighting fixture's
time base. Unfortunately, accurate crystals or oscillators can be
expensive. In another embodiment, without using expensive highly
accurate crystals in each lighting fixture, the incoming AC power
is used as a time base. Because the lighting fixtures receive power
from a common source of power, using the timing information from
the common power source is a simple, inexpensive method to maintain
the lighting fixtures in sync with one another. In an embodiment,
the timing information of the common power source comprises the
frequency of the power source.
[0459] In an embodiment, the zero-crossing of the incoming power
generates an interrupt to the microcontroller in the lighting
fixture. For example, a zero-crossing detector could be used to
generate the interrupt. Depending at least in part on the
transition speed that of the lighting fixture received in the
command, the microcontroller may take one "step" toward the next
color or hue every interrupt, or every second interrupt, or every
third interrupt, etc. For example, a counter could be used to count
the interrupts generated by the zero-crossing detector. When the
number of received interrupts correlates with to the transition
speed, the microcontroller generates control signals to control the
LEDs in the lighting fixture to produce the next color.
[0460] In an embodiment, a LED-based lighting fixture is configured
to receive a command comprising a starting hue, an optional ending
hue, and a transition speed. In another embodiment, the LED-based
lighting fixture is configured to use timing information from the
power signal as a time base for color transitions defined by the
starting hue, the optional ending hue, and the transition
speed.
Chassis
[0461] Embodiments of the lighting systems 100, 200, 1800, 4000,
4300, 4700, 4800, 4900, 5000, 5200 further comprise a frame that
would mount inside the home or anywhere an aesthetic installation
was desired. In one embodiment, the frame holds the operator
interface panel 308 and could further comprise one or more of the
following: [0462] An extension of the RS485 connection from the
chassis 302 to the frame, where the frame has wiring channels for
the cable, thus providing a very clean installation; [0463] An
integrated "nest" for the WI-FI antenna so that it would not be
seen; [0464] Work with the wireless operator interface panel
extender described herein by invisibly housing the RF transceiver
and providing power to the operator interface panel 308; and [0465]
Power the operator interface panel 308 such that the frame could
also recharge an integrated battery. This would allow users to have
the wall mounted option, be able to remove the operator panel 308,
which is now powered by the battery and in communication with the
chassis via the radio, and walk around to adjust their lighting,
seeing the affects in real time.
[0466] FIG. 65 is a front view of an exemplary lighting controller
comprising a frame 6502 and an operator interface panel 6504 which
comprises a display 6508, fixture programming ports 6510, and user
interface devices 6512, such as button, switch, knobs, and the
like. In the illustrated embodiment, latch 6506 is configured to
releasably hold the operator interface panel 6504 in the frame
6502.
[0467] FIG. 66 is a back view of an exemplary lighting controller
comprising the frame 6502, the operator interface panel 6504 and
the latch 6506. The illustrated lighting controller further
comprises a WIFI module 6606 electrically coupled to an antenna
6602 through antenna wire 6604, and an operator interface panel
extender 6608 detachable affixed to the lighting controller. The
operator interface panel extender 6608 supplies power to the power
supply of the operator interface panel 6504 through a cable, such
as a 6-conductor flat modular cable, when the operator interface
panel extender 6608 is affixed to the operator interface panel
6504. Referring to FIG. 43, the operator interface panel extender
6608 comprises the panel RF transceiver 4304, the battery/adapter
4306, and the antenna 4312. For remote operation, the operator
interface panel extender 6608 wirelessly communicates with the
chassis/power supply 302 via the chassis RF transceiver 4302 and
antenna 4310.
[0468] An adapter 6610 configured as a wall plug-in module,
provides power to the power operator interface panel extender 6608.
The operator interface panel extender 6608 may optionally comprises
a battery and a battery charger, which provide power to the
extender 6608 and operator panel 6504, allowing the panel 6504 and
extender 6608 to be removed from the frame 6502 and operated while
moving about the property.
TERMINOLOGY
[0469] Depending on the embodiment, certain acts, events, or
functions of any of the algorithms described herein can be
performed in a different sequence, can be added, merged, or left
out altogether (e.g., not all described acts or events are
necessary for the practice of the algorithm). Moreover, in certain
embodiments, acts or events can be performed concurrently, e.g.,
through multi-threaded processing, interrupt processing, or
multiple processors or processor cores or on other parallel
architectures, rather than sequentially.
[0470] The various illustrative logical blocks, modules, and
algorithm steps described in connection with the embodiments
disclosed herein can be implemented as electronic hardware,
computer software, or combinations of both. To clearly illustrate
this interchangeability of hardware and software, various
illustrative components, blocks, modules, and steps have been
described above generally in terms of their functionality. Whether
such functionality is implemented as hardware or software depends
upon the particular application and design constraints imposed on
the overall system. The described functionality can be implemented
in varying ways for each particular application, but such
implementation decisions should not be interpreted as causing a
departure from the scope of the disclosure.
[0471] The various illustrative logical blocks and modules
described in connection with the embodiments disclosed herein can
be implemented or performed by a machine, such as a general purpose
processor, a digital signal processor (DSP), an application
specific integrated circuit (ASIC), a field programmable gate array
(FPGA) or other programmable logic device, discrete gate or
transistor logic, discrete hardware components, or any combination
thereof designed to perform the functions described herein. A
general purpose processor can be a microprocessor, but in the
alternative, the processor can be a controller, microcontroller, or
state machine, combinations of the same, or the like. A processor
can also be implemented as a combination of computing devices,
e.g., a combination of a DSP and a microprocessor, a plurality of
microprocessors, one or more microprocessors in conjunction with a
DSP core, or any other such configuration.
[0472] The steps of a method, process, or algorithm described in
connection with the embodiments disclosed herein can be embodied
directly in hardware, in a software module executed by a processor,
or in a combination of the two. A software module can reside in RAM
memory, flash memory, ROM memory, EPROM memory, EEPROM memory,
registers, hard disk, a removable disk, a CD-ROM, or any other form
of computer-readable storage medium known in the art. An exemplary
storage medium can be coupled to the processor such that the
processor can read information from, and write information to, the
storage medium. In the alternative, the storage medium can be
integral to the processor. The processor and the storage medium can
reside in an ASIC.
[0473] Conditional language used herein, such as, among others,
"can," "might," "may," "e.g.," and the like, unless specifically
stated otherwise, or otherwise understood within the context as
used, is generally intended to convey that certain embodiments
include, while other embodiments do not include, certain features,
elements, and/or states. Thus, such conditional language is not
generally intended to imply that features, elements, and/or states
are in any way required for one or more embodiments or that one or
more embodiments necessarily include logic for deciding whether
these features, elements, and/or states are included or are to be
performed in any particular embodiment. The terms "comprising,"
"including," "having," and the like are synonymous and are used
inclusively, in an open-ended fashion, and do not exclude
additional elements, features, acts, operations, and so forth.
Also, the term "or" is used in its inclusive sense (and not in its
exclusive sense) so that when used, for example, to connect a list
of elements, the term "or" means one, some, or all of the elements
in the list.
[0474] While the above detailed description has shown, described,
and pointed out novel features as applied to various embodiments,
it will be understood that various omissions, substitutions, and
changes in the form and details of the devices or algorithms
illustrated can be made without departing from the spirit of the
disclosure. As will be recognized, certain embodiments of the
inventions described herein can be embodied within a form that does
not provide all of the features and benefits set forth herein, as
some features can be used or practiced separately from others. The
scope of certain inventions disclosed herein is indicated by the
appended claims rather than by the foregoing description. All
changes which come within the meaning and range of equivalency of
the claims are to be embraced within their scope.
* * * * *