U.S. patent application number 14/526991 was filed with the patent office on 2015-04-09 for frequency agile filter using a digital filter and bandstop filtering.
The applicant listed for this patent is Rockstar Consortium US LP. Invention is credited to Mark WYVILLE.
Application Number | 20150099478 14/526991 |
Document ID | / |
Family ID | 42232833 |
Filed Date | 2015-04-09 |
United States Patent
Application |
20150099478 |
Kind Code |
A1 |
WYVILLE; Mark |
April 9, 2015 |
FREQUENCY AGILE FILTER USING A DIGITAL FILTER AND BANDSTOP
FILTERING
Abstract
A method of providing frequency dependent signal attenuation. An
RF input signal is split into a first signal portion and a second
signal portion. Discrete time filtering, a negative group delay and
bandstop filtering are applied to the first signal portion to
provide a filtered signal portion. The second signal portion is
applied to a component, and a component output signal portion is
received from the component. The component output signal portion is
combined with the filtered signal portion to provide an RF output
signal having frequency dependent attenuation.
Inventors: |
WYVILLE; Mark; (Ottawa,
CA) |
|
Applicant: |
Name |
City |
State |
Country |
Type |
Rockstar Consortium US LP |
Plano |
TX |
US |
|
|
Family ID: |
42232833 |
Appl. No.: |
14/526991 |
Filed: |
October 29, 2014 |
Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
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13751599 |
Jan 28, 2013 |
8909185 |
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14526991 |
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13131918 |
May 31, 2011 |
8385871 |
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PCT/CA2009/001721 |
Nov 26, 2009 |
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13751599 |
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61262638 |
Nov 19, 2009 |
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61119090 |
Dec 2, 2008 |
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61118686 |
Dec 1, 2008 |
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Current U.S.
Class: |
455/114.3 |
Current CPC
Class: |
H04B 1/10 20130101; H04B
1/1027 20130101; H03H 11/344 20130101; H04B 1/525 20130101; H04L
25/08 20130101; H04B 1/005 20130101; H04B 1/62 20130101 |
Class at
Publication: |
455/114.3 |
International
Class: |
H04B 1/62 20060101
H04B001/62; H04B 1/00 20060101 H04B001/00 |
Claims
1. A multiband, frequency agile radio architecture, comprising: at
least one radio frequency (RF) signal path; at least one digital
signal processing path configured to apply discrete-time filtering
and negative group delay to a signal on the digital signal
processing path to produce a compensation signal; at least one
splitter configured to couple a transmit RF signal to the at least
one RF signal path and to the at least one digital signal
processing path; and at least one signal combiner configured to
couple the compensation signal from the digital signal processing
path to the RF signal path.
2. The architecture of claim 1, wherein the at least one digital
signal processing path is configured to apply the negative group
delay by applying the negative group delay at frequencies where
attenuation is desired.
3. The architecture of claim 1, wherein the digital signal
processing path is configured to apply the negative group delay
after applying the discrete-time filtering and before applying
bandstop filtering.
4. The architecture of claim 1, wherein the digital signal
processing path comprises a negative group delay element, the
negative group delay element comprising: a time delay element
connected between the first directional coupler and the second
directional coupler on the first signal path; and a phase shifter
and an amplifier connected between the second directional coupler
and the first directional coupler on the second signal path.
5. The architecture of claim 4, wherein the phase shifter is a
variable phase shifter and the amplifier is a variable gain
amplifier.
6. The architecture of claim 1, wherein the digital signal
processing path comprises a discrete-time filter having an
independently tunable transfer function zero and pole.
7. The architecture of claim 6, wherein the discrete-time filter
comprises: a down converter configured to down convert a portion of
the transmit RF signal to provide a down converted signal portion;
a discrete-time filter element configured to discrete-time filter
the down converted signal portion to provide a discrete-time
filtered signal portion; and an up converter configured to up
convert the discrete-time filtered signal portion.
8. The architecture of claim 6, wherein the digital signal
processing path comprises a band stop filter.
9. The architecture of claim 6, wherein the digital signal
processing path is configured to apply discrete-time filtering
before applying band stop filtering.
10. The architecture of claim 6, wherein the digital signal
processing path is configured to control the discrete-time filter
responsive to an RF output signal on the RF signal path.
11. The architecture of claim 10, wherein controlling the
discrete-time filter responsive to the RF output signal comprises
controlling frequency dependent cancellation of the discrete-time
filter responsive to the RF output signal.
12. The architecture of claim 10, wherein controlling the
discrete-time filtering responsive to the RF output signal
comprises: splitting off a portion of the RF output signal to
provide an RF output signal portion; and controlling the discrete
time filtering responsive to the RF output signal portion.
13. The architecture of claim 12, wherein controlling the discrete
time filtering responsive to the RF output signal portion further
comprises: down converting the RF output signal portion to provide
a down converted output signal portion; and controlling the
discrete-time filtering responsive to the down converted output
signal portion.
14. The architecture of claim 13, wherein controlling the
discrete-time filtering responsive to the down converted output
signal portion comprises: providing the down converted output
signal portion to a controller; processing the down converted
output signal in the controller to provide a control signal; and
providing the control signal to the discrete-time filter.
15. The architecture of claim 12, wherein splitting off a portion
of the RF output signal comprises splitting off a portion of the RF
output signal at a directional coupler.
16. The architecture of claim 9, wherein the RF signal path
provides an RF output signal to an RF amplifier of an RF
receiver.
17. The architecture of claim 16, wherein the RF amplifier is a
linear low noise amplifier.
18. The architecture of claim 16, wherein the transmission line
introduces a time delay.
19. The architecture of claim 1, wherein the at least one splitter
is at least one directional coupler.
20. The architecture of claim 1, wherein the at least one signal
combiner comprises at least one directional coupler.
Description
CROSS-REFERENCE TO RELATED APPLICATIONS
[0001] This application is a Continuation of U.S. patent
application Ser. No. 13/751,599, filed Jan. 28, 2013, entitled
"FREQUENCY AGILE FILTER USING A DIGITAL FILTER AND BANDSTOP
FILTERING", which is a continuation of U.S. patent application Ser.
No. 13/131,918, entitled "FREQUENCY AGILE FILTER USING A DIGITAL
FILTER AND BANDSTOP FILTERING", now U.S. Pat. No. 8,385,871, having
a National Phase Entry date of May 31, 2011, for PCT Application
Serial No.: PCT/CA2009/001721, filed Nov. 26, 2009, and claims the
benefit of U.S. Provisional Patent Application Ser. No. 61/262,638,
filed Nov. 19, 2009, U.S. Provisional Patent Application Ser. No.
61/119,090, filed Dec. 2, 2008, and U.S. Provisional Patent
Application Ser. No. 61/118,686, filed Dec. 1, 2009, the entire
contents of each of which are hereby incorporated herein by
reference.
TECHNICAL FIELD OF THE INVENTION
[0002] The present invention relates to a frequency agile duplex
filter for use in RF filters and signal cancellation in a wireless
communication system, multiband radio architecture, system capable
of spectrum re-farming and software defined radio.
BACKGROUND OF THE INVENTION
[0003] Presently used RF filters in base stations include
mechanically tunable RF filters. These filters are coupled-cavity
filters with low-loss, high dynamic range and superior selectivity,
but requiring mechanical tuning limits the reconfigurability of the
filter in terms of carrier frequency range. What is needed is a
filter and signal cancellation system that eliminates the need for
mechanical tuning.
[0004] Feed-forward configurations of RF discrete-time filters are
also available. A known three path RF discrete-time feed-forward
filter system is shown in FIG. 1 for improving duplexer isolation.
In this figure, h.sub.1 and h.sub.2 are system blocks containing
vector modulators. The symbols labeled .tau..sub.1 and .tau..sub.2
are fixed delay lines, which classifies this system as
discrete-time.
[0005] The known RF discrete-time filters consist of RF paths
containing tunable phase shifters and variable attenuators, or
vector modulators. The number of RF paths, however, is limited to
two or three paths since each additional path requires an
additional splitter, combiner, tunable component, gain block and a
time delay element. For this reason, only low-order filtering can
be performed with known filter systems having two or three paths.
What is needed is a two path filter and signal cancellation system
that performs high-order filtering, but without needing additional
elements such as tunable phase shifters and variable attenuators,
or vector modulators for each increase of filter order.
[0006] Tunable filters have also been realized in the past with
tunable capacitors, such as MEMS, BST and varicap diodes. Heat is
dissipated into the tunable components of such known filters, and
the Q-factor of tunable capacitors is limited. The limited Q-factor
of tunable elements means they cannot be used to filter high-power
signals, and large insertion loss results for high-order
configurations. What is needed is a filter capable of filtering
high-power signals with low insertion loss for high-order
configurations.
[0007] Known filter banks contain multiple fixed filters and a
switch matrix to choose a desired filter configuration. For a large
ensemble of filter characteristics, a large number of filters and a
large switching matrix is required. The former results in a large
space commitment and possesses limited reconfigurability, while the
latter results in increasing insertion loss. What is needed is a
filter with a small footprint, a continuous range of
reconfigurations, and a low insertion loss.
[0008] A feed-forward configuration cancellation system with a
digital signal processor (DSP) on one path of the filter system has
been used to cancel the transmit signal that leaked into the
receiver in the transmit passband. The input to the feed-forward
system was the digital baseband signal that was also sent to the
primary transmitter. The cancellation system is shown in FIG. 2,
with this system only the linear portion of the transmitted RF
signal can be cancelled. There is a need for a cancellation system
that does not only cancel the linear portion of the transmitted RF
signal.
[0009] Wireless communication systems could include multiband radio
architectures, systems capable of spectrum re-farming and software
defined radio systems. Common system components in a wireless
communication system, such as an IP-based mobile system, include at
least one mobile node (or user equipment) and at least one access
point AP or a basestation (eNodeB or eNB) on a wireless
communication system. The various components on these systems may
be called different names depending on the nomenclature used on any
particular network configuration or communication system.
[0010] For instance, the term "mobile node" includes a mobile
communication unit that is called mobile terminal, "smart phones,"
or nomadic devices such as laptop PCs with wireless connectivity. A
"mobile node" or "user equipment" also encompasses PC's having
cabled (e.g., telephone line ("twisted pair"), Ethernet cable,
optical cable, and so on) connectivity to the wireless network, as
well as wireless connectivity directly to the cellular network, as
can be experienced by various makes and models of mobile terminals
("cell phones") having various features and functionality, such as
Internet access, e-mail, messaging services, and the like.
[0011] "Mobile nodes" may sometimes be referred to as user
equipment, mobile unit, mobile terminal, mobile device, or similar
names depending on the nomenclature adopted by particular system
providers. A "receiver" and "transmitter" is located at each
"access point" (AP), "basestation," or "user equipment." As such,
terms such as transmitter or receiver in the present invention are
not meant to be restrictively defined, but could include components
on each mobile communication unit or transmission device located on
the network.
SUMMARY OF THE INVENTION
[0012] The present invention proposes a frequency agile multiple
bandstop filter for use on a wireless communication system,
multi-band radio architecture, system capable of spectrum
re-farming and software defined radio. The system has a large
dynamic range which can be used to handle high transmit power, or
to handle weak receive signals in the presence of blockers. A notch
or bandstop filter is used within the invention to relax the
dynamic range requirements of the discrete-time filter when a large
dynamic range exists between the passband and desired stopband
signals.
[0013] The present invention can be used as a tunable filter, but
can also be used as a tunable signal cancellation system when the
component in the invention's RF path differs from a transmission
line. The input signal to the path containing the discrete-time
filter is tapped off the main path with a directional coupler from
the coupled port. The output signal of this path is combined back
into the output of the main path with a directional coupler. A
third directional coupler is used to tap-off the combined signal
for monitoring. Directional couplers ensure low loss to the main
path. In the present invention, an RF component is a low-loss
transmission line, a low noise amplifier or a fixed duplexer, and
the discrete-time filter is a digital filter.
BRIEF DESCRIPTION OF THE DRAWINGS
[0014] Embodiments of the present application will now be
described, by way of example only, with reference to the
accompanying drawing figures, wherein:
[0015] FIG. 1 is a block diagram of a known RF feed-forward filter
system;
[0016] FIG. 2 is a block diagram of a known RF feed-forward filter
system;
[0017] FIG. 3 is a block diagram of a first embodiment of an RF
feed-forward filter system constructed in accordance with
principles of the present invention;
[0018] FIG. 4 is a block diagram of a second embodiment of an RF
feed-forward filter system constructed in accordance with
principles of the present invention;
[0019] FIG. 5 is a more detailed block diagram of an embodiment of
an RF feed-forward filter system of the present invention;
[0020] FIG. 6 is a block diagram of a third embodiment of an RF
feed-forward filter system constructed in accordance with
principles of the present invention;
[0021] FIG. 7 is a block diagram of a fourth embodiment of an RF
feed-forward filter system constructed in accordance with
principles of the present invention;
[0022] FIG. 8 is a block diagram of a fifth embodiment of an RF
feed-forward filter system constructed in accordance with
principles of the present invention;
[0023] FIG. 9 is a block diagram of a sixth embodiment of an RF
feed-forward filter system constructed in accordance with
principles of the present invention;
[0024] FIG. 10 is comprised of FIGS. 10A and 10B in which FIG. 10A
is a block diagram of a first portion of a seventh embodiment of an
RF feed-forward filter system constructed in accordance with
principles of the present invention, and FIG. 10B is a block
diagram of a second portion of the seventh embodiment of an RF
feed-forward filter system constructed in accordance with
principles of the present invention.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
[0025] The present invention is a hybrid RF and digital signal
processor-based filter for multiband radio architectures, systems
capable of spectrum re-farming and software defined radios. The
invention can perform low-loss frequency agile multiple bandstop
filtering at RF where a large dynamic range exists at the filter
input between signals in stopband and passband. At the output of
the transmitter the invention can be used to attenuate spurs, or
noise within bands with strict emission constraints. At the input
to the receiver the invention can be used to attenuate blockers or
noise from the transmitter.
[0026] The present invention is a reconfigurable system that
synthesizes and combines a cancellation signal with the output of
an RF or analog component. The cancellation signal is synthesized
using the signal tapped-off from the first coupler. The system can
operate over a range of carrier frequencies, which means it is
frequency agile. At a specific carrier frequency, the system can
generate frequency dependent cancellation signals within the
system's bandwidth. Frequency agility and the frequency dependent
cancellation are the two components that make the system
reconfigurable.
[0027] The present invention can be used to augment a fixed
duplexer, which reduces the manufacturing and production time to
market for the augmented duplexer by relaxing the filtering
requirements of the fixed duplexer. One augmented duplexer would
satisfy the specifications of multiple customers unlike known
mechanically tuned filters.
[0028] Prior art feed-forward configurations of RF discrete-time
filters are available. A known three path RF discrete-time
feed-forward filter system is shown in FIG. 1 for improving
duplexer isolation. In this figure, h.sub.1 and h.sub.2 are system
blocks containing vector modulators. The symbols labeled
.tau..sub.1 and .tau..sub.2 are fixed delay lines, which classifies
this system as discrete-time.
[0029] In FIG. 1, a discrete-time feed-forward system 100 having
two paths is shown where a transmitter's power amplifier PA 105
provides an input signal to a directional coupler 110 via
connection 107. This system is a discrete system made with fixed
frequency components, and therefore does not demonstrate frequency
agility.
[0030] On a first path, the directional coupler 110 is coupled to a
splitter 129 via connection 125. The splitter provides two signal
paths, which include a connection to delay element one .tau..sub.1
136 via connection 134. Delay element one .tau..sub.1 136 is
coupled to RF component h1 142 via connection 139, where the phase
and amplitude of the signal are adjusted. On a second signal path
from the splitter, a connection to delay element two .tau..sub.2
135 via a connection 131. Delay element two .tau..sub.2 135 is
coupled to RF component h2 141 via connection 137, where the phase
and amplitude of the signal are adjusted. The output of the RF
component h1 142 and RF component h2 141 are coupled to the
combiner 150 through connections 145 and 143, respectively. The
output of the combiner 150 is coupled to the directional coupler
121 via connection 152.
[0031] The directional coupler 110 is coupled on a second path to a
duplexer 115. The duplexer 115 is coupled to an antenna 117, and
the duplexer is also coupled to the directional coupler 121 via
connection 119. The first and the second paths converge at the
directional coupler 121, which provides an output signal to the low
noise amplifier LNA within the receiver 155 coupled to this filter
network via connection 154.
[0032] In FIG. 1, the known RF discrete-time filters consist of RF
paths containing tunable phase shifters and variable attenuators,
or vector modulators. The number of RF paths, however, is limited
to two or three paths since each additional path requires an
additional splitter, combiner, tunable component, gain block and a
time delay element. For this reason, only low-order filtering can
be performed with known filter systems having two or three paths.
What is needed is a two path filter and signal cancellation system
that performs high-order filtering, but without needing additional
elements such as tunable phase shifters and variable attenuators,
or vector modulators for each increase of filter order.
[0033] In FIG. 2, a feed-forward system with two paths is shown
with a digital filter on one path, which improves duplexer
isolation. In FIG. 2, a digital input signal is shown at 205 and
split onto a first and a second path. On a first path, the digital
signal is sent to an FIR Filter 215 via connection 210, with the
output of the FIR Filter 215 being sent to the auxiliary
transmitter 225 via connection 220. The output of the auxiliary
transmitter 225 is sent to the directional coupler 265 via
connection 230.
[0034] On a second path, the digital signal is provided to the
transmitter 240 via connection 235. The output of the transmitter's
power amplifier 240 is provided to the duplexer 255 via connection
245. The duplexer 255 is coupled to an antenna 250, and the
duplexer is also coupled to the directional coupler 265 via
connection 260. The first and the second paths converge at the
directional coupler 265, which provides an output signal to the low
noise amplifier LNA within the receiver 275 coupled to this filter
network via connection 270.
[0035] In FIG. 2, a feed-forward configuration cancellation system
with a digital signal processor (DSP) is shown on one path of the
filter system, which has been used to cancel the transmit signal
that leaked into the receiver in the transmit passband. The input
to the feed-forward system was the digital baseband signal that was
also sent to the primary transmitter. The cancellation system is
shown in FIG. 2, with this system only the linear portion of the
transmitted RF signal can be cancelled. There is a need for a
cancellation system that does not only cancel the linear portion of
the transmitted RF signal.
[0036] An RF (or analog) component or system is connected to the
present invention in a feed-forward configuration with one signal
path containing a discrete-time filter. This configuration is shown
in FIG. 3. The signal path containing the discrete-time filter uses
its input signal to synthesize a cancellation signal, which is
combined with the RF (or analog) component's output signal. An RF
or analog bandstop filter (BSF) or notch filter is also placed in
the signal path containing the discrete-time filter to reduce the
dynamic range requirements of the discrete-time filter. The
combined signal is monitored and used to adaptively reconfigurable
the discrete-time filter and other tunable components within the
same signal path.
[0037] In FIG. 3, the system 300 is shown using the present
invention, which includes receiving an input signal RF.sub.in 305
(e.g. between 450 MHz to 3500 MHz) coupled to a directional coupler
310. On a first path, the directional coupler 310 is coupled to the
RF/Analog 1 frequency down converter 320 via connection 315. The
RF/Analog 1 frequency down converter 320 is coupled to a
discrete-time filter 330 via connection 325, where the
down-converted input signal is input into the discrete-time filter
330. The discrete-time filter 330 coupled to the RF/Analog 2
frequency up converter 340 via connection 335, and the RF/Analog 2
frequency up converter 340 is coupled to the bandstop filter BSF
350 via connection 345. The bandstop filter BSF 350 is coupled to
the directional coupler 365 via connection 355.
[0038] The directional coupler 310 is coupled on a second path to
an RF or analog component 359 via connection 357. The RF or analog
component 359 is coupled to the directional coupler 365 via
connection 363. The first and the second paths converge at the
directional coupler 365, which provides a combined signal to a
third directional coupler 373 via connection 370.
[0039] A third directional coupler is used to tap-off the combined
signal for monitoring. On a third path, the directional coupler 373
is coupled to the RF/Analog 3 frequency down converter 380 via
connection 375. The RF/Analog 3 frequency down converter 380 is
coupled to a discrete-time filter controller 387 via connection
385. The discrete-time filter controller 387 controls the frequency
dependent cancellation of the discrete-time filter 330, which it is
connected to via connection 390. The directional coupler 373 is
coupled to the output signal RF.sub.out 680 for connection to the
remainder of the network.
[0040] The invention uses two signal paths in a feed-forward
configuration with a discrete-time filter in one of the paths. A
feed-forward configuration permits the system's passband signal to
pass through the RF or analog component and experience minimal loss
from the couplers. In one embodiment, the RF component is a
low-loss transmission line, then the main path will handle high
power if the passband signal is a transmit signal, or will
minimally corrupt a weak signal if the passband signal is a receive
signal.
[0041] The input signal to the path containing the discrete-time
filter is tapped off the main path with a directional coupler from
the coupled port. The output signal of this path is combined back
into the output of the main path with a directional coupler. A
third directional coupler is used to tap-off the combined signal
for the monitoring. Directional couplers ensure low loss to the
main path. These embodiments with a third directional coupler are
shown in FIGS. 3, 4 and 10.
[0042] In FIG. 4, the system 400 is shown using the present
invention, which includes receiving an input signal RF.sub.in 405
(e.g. between 450 MHz to 3500 MHz) coupled to a directional coupler
410. On a first path, the directional coupler 410 is coupled to the
RF/Analog 1 frequency down converter 460 via connection 455. The
RF/Analog 1 frequency down converter 460 is coupled to a digital
filter 464 via connection 463, where the down-converted input
signal is input into the digital filter 464. The digital filter 464
is a digital filter coupled to the RF/Analog 2 frequency up
converter 470 via connection 467, and the RF/Analog 2 frequency up
converter 470 is coupled to the bandstop filter BSF 485 via
connection 480. The bandstop filter BSF 485 is coupled to the
directional coupler 430 via connection 490.
[0043] The directional coupler 410 is coupled on a second path to a
time delay element .tau..sub.d 420 via connection 415. The time
delay element .tau..sub.d 420 is coupled to the directional coupler
430 via connection 425. The first and the second paths converge at
the directional coupler 430, which provides a combined signal to a
third directional coupler 440 via connection 435.
[0044] A third directional coupler is used to tap-off the combined
signal for monitoring. On a third path, the directional coupler 440
is coupled to the RF/Analog 3 frequency down converter 445 via
connection 442. The RF/Analog 3 frequency down converter 445 is
coupled to a digital filter controller 449 via connection 447. The
digital filter controller 449 controls the frequency dependent
cancellation of the digital filter 464, which it is connected to
via connection 450. The directional coupler 440 is coupled to the
output signal RF.sub.out 495 for connection to the remainder of the
network.
[0045] In FIG. 10, a more detailed diagram of the invention is
shown with component level identifications. In FIG. 10, the system
1000 is shown using the present invention, which includes receiving
an input signal RF.sub.in 1105 (e.g. between 450 MHz to 3500 MHz)
coupled to a directional coupler 1010. On a first path, the
directional coupler 1010 is coupled to the RF/Analog 1 frequency
down converter via connection 1012. The connection 1012 is coupled
to amplifier 1013, which is coupled to a splitter 1015 via
connection 1014.
[0046] The splitter 1015 is connected to down converter mixers 1026
and 1028 via connections 1016 and 1017, respectively. Down
converter mixer 1026 is coupled to the analog low pass filter 1034
via connection 1032, and down converter mixer 1028 is coupled to
the analog low pass filter 1036 via connection 1030. The analog low
pass filter 1034 is coupled to the analog to digital converter 1044
via connection 1042, and the analog low pass filter 1036 is coupled
to the analog to digital converter 1040 via connection 1038.
[0047] The RF/Analog 1 frequency down converter is coupled to
digital filter 1050, where the down-converted input signal is input
into the digital filter 1050. Specifically, the analog to digital
converter 1044 is coupled to the digital filter 1050 via connection
1046, and the analog to digital converter 1040 is coupled to the
digital filter 1050 via connection 1048.
[0048] The digital filter 1050 is a digital filter coupled to the
RF/Analog 2 frequency up converter. Specifically, the digital
filter 1050 is coupled to digital to analog converter 1056 and
digital to analog converter 1059 via connections 1051 and 1052,
respectively. The digital to analog converter 1056 is coupled to
the analog low pass filter 1062 via connection 1058, and the
digital to analog converter 1059 is coupled to the analog low pass
filter 1064 via connection 1060.
[0049] The analog low pass filter 1062 is coupled to the up
converter mixer 1068 via connection 1066. The analog low pass
filter 1064 is coupled to the up converter mixer 1070 via
connection 1065. Up converter mixer 1068 and up converter mixer
1070 are coupled to the combiner 1080 via connections 1075 and
1078, respectively. The combiner 1080 is coupled to an amplifier
1081 via connection 1079, and the amplifier 1081 is coupled to the
bandstop filter via connection 1082.
[0050] The bandstop filter is shown in a discrete-time
configuration that has an independently tunable transfer function
zero and pole. Connection 1082 is coupled to splitter component
1085, which splits the signal into two paths. On the first path
from splitter 1085, signal 1107 is transmitted to combiner 1108,
which provides a signal along line 1109 to vector modulator VM1
1111, which provides an output signal to the splitter 1101. The
splitter 1101 provides two signal, one along line 1102 to vector
modulator VM2 1103.
[0051] VM2 1103 provides an output to time delay element
.tau..sub.2 1105 along line 1104, which provides an output signal
from combination with the other input signal of combiner 1108 along
line 1106. On the other path from splitter 1101, the second signal
is provided on line 1100 to combiner 1089. On the second path from
splitter 1085, the second output signal 1086 is provided to time
delay element .tau..sub.1 1087, which provides an output signal
along line 1088 to combiner 1089. The bandstop filter T-BSF is
coupled to the directional coupler 1035 via connection 1090.
[0052] Converter mixers are coupled to a local frequency
oscillator, f.sub.LO, which provides a base signal with the
frequency of the local oscillator to the converters. The local
oscillator controls the frequency agility of the invention. Down
converter mixer 1028 and up converter mixer 1070 are coupled to
f.sub.LO via connections 1020 and 1073 respectively. 90.degree.
phase shifter 1022 is coupled to f.sub.LO via connection 1021, and
90.degree. phase shifter 1072 is coupled to f.sub.LO via connection
1071. 90.degree. phase shifter 1022 is coupled to down converter
mixer 1026 via connection 1024, and 90.degree. phase shifter 1072
is coupled to up converter mixer 1068 via connection 1074.
[0053] The directional coupler 1010 is coupled on a second path to
a time delay element .tau..sub.d 1020 via connection 1015. The time
delay element .tau..sub.d 1020 is coupled to the directional
coupler 1035 via connection 1025. The first and the second paths
converge at the directional coupler 1035, which provides an output
signal to a third directional coupler 1130.
[0054] A third directional coupler 1130 is used to tap-off the
combined signal for the monitoring. On a third path, the
directional coupler 1130 is coupled to the RF/Analog 3 frequency
down converter via connection 1135. The connection 1135 is coupled
to amplifier 1140, which is coupled to a splitter 1145 via
connection 1142. The splitter 1145 is connected to down converter
mixers 1160 and 1165 via connections 1150 and 1155, respectively.
Down converter mixer 1160 is coupled to the analog low pass filter
1183 via connection 1178, and down converter mixer 1165 is coupled
to the analog low pass filter 1180 via connection 1179. The analog
low pass filter 1183 is coupled to the analog to digital converter
1189 via connection 1187, and the analog low pass filter 1180 is
coupled to the analog to digital converter 1191 via connection
1185.
[0055] Converter mixers 1165 and 1160 in the RF/Analog 3 frequency
down converter are coupled to a local frequency oscillator,
f.sub.LO, which provides a base signal with the frequency of the
local oscillator to the down converters. Down converter mixer 1165
is coupled to f.sub.LO via connection 1171. 90.degree. phase
shifter 1175 is coupled to f.sub.LO via connection 1172. 90.degree.
phase shifter 1175 is coupled to down converter mixer 1160 via
connection 1173.
[0056] The RF/Analog 3 frequency down converter is coupled to an
algorithm processor from the analog to digital converter 1189 via
connection 1190 and from analog to digital converter 1191 via
connection 1195, where the digital filter 1050 is provided with
input and control signal. The RF/Analog 3 frequency down converter
is coupled to a digital filter controller to provide those control
signals. The digital filter controller controls the frequency
dependent cancellation of the digital filter 1050. The directional
coupler 1130 is coupled to the output signal RF.sub.out for
connection to the remainder of the network.
[0057] The discrete-time filter performs the filtering necessary to
synthesize a cancellation signal suitable to cancel the undesired
signal components present in the main signal path. This filter only
needs to operate on the stopband signals and not the passband
signals, hence the dynamic range of the signal to be filtered by
the discrete-time filter can be less than the dynamic range of the
input or output signal of the invention.
[0058] The discrete-time filter is preceded with a down-conversion
stage and anti-alias filtering, and is followed by reconstruction
filtering and an up-conversion stage. A gain stage is used prior to
the down-conversion stage to improve the signal path's noise
figure. A gain stage is used after the up-conversion stage to
ensure the cancellation signals are as large as the signals to be
cancelled in the main path.
[0059] The notch or bandstop filter relaxes the dynamic range
requirements of the discrete-time filter. If placed after the
discrete-time filter, then it can be used to reduce the noise in
the system's passband. This configuration is beneficial in a
receiver. If the notch filter is placed before the discrete-time
filter, then it can be used to attenuate a large signal in the
system's passband. This configuration is beneficial in a
transmitter. In both locations, the notch filter reduces the
dynamic range requirements of the other components in the signal
path including the discrete-time filter.
[0060] The negative group delay circuit takes some of the filtering
burden off the DSP filter. Optimization of the DSP filter shows
that frequency bands where cancellation is desired have negative
group delay in the digital filter's frequency response. By using
negative group delay circuits, the digital filter can perform as
well as if it had no negative group delay circuits, but with fewer
filter taps. Conversely, if the number of filter taps is not
reduced, then the negative group delay augmented filter will have
more degrees of freedom to optimize a cost function.
[0061] A directional coupler and down-conversion stage is located
after the cancellation signal is combined with the main path
signal. This subsystem is used to monitor the output. This
monitored signal is processed, then used to control the adaptation
of the digital filter and any tunable components in the system.
[0062] The system has a large dynamic range which can be used to
handle high transmit power, or to handle weak receive signals. A
notch or bandstop filter is used to relax the dynamic range
requirements of the discrete-time filter when a large dynamic range
exists between the passband and desired stopband signals. In one or
more embodiments of the invention, the RF component is a low-loss
transmission line, and the discrete-time filter is a digital
filter. This embodiment is shown in FIG. 4, and in more detail in
FIG. 5. In these embodiments, the invention may be used as a
tunable multiple band-stop filter, or multiple notch filter. In
this embodiment the invention is in the field of tunable filters,
but when the RF component differs from a transmission line, then it
is in the field of tunable signal cancellation systems.
[0063] Prior to the input of the low noise amplifier the invention
can be used to attenuate blockers and transmitter noise outside of
the receiver passband. These embodiments are shown in FIGS. 5
through 9. The invention can be used for isolation improvement for
components with more than two ports. The invention can be used to
cancel transmitter noise that leaks through a fixed duplexer into
the receiver in the receiver and transmitter passbands. The
invention can be used for linearity relaxation for components along
the signal chain in the receiver. The invention can be used to
cancel large signals outside of the system's passband at the output
of any component. This cancellation will reduce the dynamic range
of the signal, hence relax the linearity requirements for the
proceeding components.
[0064] In FIG. 5, a detailed diagram for the present invention is
shown where the major components are described with more
specificity. In FIG. 5, the system 500 is shown using the present
invention, which includes receiving an input signal RF.sub.in 505
(e.g. between 450 MHz to 3500 MHz) coupled to a directional coupler
510. On a first path, the directional coupler 510 is coupled to the
RF/Analog 1 frequency down converter 535 via connection 530. The
connection 530 is coupled to amplifier 537, which is coupled to a
splitter 540 via connection 538.
[0065] The splitter 540 is connected to down converter mixers 543
and 563 via connections 541 and 560, respectively. Down converter
mixer 543 is coupled to the analog low pass filter 550 via
connection 545, and down converter mixer 563 is coupled to the
analog low pass filter 570 via connection 565. The analog low pass
filter 550 is coupled to the analog to digital converter 553 via
connection 551, and the analog low pass filter 570 is coupled to
the analog to digital converter 573 via connection 571.
[0066] The RF/Analog 1 frequency down converter 535 is coupled to
digital filter 558, where the down-converted input signal is input
into the digital filter 558. Specifically, the analog to digital
converter 553 is coupled to the digital filter 558 via connection
555, and the analog to digital converter 573 is coupled to the
digital filter 558 via connection 575.
[0067] The digital filter 558 is a digital filter coupled to the
RF/Analog 2 frequency up converter 506. Specifically, the digital
filter 558 is coupled to digital to analog converter 593 and
digital to analog converter 595 via connections 591 and 592,
respectively. The digital to analog converter 593 is coupled to the
analog low pass filter 511 via connection 597, and the digital to
analog converter 595 is coupled to the analog low pass filter 512
via connection 599.
[0068] The analog low pass filter 511 is coupled to the up
converter mixer 536 via connection 513. The analog low pass filter
512 is coupled to the up converter mixer 535 via connection 514. Up
converter mixer 536 and up converter mixer 535 are coupled to the
combiner 523 via connections 521 and 522, respectively. The
combiner 523 is coupled to an amplifier 526 via connection 524, and
the amplifier 526 is coupled to the bandstop filter 529 via
connection 528. Generally, the RF/Analog 2 frequency up converter
506 is coupled to the bandstop filter T-BSF 529 via connection 528.
The bandstop filter T-BSF 529 is coupled to the directional coupler
527 via connection 531.
[0069] The directional coupler 510 is coupled on a second path to a
time delay element .tau..sub.d 520 via connection 515. The time
delay element .tau..sub.d 520 is coupled to the directional coupler
527 via connection 525. The first and the second paths converge at
the directional coupler 527, which provides an output signal
RF.sub.out to the remainder of the network.
[0070] Converter mixers are coupled to a local frequency oscillator
.omega..sub.p 587 which provides a base signal with the frequency
of the local oscillator to the down converters. The local
oscillator controls the frequency agility of the invention 500.
Down converter mixer 563 and up converter mixer 535 are coupled to
.omega..sub.p via connections 588 and 589 respectively. 90.degree.
phase shifter 583 is coupled to .omega..sub.p via connection 588,
and 90.degree. phase shifter 532 is coupled to .omega..sub.p via
connection 589. 90.degree. phase shifter 583 is coupled to down
converter mixer 543 via connection 585, and 90.degree. phase
shifter 532 is coupled to up converter mixer 536 via connection
533.
[0071] In FIG. 6, the system 600 is shown using the present
invention, which includes receiving an input signal RF.sub.in 605
(e.g. between 450 MHz to 3500 MHz) coupled to a directional coupler
610. On a first path, the directional coupler 610 is coupled to the
RF/Analog 1 frequency down converter 620 via connection 615. The
RF/Analog 1 frequency down converter 620 is coupled to digital
filter 630 via connection 625, where the down-converted input
signal is input into the digital filter 630. The digital filter 630
is a discrete-time filter coupled to the RF/Analog 2 frequency up
converter 640 via connection 635, and the RF/Analog 2 frequency up
converter 640 is coupled to the negative group delay (NGF) element
646 via connection 645.
[0072] The NGF element 646 can be a single pole RF discrete time
system, comprising a first input signal provided to a first NGF
directional coupler via connection 645, which provides a signal
along a first signal path through a time delay element to a second
NGF directional coupler. The second NGF directional coupler
provides a output NGF signal along connection 647 to the bandstop
filter T-BSF 650.
[0073] The second NGF directional coupler also provides for a
feedback signal split along a second pathway from the second NGF
directional coupler through an amplifier, a variable phase shifter,
a variable gain amplifier and a fixed time delay. This second
signal pathway in the NGF element 646 is then coupled back into the
first NGF directional coupler on the NGF element 646 to combine
with the signal being transferred along the first signal pathway in
the NGF element 646.
[0074] The bandstop filter T-BSF 650 is coupled to the second
directional coupler 675 via connection 655. The first directional
coupler 610 is coupled on a second path to a time delay element
.tau..sub.d 665 via connection 660. The time delay element
.tau..sub.d 665 is coupled to the second directional coupler 675
via connection 670 where the first and second signal pathways are
recombined. The first and the second paths converge at the second
directional coupler 675, which provides an output signal RF.sub.out
680 to the low noise amplifier LNA on the network.
[0075] In FIG. 7, the system 700 is shown using the present
invention, which includes receiving an input signal RF.sub.in 705
(e.g. between 450 MHz to 3500 MHz) coupled to a directional coupler
710 via line 707. On a first path, the directional coupler 710 is
coupled to the RF/Analog 1 frequency down converter 722 via
connection 711. The RF/Analog 1 frequency down converter 722 is
coupled to digital filter 726 via connection 724, where the
down-converted input signal is input into the digital filter 726.
The digital filter 726 is a discrete-time filter coupled to the
RF/Analog 2 frequency up converter 735 via connection 728, and the
RF/Analog 2 frequency up converter 735 is coupled to the bandstop
filter T-BSF 739 via connection 737. The bandstop filter T-BSF 739
is coupled to the directional coupler 720 via connection 741.
[0076] The directional coupler 710 is coupled on a second path to
the low noise amplifier Linear LNA 715 via connection 712. The low
noise amplifier Linear LNA 715 is coupled to the directional
coupler 720 via connection 717. The first and the second paths
converge at the directional coupler 720, which provides an output
signal RF.sub.out 745 to the down-converter coupled to this filter
network. In this embodiment, interference cancellation is performed
prior to the down-converter mixer.
[0077] In FIG. 8, the system 800 is shown using the present
invention, which includes receiving an input signal RF.sub.in 805
(e.g. between 450 MHz to 3500 MHz) coupled to a directional coupler
810. On a first path, the directional coupler 810 is coupled to the
bandstop filter T-BSF 820 via connection 815. The bandstop filter
T-BSF 820 is coupled to the RF/Analog 1 frequency down converter
830 via connection 825. The RF/Analog 1 frequency down converter
830 is coupled to digital filter 840 via connection 835, where the
down-converted input signal is input into the digital filter 840.
The digital filter 840 is a discrete-time filter coupled to the
RF/Analog 2 frequency up converter 850 via connection 845, and the
RF/Analog 2 frequency up converter 850 is coupled to the
directional coupler 875 via connection 855.
[0078] The directional coupler 810 is coupled on a second path to a
time delay element .tau..sub.d 865 via connection 860. The time
delay element .tau..sub.d 865 is coupled to the directional coupler
875 via connection 870. The first and the second paths converge at
the directional coupler 875, which provides an output signal
RF.sub.out 880 to the duplexer circuit coupled to this filter
network. In this embodiment, noise cancellation is performed after
the transmitter to perform multiple stopband filtering on the
output signal to avoid violating the emission mask, and to cancel
transmitter noise in the receiver passband.
[0079] In FIG. 9, the system 900 is shown using the present
invention, which includes receiving an input signal RF.sub.in 905
(e.g. between 450 MHz to 3500 MHz) coupled to a directional coupler
910. On a first path, the directional coupler 910 is coupled to the
bandstop filter T-BSF 920 via connection 915. The bandstop filter
T-BSF 920 is coupled to the RF/Analog 1 frequency down converter
930 via connection 925. The RF/Analog 1 frequency down converter
930 is coupled to digital filter 940 via connection 935, where the
down-converted input signal is input into the digital filter 940.
The digital filter 940 is a discrete-time filter coupled to the
RF/Analog 2 frequency up converter 950 via connection 945, and the
RF/Analog 2 frequency up converter 950 is coupled to the
directional coupler 980 via connection 955.
[0080] The directional coupler 910 is coupled on a second path to a
duplexer 970 via connection 960. The duplexer 970 is coupled to an
antenna 971, and the duplexer is also coupled to the directional
coupler 980 via connection 975. The first and the second paths
converge at the directional coupler 980, which provides an output
signal RF.sub.out 985 to the low noise amplifier LNA coupled to
this filter network. In this embodiment, transmitter noise
cancellation is performed to improve the isolation of a fixed
duplexer circuit.
[0081] The present invention proposes a hybrid RF-digital signal
processing based RF filter and signal cancellation system for use
on a wireless communication system, multi-band radio architecture,
system capable of spectrum re-farming and software defined radio.
The present invention can be used to augment a fixed duplexer,
which reduces the manufacturing and production time to market for
the augmented duplexer by relaxing the filtering requirements of
the fixed duplexer. One augmented duplexer would satisfy the
specifications of multiple customers unlike known mechanically
tuned filters.
[0082] The above-described embodiments of the present application
are intended to be examples only. Those of skill in the art may
effect alterations, modifications and variations to the particular
embodiments without departing from the scope of the application. In
the foregoing description, numerous details are set forth to
provide an understanding of the present invention. However, it will
be understood by those skilled in the art that the present
invention may be practiced without these details. While the
invention has been disclosed with respect to a limited number of
embodiments, those skilled in the art will appreciate numerous
modifications and variations there from. It is intended that the
appended claims cover such modifications and variations as fall
within the true spirit and scope of the invention.
* * * * *