U.S. patent application number 14/075535 was filed with the patent office on 2014-10-16 for universal platform module for a plurality of communication protocols.
This patent application is currently assigned to PARKERVISION, INC.. The applicant listed for this patent is ParkerVision, Inc.. Invention is credited to Michael J. Bultman, Robert W. Cook, Richard C. Looke, Charley D. Moses, JR., David F. Sorrells.
Application Number | 20140307760 14/075535 |
Document ID | / |
Family ID | 47017461 |
Filed Date | 2014-10-16 |
United States Patent
Application |
20140307760 |
Kind Code |
A1 |
Sorrells; David F. ; et
al. |
October 16, 2014 |
Universal Platform Module for a Plurality of Communication
Protocols
Abstract
A communication system comprising a multi-protocol, multi-bearer
sub-system is described herein. The sub-system is a universal
platform module that can transmit and receive one or more
information signals in one or more protocols using one or more
bearer services. In one embodiment, the sub-system may form a
portion of a transceiver that is composed of a transmitter and a
receiver, and which is a gateway server between a personal area
network (PAN) and the global wireless network.
Inventors: |
Sorrells; David F.;
(Middleburg, FL) ; Bultman; Michael J.;
(Jacksonville, FL) ; Cook; Robert W.;
(Switzerland, FL) ; Looke; Richard C.;
(Jacksonville, FL) ; Moses, JR.; Charley D.;
(Jacksonville, FL) |
|
Applicant: |
Name |
City |
State |
Country |
Type |
ParkerVision, Inc. |
Jacksonville |
FL |
US |
|
|
Assignee: |
PARKERVISION, INC.
Jacksonville
FL
|
Family ID: |
47017461 |
Appl. No.: |
14/075535 |
Filed: |
November 8, 2013 |
Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
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13550501 |
Jul 16, 2012 |
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14075535 |
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09569045 |
May 10, 2000 |
8295406 |
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13550501 |
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09550642 |
Apr 14, 2000 |
7065162 |
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09569045 |
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09521878 |
Mar 9, 2000 |
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09550642 |
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Current U.S.
Class: |
375/219 |
Current CPC
Class: |
H04L 27/2601 20130101;
H04W 88/06 20130101; H04L 27/0008 20130101; H03D 7/00 20130101;
H04L 27/18 20130101; H04L 27/02 20130101; H04L 27/34 20130101 |
Class at
Publication: |
375/219 |
International
Class: |
H04L 27/26 20060101
H04L027/26 |
Claims
1. A universal platform module, comprising: at least one universal
platform sub-module, comprising at least one universal frequency
conversion module that frequency converts a signal; and a control
module that provides operating information for said at least one
universal platform sub-module.
Description
CROSS-REFERENCE TO OTHER APPLICATIONS
[0001] This is a continuation of pending U.S. patent application
Ser. No. 13/550,501 titled "Universal Platform Module for a
Plurality of Communication Protocols", filed Jul. 16, 2012, which
is a continuation of U.S. patent application Ser. No. 09/569,045,
titled "Universal Platform Module for a Plurality of Communication
Protocols," filed on May 10, 2000, now U.S. Pat. No. 8,295,406,
which is a continuation-in-part application of U.S. patent
application Ser. No. 09/5550,642, titled "Method and System for
Down Converting an Electromagnetic Signal and Transforms for Same,"
filed on Apr. 14, 2000, now U.S. Pat. No. 7,065,162, which is a
continuation-in-part application of U.S. application Ser. No.
09/521,878, titled "Matched Filter Characterization and
Implementation of Universal Frequency Translation Method and
Apparatus," filed Mar. 9, 2000, abandoned, all of which are herein
incorporated by reference in their entireties.
[0002] The following applications of common assignee are related to
the present application, and are all herein incorporated by
reference in their entireties:
[0003] "Wireless Local Area Network (LAN) Using Universal Frequency
Translation Technology," Ser. No. 60/147,129, filed Aug. 4, 1999,
Attorney Docket No. 1744.0630000.
[0004] "Method, System, and Apparatus for Balanced Frequency
Up-Conversion of a Baseband Signal," Ser. No. 09/525,615, filed
Mar. 14, 2000, Attorney Docket No. 1744.0450003
[0005] "Wireless Telephone Using Universal Frequency Translation,"
Ser. No. 60/195,328, filed Apr. 10, 2000, Attorney Docket No.
1744.0070000.
BACKGROUND OF THE INVENTION
[0006] 1. Field of the Invention
[0007] The present invention is generally related to multi-mode
communications devices, and more particularly, to multi-mode
communications devices implemented using universal frequency
translation technology.
[0008] 2. Related Art
[0009] Recent developments in computing and communications systems
seek to enhance the performance and interoperability of devices.
These devices, which include personal digital assistants (PDAs),
mobile phones, set-top boxes, handheld personal computers, pagers,
laptop personal computers, as well as home and office appliances,
are being constructed to handle the tasks of traditional systems.
These systems are currently constructed for receiving information
signals for only a few platforms. Typically, the platforms
available for a given device are predetermined. These systems can
suffer from the disadvantage of being obsolete within a year or so
of production, as well as being relatively expensive in terms of
cost and power consumption. Conventional wireless communications
circuitry is complex and has a large number of circuit parts. This
complexity and high parts count increases overall cost.
Additionally, higher part counts result in higher power
consumption, which is undesirable, particularly in battery powered
units.
[0010] Consequently, it is desirable to provide a method and
apparatus for a universal platform module (UPM) for devices.
SUMMARY OF THE INVENTION
[0011] The present invention is directed to a universal platform
module (UPM). The UPM includes at least one universal frequency
translation (UFT) module implemented for signal reception,
transmission and/or processing. In one embodiment, the UMP also
includes a control module for operating the UFT module for any
selected platform or combination of platforms.
[0012] Further features and advantages of the invention, as well as
the structure and operation of various embodiments of the
invention, are described in detail below with reference to the
accompanying drawings.
BRIEF DESCRIPTION OF THE FIGURES
[0013] The invention shall be described with reference to the
accompanying figures, wherein:
[0014] FIG. 1A is a block diagram of a universal frequency
translation (UFT) module according to an embodiment of the
invention;
[0015] FIG. 1B is a more detailed diagram of a universal frequency
translation (UFT) module according to an embodiment of the
invention;
[0016] FIG. 1C illustrates a UFT module used in a universal
frequency down-conversion (UFD) module according to an embodiment
of the invention;
[0017] FIG. 1D illustrates a UFT module used in a universal
frequency up-conversion (UFU) module according to an embodiment of
the invention;
[0018] FIG. 2 is a block diagram of a universal frequency
translation (UFT) module according to an alternative embodiment of
the invention;
[0019] FIG. 3 is a block diagram of a universal frequency
up-conversion (UFU) module according to an embodiment of the
invention;
[0020] FIG. 4 is a more detailed diagram of a universal frequency
up-conversion (UFU) module according to an embodiment of the
invention;
[0021] FIG. 5 is a block diagram of a universal frequency
up-conversion (UFU) module according to an alternative embodiment
of the invention;
[0022] FIGS. 6A-6I illustrate example waveforms used to describe
the operation of the UFU module;
[0023] FIG. 7 illustrates a UFT module used in a receiver according
to an embodiment of the invention;
[0024] FIG. 8 illustrates a UFT module used in a transmitter
according to an embodiment of the invention;
[0025] FIG. 9 illustrates an environment comprising a transmitter
and a receiver, each of which may be implemented using a UFT module
of the invention;
[0026] FIG. 10 illustrates a transceiver according to an embodiment
of the invention;
[0027] FIG. 11 illustrates a transceiver according to an
alternative embodiment of the invention;
[0028] FIG. 12 illustrates an environment comprising a transmitter
and a receiver, each of which may be implemented using enhanced
signal reception (ESR) components of the invention;
[0029] FIG. 13 illustrates a UFT module used in a unified
down-conversion and filtering (UDF) module according to an
embodiment of the invention;
[0030] FIG. 14 illustrates an example receiver implemented using a
UDF module according to an embodiment of the invention;
[0031] FIGS. 15A-15F illustrate example applications of the UDF
module according to embodiments of the invention;
[0032] FIG. 16 illustrates an environment comprising a transmitter
and a receiver, each of which may be implemented using enhanced
signal reception (ESR) components of the invention, wherein the
receiver may be further implemented using one or more UFD modules
of the invention;
[0033] FIG. 17 illustrates a unified down-converting and filtering
(UDF) module according to an embodiment of the invention;
[0034] FIG. 18 is a table of example values at nodes in the UDF
module of FIG. 17;
[0035] FIG. 19 is a detailed diagram of an example UDF module
according to an embodiment of the invention;
[0036] FIGS. 20A and 20A-1 are example aliasing modules according
to embodiments of the invention;
[0037] FIGS. 20B-20F are example waveforms used to describe the
operation of the aliasing modules of FIGS. 20A and 20A-1;
[0038] FIG. 21 illustrates an enhanced signal reception system
according to an embodiment of the invention;
[0039] FIGS. 22A-22F are example waveforms used to describe the
system of FIG. 21;
[0040] FIG. 23A illustrates an example transmitter in an enhanced
signal reception system according to an embodiment of the
invention;
[0041] FIGS. 23B and 23C are example waveforms used to further
describe the enhanced signal reception system according to an
embodiment of the invention;
[0042] FIG. 23D illustrates another example transmitter in an
enhanced signal reception system according to an embodiment of the
invention;
[0043] FIGS. 23E and 23F are example waveforms used to further
describe the enhanced signal reception system according to an
embodiment of the invention;
[0044] FIG. 24A illustrates an example receiver in an enhanced
signal reception system according to an embodiment of the
invention;
[0045] FIGS. 24B-24J are example waveforms used to further describe
the enhanced signal reception system according to an embodiment of
the invention;
[0046] FIG. 25A illustrates a high level block diagram of an
example conventional multi-mode device;
[0047] FIG. 25B illustrates a detailed block diagram of a
conventional receiver;
[0048] FIG. 25C illustrates a detailed block diagram of a
conventional transmitter;
[0049] FIG. 26A-26C illustrate example universal platform modules
according to embodiments of the invention;
[0050] FIGS. 27A-27C illustrate example universal platform
sub-module receivers according to embodiments of the invention;
[0051] FIG. 28 illustrates an example UFD module in greater detail
according to an embodiment of the invention;
[0052] FIG. 29 illustrates an exemplary I/Q modulation embodiment
of a receiver, according to the invention;
[0053] FIGS. 30A-30C illustrate example universal platform
sub-module transmitters according to embodiments of the
invention;
[0054] FIG. 31 illustrates further detail of an example modulator
of FIG. 30B, operating in a pulse modulation (PM) mode, according
to an embodiment of the invention;
[0055] FIG. 32 illustrates an universal platform module according
to an embodiment of the invention;
[0056] FIG. 33 illustrates an UFU module in greater detail
according to an embodiment of the invention;
[0057] FIGS. 34 and 35 illustrate exemplary block diagrams of a
transmitter operating in an I/Q modulation mode, according to
embodiments of the invention;
[0058] FIG. 36 illustrates a block diagram of a receiver
incorporating unified down-convert and filtering according to an
embodiment of the invention;
[0059] FIG. 37 illustrates a high level block diagram of an
universal platform sub-module transceiver implementation according
to an embodiment of the invention;
[0060] FIG. 38 illustrates a high level block diagram of universal
platform sub-module receiver and transmitter implementations
according to an embodiment of the invention;
[0061] FIG. 39 shows some possible protocol/bearer service
combinations;
[0062] FIG. 40 shows possible representative groupings of network
links;
[0063] FIG. 41 illustrates a high level block diagram of an
universal platform sub-module transceiver implementation according
to an embodiment of the invention;
[0064] FIG. 42 shows a chart of some standards, protocols, and
bearer services;
[0065] FIG. 43 illustrates a high level block diagram of a specific
implementation of device employing a universal platform module;
[0066] FIG. 44 illustrates a high level block diagram of a flexible
implementation of a device employing a universal platform
module;
[0067] FIGS. 45A-D illustrate example implementations of a switch
module according to embodiments of the invention;
[0068] FIGS. 46A-D illustrate example aperture generators;
[0069] FIG. 46E illustrates an oscillator according to an
embodiment of the present invention;
[0070] FIG. 47 illustrates an energy transfer system with an
optional energy transfer signal module according to an embodiment
of the invention;
[0071] FIG. 48 illustrates an aliasing module with input and output
impedance match according to an embodiment of the invention;
[0072] FIG. 49A illustrates an example pulse generator;
[0073] FIGS. 49B and C illustrate example waveforms related to the
pulse generator of FIG. 49A;
[0074] FIG. 50 illustrates an example energy transfer module with a
switch module and a reactive storage module according to an
embodiment of the invention;
[0075] FIGS. 51A-B illustrate example energy transfer systems
according to embodiments of the invention;
[0076] FIG. 52A illustrates an example energy transfer signal
module according to an embodiment of the present invention;
[0077] FIG. 52B illustrates a flowchart of state machine operation
according to an embodiment of the present invention;
[0078] FIG. 52C is an example energy transfer signal module;
[0079] FIG. 53 is a schematic diagram of a circuit to down-convert
a 915 MHZ signal to a 5 MHZ signal using a 101.1 MHZ clock
according to an embodiment of the present invention;
[0080] FIG. 54 shows example simulation waveforms for the circuit
of FIG. 53 according to embodiments of the present invention;
[0081] FIG. 55 is a schematic diagram of a circuit to down-convert
a 915 MHZ signal to a 5 MHZ signal using a 101 MHZ clock according
to an embodiment of the present invention;
[0082] FIG. 56 shows example simulation waveforms for the circuit
of FIG. 55 according to embodiments of the present invention;
[0083] FIG. 57 is a schematic diagram of a circuit to down-convert
a 915 MHZ signal to a 5 MHZ signal using a 101.1 MHZ clock
according to an embodiment of the present invention;
[0084] FIG. 58 shows example simulation waveforms for the circuit
of FIG. 57 according to an embodiment of the present invention;
[0085] FIG. 59 shows a schematic of the circuit in FIG. 53
connected to an FSK source that alternates between 913 and 917 MHZ
at a baud rate of 500 Kbaud according to an embodiment of the
present invention;
[0086] FIG. 60A illustrates an example energy transfer system
according to an embodiment of the invention;
[0087] FIGS. 60B-C illustrate example timing diagrams for the
example system of FIG. 60A;
[0088] FIG. 61 illustrates an example bypass network according to
an embodiment of the invention;
[0089] FIG. 62 illustrates an example bypass network according to
an embodiment of the invention;
[0090] FIG. 63 illustrates an example embodiment of the
invention;
[0091] FIG. 64A illustrates an example real time aperture control
circuit according to an embodiment of the invention;
[0092] FIG. 64B illustrates a timing diagram of an example clock
signal for real time aperture control, according to an embodiment
of the invention;
[0093] FIG. 64C illustrates a timing diagram of an example optional
enable signal for real time aperture control, according to an
embodiment of the invention;
[0094] FIG. 64D illustrates a timing diagram of an inverted clock
signal for real time aperture control, according to an embodiment
of the invention;
[0095] FIG. 64E illustrates a timing diagram of an example delayed
clock signal for real time aperture control, according to an
embodiment of the invention;
[0096] FIG. 64F illustrates a timing diagram of an example energy
transfer including pulses having apertures that are controlled in
real time, according to an embodiment of the invention;
[0097] FIG. 65 illustrates an example embodiment of the
invention;
[0098] FIG. 66 illustrates an example embodiment of the
invention;
[0099] FIG. 67 illustrates an example embodiment of the
invention;
[0100] FIG. 68 illustrates an example embodiment of the
invention;
[0101] FIG. 69A is a timing diagram for the example embodiment of
FIG. 65;
[0102] FIG. 69B is a timing diagram for the example embodiment of
FIG. 66;
[0103] FIG. 70A is a timing diagram for the example embodiment of
FIG. 67;
[0104] FIG. 70B is a timing diagram for the example embodiment of
FIG. 68;
[0105] FIG. 71A illustrates and example embodiment of the
invention;
[0106] FIG. 71B illustrates example equations for determining
charge transfer, in accordance with the present invention;
[0107] FIG. 71C illustrates relationships between capacitor
charging and aperture, in accordance with an embodiment of the
present invention;
[0108] FIG. 71D illustrates relationships between capacitor
charging and aperture, in accordance with an embodiment of the
present invention;
[0109] FIG. 71E illustrates power-charge relationship equations, in
accordance with an embodiment of the present invention;
[0110] FIG. 71F illustrates insertion loss equations, in accordance
with an embodiment of the present invention; and
[0111] FIG. 72 shows the original FSK waveform 5902 and the
down-converted waveform 5904;
[0112] The invention will now be described with reference to the
accompanying drawings. In the drawings, like reference numbers
generally indicate identical, functionally similar, and/or
structurally similar elements. The drawing in which an element
first appears is generally indicated by the left-most digit(s) in
the corresponding reference number.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENTS
TABLE-US-00001 [0113] Table of Contents 1. Overview of the
Invention 2. Universal Frequency Translation 3. Frequency
Down-conversion 3.1 Optional Energy Transfer Signal Module 3.2
Smoothing the Down-Converted Signal 3.3 Impedance Matching 3.4
Tanks and Resonant Structures 3.5 Charge and Power Transfer
Concepts 3.6 Optimizing and Adjusting the Non-Negligible Aperture
Width/Duration 3.6.1 Varying Input and Output Impedances 3.6.2 Real
Time Aperture Control 3.7 Adding a Bypass Network 3.8 Modifying the
Energy Transfer Signal Utilizing Feedback 3.9 Other Implementations
3.10 Example Energy Transfer Down-Converters 4. Frequency
Up-conversion 5. Enhanced Signal Reception 6. Unified
Down-conversion and Filtering 7. Example Application Embodiments of
the Invention 8. Universal Platform Module (UPM) 8.1 Conventional
Multi-Mode Usage Models 8.2 Universal Platform Module of the
Present Invention 8.2.1 Universal Platform Module Embodiments 8.2.2
Universal Platform Module Receiver 8.2.2.1 Universal Platform
Module Receiver Embodiments 8.2.2.1.1 Detailed UFD Module Block
Diagram 8.2.2.2 In-phase/Quadrature-phase (I/Q) Modulation Mode
Receiver Embodiments 8.2.2.3 Unified Down-convert and Filter
Receiver Embodiments 8.2.2.4 Other Receiver Embodiments 8.2.3
Universal Platform Module Transmitter Embodiments 8.2.3.1 Various
Modulation Mode Transmitter Embodiments, Including Phase Modulation
(PM) 8.2.3.1.1 Detailed UFU Module Embodiments 8.2.3.2
In-phase/Quadrature-phase (I/Q) Modulation Mode Transmitter
Embodiments 8.2.3.3 Other Transmitter Embodiments 8.2.4 Enhanced
Signal Reception Universal Platform Module Embodiments 8.2.5
Universal Platform Module Transceiver Embodiments 8.2.6 Other
Universal Platform Module Embodiments 8.3 Multi-Mode Infrastructure
8.4 Additional Multi-mode Teachings 9. Conclusion
1. OVERVIEW OF THE INVENTION
[0114] The present invention is directed to a universal platform
module (UPM) that operates for and/or within a device. Devices
include, without limitation, phones, personal digital/data
assistants (PDAs), smart appliances, personal computers (PCs),
set-top boxes, networked outlets (printers, projectors,
facsimiles), servers, gateways, other computing and/or data
processing devices, etc. The UPM may include one or more receivers,
transmitters, and/or transceivers, as well as other components such
as local oscillators, switches, amplifiers, etc. According to
embodiments of the invention, at least some of these components are
implemented using universal frequency translation (UFT) modules.
The UFT module performs frequency translation operations.
Embodiments of the present invention incorporating various
applications of the UFT module are described below. The UPM
provides new functionality, and/or optionally works alternatively
to existing components. The UPM utilizes protocols and/or bearer
services and/or combinations thereof to exchange and/or process
information with other components on any given network or networks
(or any communication medium, for that matter). Generally,
protocols, such as but not limited to Wireless Application Protocol
(WAP), Jini, Java Virtual Machine (JVM), Bluetooth, IEEE 802.11,
TCP/IP, UDP, HAVi, Salutation, Infrared (IR, IRDA), Service
Location Protocol (SLP), Universal Plug-n-Play (UPnP, Simple
Service Discovery Protocol (SSDP)), etc., provide the format for
the transfer of data. Other procedures, methods, protocols, and/or
standards may be combined with these protocols to enable and/or
support this, similar, and additional functionalities. For example,
in the case of Bluetooth, the transport standard is also
supplied.
[0115] Generally, protocols call upon bearer services (also known
as standards), such as CDMA (IS-95, IS-707), US-TDMA (IS-136),
W-CDMA, EDGE, IS-95C, SMS, GSM (900, 1800, 1900 MHz), DataTAC, iDEN
(ESMR), CDPD, dDECT, Project Angel, LMDS, MMDS, ARDIS, Mobitex,
AMPS, etc. These bearer services can be classified into generations
(Gs), several of which are shown in FIG. 42. The bearer services
are called upon to provide the communication pipeline (such as a
wired or wireless pipeline) for the device to interact with the
network. It is noted that, while the invention is sometimes
described herein for example purposes as involving wireless
communication, the invention is applicable to any communication
medium, including without limitation any wireless or wired
communication medium.
[0116] Generally, platforms are layers on which protocols and
bearer services are implemented and/or enabled. Platforms may be
implemented using hardware, software, or combinations thereof.
Conventional platforms require specialized circuitry for each type
of protocol and/or bearer service. According to the invention, a
UPM is enabled by one or more UFT modules on a layer with logic
and/or circuitry and/or software (or combinations thereof) for any
number/combination of protocols and bearer services.
[0117] In one embodiment, the UPM includes a UFT module for
connecting to/interacting with any network using any
protocol/bearer service combination. This embodiment provides the
benefit of reduced circuitry over conventional implementations.
Furthermore, the UPM can perform multi-platform operations nearly
simultaneously. Such operation by the invention is sometimes
referred to herein as "apparent simultaneous operation" or "virtual
simultaneous operation." For example, the UFT module can switch
between a wireless local area network (WLAN) and a wide area
network (WAN) and thus, communicate with components on both
networks.
[0118] In another embodiment, through the use of more than one UFT
module, multiple protocols and multiple bearer services can be
employed simultaneously. Thus, actual simultaneous multi-operation
is possible. Further, components for specific protocols and/or
bearer services are included in the UPM's control module which may
be upgraded and/or reprogrammed to provide support for additional
platforms.
[0119] Universal platform modules exhibit multiple advantages by
using UFT modules. These advantages include, but are not limited
to, lower power consumption, longer power source life, fewer parts,
lower cost, less tuning, and more effective signal transmission and
reception. The UPM of the present invention can receive and
transmit signals across a broad frequency range. The structure and
operation of embodiments of the UFT module, and various
applications of the same are described in detail in the following
sections.
2. UNIVERSAL FREQUENCY TRANSLATION
[0120] The present invention is related to frequency translation,
and applications of same. Such applications include, but are not
limited to, frequency down-conversion, frequency up-conversion,
enhanced signal reception, unified down-conversion and filtering,
and combinations and applications of same.
[0121] FIG. 1A illustrates a universal frequency translation (UFT)
module 102 according to embodiments of the invention. (The UFT
module is also sometimes called a universal frequency translator,
or a universal translator.)
[0122] As indicated by the example of FIG. 1A, some embodiments of
the UFT module 102 include three ports (nodes), designated in FIG.
1A as Port 1, Port 2, and Port 3. Other UFT embodiments include
other than three ports.
[0123] Generally, the UFT module 102 (perhaps in combination with
other components) operates to generate an output signal from an
input signal, where the frequency of the output signal differs from
the frequency of the input signal. In other words, the UFT module
102 (and perhaps other components) operates to generate the output
signal from the input signal by translating the frequency (and
perhaps other characteristics) of the input signal to the frequency
(and perhaps other characteristics) of the output signal.
[0124] An example embodiment of the UFT module 103 is generally
illustrated in FIG. 1B. Generally, the UFT module 103 includes a
switch 106 controlled by a control signal 108. The switch 106 is
said to be a controlled switch.
[0125] As noted above, some UFT embodiments include other than
three ports. For example, and without limitation, FIG. 2
illustrates an example UFT module 202. The example UFT module 202
includes a diode 204 having two ports, designated as Port 1 and
Port 2/3. This embodiment does not include a third port, as
indicated by the dotted line around the "Port 3" label.
[0126] The UFT module is a very powerful and flexible device. Its
flexibility is illustrated, in part, by the wide range of
applications in which it can be used. Its power is illustrated, in
part, by the usefulness and performance of such applications.
[0127] For example, a UFT module 115 can be used in a universal
frequency down-conversion (UFD) module 114, an example of which is
shown in FIG. 1C. In this capacity, the UFT module 115 frequency
down-converts an input signal to an output signal.
[0128] As another example, as shown in FIG. 1D, a UFT module 117
can be used in a universal frequency up-conversion (UFU) module
116. In this capacity, the UFT module 117 frequency up-converts an
input signal to an output signal.
[0129] These and other applications of the UFT module are described
below. Additional applications of the UFT module will be apparent
to persons skilled in the relevant art(s) based on the teachings
contained herein. In some applications, the UFT module is a
required component. In other applications, the UFT module is an
optional component.
3. FREQUENCY DOWN-CONVERSION
[0130] The present invention is directed to systems and methods of
universal frequency down-conversion, and applications of same.
[0131] In particular, the following discussion describes
down-converting using a Universal Frequency Translation Module. The
down-conversion of an EM signal by aliasing the EM signal at an
aliasing rate is fully described in co-pending U.S. patent
application entitled "Method and System for Down-Converting
Electromagnetic Signals," Ser. No. 09/176,022, filed Oct. 21, 1998,
issued as U.S. Pat. No. 6,061,551, the full disclosure of which is
incorporated herein by reference, as well as other cases cited
above. A relevant portion of the above mentioned patent application
is summarized below to describe down-converting an input signal to
produce a down-converted signal that exists at a lower frequency or
a baseband signal.
[0132] FIG. 20A illustrates an aliasing module 2000 for
down-conversion using a universal frequency translation (UFT)
module 2002 which down-converts an EM input signal 2004. In
particular embodiments, aliasing module 2000 includes a switch 2008
and a capacitor 2010. The electronic alignment of the circuit
components is flexible. That is, in one implementation, the switch
2008 is in series with input signal 2004 and capacitor 2010 is
shunted to ground (although it may be other than ground in
configurations such as differential mode). In a second
implementation (see FIG. 20A-1), the capacitor 2010 is in series
with the input signal 2004 and the switch 2008 is shunted to ground
(although it may be other than ground in configurations such as
differential mode). Aliasing module 2000 with UFT module 2002 can
be easily tailored to down-convert a wide variety of
electromagnetic signals using aliasing frequencies that are well
below the frequencies of the EM input signal 2004.
[0133] In one implementation, aliasing module 2000 down-converts
the input signal 2004 to an intermediate frequency (IF) signal. In
another implementation, the aliasing module 2000 down-converts the
input signal 2004 to a demodulated baseband signal. In yet another
implementation, the input signal 2004 is a frequency modulated (FM)
signal, and the aliasing module 2000 down-converts it to a non-FM
signal, such as a phase modulated (PM) signal or an amplitude
modulated (AM) signal. Each of the above implementations is
described below.
[0134] In an embodiment, the control signal 2006 includes a train
of pulses that repeat at an aliasing rate that is equal to, or less
than, twice the frequency of the input signal 2004. In this
embodiment, the control signal 2006 is referred to herein as an
aliasing signal because it is below the Nyquist rate for the
frequency of the input signal 2004. Preferably, the frequency of
control signal 2006 is much less than the input signal 2004.
[0135] A train of pulses 2018 as shown in FIG. 20D controls the
switch 2008 to alias the input signal 2004 with the control signal
2006 to generate a down-converted output signal 2012. More
specifically, in an embodiment, switch 2008 closes on a first edge
of each pulse 2020 of FIG. 20D and opens on a second edge of each
pulse. When the switch 2008 is closed, the input signal 2004 is
coupled to the capacitor 2010, and charge is transferred from the
input signal to the capacitor 2010. The charge stored during
successive pulses forms down-converted output signal 2012.
[0136] Exemplary waveforms are shown in FIGS. 20B-20F.
[0137] FIG. 20B illustrates an analog amplitude modulated (AM)
carrier signal 2014 that is an example of input signal 2004. For
illustrative purposes, in FIG. 20C, an analog AM carrier signal
portion 2016 illustrates a portion of the analog AM carrier signal
2014 on an expanded time scale. The analog AM carrier signal
portion 2016 illustrates the analog AM carrier signal 2014 from
time t.sub.0 to time t.sub.1.
[0138] FIG. 20D illustrates an exemplary aliasing signal 2018 that
is an example of control signal 2006. Aliasing signal 2018 is on
approximately the same time scale as the analog AM carrier signal
portion 2016. In the example shown in FIG. 20D, the aliasing signal
2018 includes a train of pulses 2020 having negligible apertures'
that tend towards zero (the invention is not limited to this
embodiment, as discussed below). The pulse aperture may also be
referred to as the pulse width as will be understood by those
skilled in the art(s). The pulses 2020 repeat at an aliasing rate,
or pulse repetition rate of aliasing signal 2018. The aliasing rate
is determined as described below, and further described in
co-pending U.S. patent application entitled "Method and System for
Down-converting Electromagnetic Signals," Ser. No. 09/176,022,
issued as U.S. Pat. No. 6,061,551.
[0139] As noted above, the train of pulses 2020 (i.e., control
signal 2006) control the switch 2008 to alias the analog AM carrier
signal 2016 (i.e., input signal 2004) at the aliasing rate of the
aliasing signal 2018. Specifically, in this embodiment, the switch
2008 closes on a first edge of each pulse and opens on a second
edge of each pulse. When the switch 2008 is closed, input signal
2004 is coupled to the capacitor 2010, and charge is transferred
from the input signal 2004 to the capacitor 2010. The charge
transferred during a pulse is referred to herein as an
under-sample. Exemplary under-samples 2022 form down-converted
signal portion 2024 (FIG. 20E) that corresponds to the analog AM
carrier signal portion 2016 (FIG. 20C) and the train of pulses 2020
(FIG. 20D). The charge stored during successive under-samples of AM
carrier signal 2014 form the down-converted signal 2024 (FIG. 20E)
that is an example of down-converted output signal 2012 (FIG. 20A).
In FIG. 20F, a demodulated baseband signal 2026 represents the
demodulated baseband signal 2024 after filtering on a compressed
time scale. As illustrated, down-converted signal 2026 has
substantially the same "amplitude envelope" as AM carrier signal
2014. Therefore, FIGS. 20B-20F illustrate down-conversion of AM
carrier signal 2014.
[0140] The waveforms shown in FIGS. 20B-20F are discussed herein
for illustrative purposes only, and are not limiting. Additional
exemplary time domain and frequency domain drawings, and exemplary
methods and systems of the invention relating thereto, are
disclosed in co-pending U.S. patent application entitled "Method
and System for Down-converting Electromagnetic Signals," Ser. No.
09/176,022, issued as U.S. Pat. No. 6,061,551.
[0141] The aliasing rate of control signal 2006 determines whether
the input signal 2004 is down-converted to an IF signal,
down-converted to a demodulated baseband signal, or down-converted
from an FM signal to a PM or an AM signal. Generally, relationships
between the input signal 2004, the aliasing rate of the control
signal 2006, and the down-converted output signal 2012 are
illustrated below:
(Freq. of input signal 2004)=n(Freq. of control signal
2006).+-.(Freq. of down-converted output signal 2012)
For the examples contained herein, only the "+" condition will be
discussed. The value of n represents a harmonic or sub-harmonic of
input signal 2004 (e.g., n=0.5, 1, 2, 3, . . . ).
[0142] When the aliasing rate of control signal 2006 is off-set
from the frequency of input signal 2004, or off-set from a harmonic
or sub-harmonic thereof, input signal 2004 is down-converted to an
IF signal. This is because the under-sampling pulses occur at
different phases of subsequent cycles of input signal 2004. As a
result, the under-samples form a lower frequency oscillating
pattern. If the input signal 2004 includes lower frequency changes,
such as amplitude, frequency, phase, etc., or any combination
thereof, the charge stored during associated under-samples reflects
the lower frequency changes, resulting in similar changes on the
down-converted IF signal. For example, to down-convert a 901 MHZ
input signal to a 1 MHZ IF signal, the frequency of the control
signal 2006 would be calculated as follows:
(Freq.sub.input-Freq.sub.IF)/n=Freq.sub.control
(901 MHZ-1 MHZ)/n=900/n
For n=0.5, 1, 2, 3, 4, etc., the frequency of the control signal
2006 would be substantially equal to 1.8 GHz, 900 MHZ, 450 MHZ, 300
MHZ, 225 MHZ, etc.
[0143] Exemplary time domain and frequency domain drawings,
illustrating down-conversion of analog and digital AM, PM and FM
signals to IF signals, and exemplary methods and systems thereof,
are disclosed in co-pending U.S. patent application entitled
"Method and System for Down-converting Electromagnetic Signals,"
Ser. No. 09/176,022, issued as U.S. Pat. No. 6,061,551.
[0144] Alternatively, when the aliasing rate of the control signal
2006 is substantially equal to the frequency of the input signal
2004, or substantially equal to a harmonic or sub-harmonic thereof,
input signal 2004 is directly down-converted to a demodulated
baseband signal. This is because, without modulation, the
under-sampling pulses occur at the same point of subsequent cycles
of the input signal 2004. As a result, the under-samples form a
constant output baseband signal. If the input signal 2004 includes
lower frequency changes, such as amplitude, frequency, phase, etc.,
or any combination thereof, the charge stored during associated
under-samples reflects the lower frequency changes, resulting in
similar changes on the demodulated baseband signal. For example, to
directly down-convert a 900 MHZ input signal to a demodulated
baseband signal (i.e., zero IF), the frequency of the control
signal 2006 would be calculated as follows:
(Freq.sub.input-Freq.sub.IF)/n=Freq.sub.control
(900 MHZ-0 MHZ)/n=900 MHZ/n
For n=0.5, 1, 2, 3, 4, etc., the frequency of the control signal
2006 should be substantially equal to 1.8 GHz, 900 MHZ, 450 MHZ,
300 MHZ, 225 MHZ, etc.
[0145] Exemplary time domain and frequency domain drawings,
illustrating direct down-conversion of analog and digital AM and PM
signals to demodulated baseband signals, and exemplary methods and
systems thereof, are disclosed in the co-pending U.S. patent
application entitled "Method and System for Down-converting
Electromagnetic Signals," Ser. No. 09/176,022, issued as U.S. Pat.
No. 6,061,551.
[0146] Alternatively, to down-convert an input FM signal to a
non-FM signal, a frequency within the FM bandwidth must be
down-converted to baseband (i.e., zero IF) As an example, to
down-convert a frequency shift keying (FSK) signal (a subset of FM)
to a phase shift keying (PSK) signal (a subset of PM), the
mid-point between a lower frequency F.sub.1 and an upper frequency
F.sub.2 (that is, [(F.sub.1+F.sub.2)/2]) of the FSK signal is
down-converted to zero IF. For example, to down-convert an FSK
signal having F.sub.1 equal to 899 MHZ and F.sub.2 equal to 901
MHZ, to a PSK signal, the aliasing rate of the control signal 2006
would be calculated as follows:
Frequency of the input = ( F 1 + F 2 ) / 2 = ( 899 MHZ + 901 MHZ )
/ 2 = 900 MHZ ##EQU00001##
Frequency of the down-converted signal=0 (i.e., baseband)
(Freq.sub.input-Freq.sub.IF)/n=Freq.sub.control
(900 MHZ-0 MHZ)/n=900 MHZ/n
For n=0.5, 1, 2, 3, etc., the frequency of the control signal 2006
should be substantially equal to 1.8 GHz, 900 MHZ, 450 MHZ, 300
MHZ, 225 MHZ, etc. The frequency of the down-converted PSK signal
is substantially equal to one half the difference between the lower
frequency F.sub.1 and the upper frequency F.sub.2.
[0147] As another example, to down-convert a FSK signal to an
amplitude shift keying (ASK) signal (a subset of AM), either the
lower frequency F.sub.1 or the upper frequency F.sub.2 of the FSK
signal is down-converted to zero IF. For example, to down-convert
an FSK signal having F.sub.1 equal to 900 MHZ and F.sub.2 equal to
901 MHZ, to an ASK signal, the aliasing rate of the control signal
2006 should be substantially equal to:
(900 MHZ-0MHZ)/n=900 MHZ/n, or
(901 MHZ-0 MHZ)/n=901 MHZ/n.
For the former case of 900 MHZ/n, and for n=0.5, 1, 2, 3, 4, etc.,
the frequency of the control signal 2006 should be substantially
equal to 1.8 GHz, 900 MHZ, 450 MHZ, 300 MHZ, 225 MHZ, etc. For the
latter case of 901 MHZ/n, and for n=0.5, 1, 2, 3, 4, etc., the
frequency of the control signal 2006 should be substantially equal
to 1.802 GHz, 901 MHZ, 450.5 MHZ, 300.333 MHZ, 225.25 MHZ, etc. The
frequency of the down-converted AM signal is substantially equal to
the difference between the lower frequency F.sub.1 and the upper
frequency F.sub.2 (i.e., 1 MHZ).
[0148] Exemplary time domain and frequency domain drawings,
illustrating down-conversion of FM signals to non-FM signals, and
exemplary methods and systems thereof, are disclosed in the
co-pending U.S. patent application entitled "Method and System for
Down-converting Electromagnetic Signals," Ser. No. 09/176,022,
issued as U.S. Pat. No. 6,061,551.
[0149] In an embodiment, the pulses of the control signal 2006 have
negligible apertures that tend towards zero. This makes the UFT
module 2002 a high input impedance device. This configuration is
useful for situations where minimal disturbance of the input signal
may be desired.
[0150] In another embodiment, the pulses of the control signal 2006
have non-negligible apertures that tend away from zero. This makes
the UFT module 2002 a lower input impedance device. This allows the
lower input impedance of the UFT module 2002 to be substantially
matched with a source impedance of the input signal 2004. This also
improves the energy transfer from the input signal 2004 to the
down-converted output signal 2012, and hence the efficiency and
signal to noise (s/n) ratio of UFT module 2002.
[0151] Exemplary systems and methods for generating and optimizing
the control signal 2006, and for otherwise improving energy
transfer and s/n ratio, are disclosed in the co-pending U.S. patent
application entitled "Method and System for Down-converting
Electromagnetic Signals," Ser. No. 09/176,022, issued as U.S. Pat.
No. 6,061,551.
[0152] When the pulses of the control signal 2006 have
non-negligible apertures, the aliasing module 2000 is referred to
interchangeably herein as an energy transfer module or a gated
transfer module, and the control signal 2006 is referred to as an
energy transfer signal. Exemplary systems and methods for
generating and optimizing the control signal 2006 and for otherwise
improving energy transfer and/or signal to noise ratio in an energy
transfer module are described below.
[0153] 3.1. Optional Energy Transfer Signal Module
[0154] FIG. 47 illustrates an energy transfer system 4701 that
includes an optional energy transfer signal module 4702, which can
perform any of a variety of functions or combinations of functions
including, but not limited to, generating the energy transfer
signal 4506.
[0155] In an embodiment, the optional energy transfer signal module
4702 includes an aperture generator, an example of which is
illustrated in FIG. 46C as an aperture generator 4620. The aperture
generator 4620 generates non-negligible aperture pulses 4626 from
an input signal 4624. The input signal 4624 can be any type of
periodic signal, including, but not limited to, a sinusoid, a
square wave, a saw-tooth wave, etc. Systems for generating the
input signal 4624 are described below.
[0156] The width or aperture of the pulses 4626 is determined by
delay through the branch 4622 of the aperture generator 4620.
Generally, as the desired pulse width increases, the difficulty in
meeting the requirements of the aperture generator 4620 decrease.
In other words, to generate non-negligible aperture pulses for a
given EM input frequency, the components utilized in the example
aperture generator 4620 do not require as fast reaction times as
those that are required in an under-sampling system operating with
the same EM input frequency.
[0157] The example logic and implementation shown in the aperture
generator 4620 are provided for illustrative purposes only, and are
not limiting. The actual logic employed can take many forms. The
example aperture generator 4620 includes an optional inverter 4628,
which is shown for polarity consistency with other examples
provided herein.
[0158] An example implementation of the aperture generator 4620 is
illustrated in FIG. 46D. Additional examples of aperture generation
logic are provided in FIGS. 46A and 46B. FIG. 46A illustrates a
rising edge pulse generator 4640, which generates pulses 4626 on
rising edges of the input signal 4624. FIG. 46B illustrates a
falling edge pulse generator 4650, which generates pulses 4626 on
falling edges of the input signal 4624.
[0159] In an embodiment, the input signal 4624 is generated
externally of the energy transfer signal module 4702, as
illustrated in FIG. 47. Alternatively, the input signal 4724 is
generated internally by the energy transfer signal module 4702. The
input signal 4624 can be generated by an oscillator, as illustrated
in FIG. 46E by an oscillator 4630. The oscillator 4630 can be
internal to the energy transfer signal module 4702 or external to
the energy transfer signal module 4702. The oscillator 4630 can be
external to the energy transfer system 4701. The output of the
oscillator 4630 may be any periodic waveform.
[0160] The type of down-conversion performed by the energy transfer
system 4701 depends upon the aliasing rate of the energy transfer
signal 4506, which is determined by the frequency of the pulses
4626. The frequency of the pulses 4626 is determined by the
frequency of the input signal 4624. For example, when the frequency
of the input signal 4624 is substantially equal to a harmonic or a
sub-harmonic of the EM signal 4504, the EM signal 4504 is directly
down-converted to baseband (e.g. when the EM signal is an AM signal
or a PM signal), or converted from FM to a non-FM signal. When the
frequency of the input signal 4624 is substantially equal to a
harmonic or a sub-harmonic of a difference frequency, the EM signal
4504 is down-converted to an intermediate signal.
[0161] The optional energy transfer signal module 4702 can be
implemented in hardware, software, firmware, or any combination
thereof.
[0162] 3.2 Smoothing the Down-Converted Signal
[0163] Referring back to FIG. 20A, the down-converted output signal
2012 may be smoothed by filtering as desired.
[0164] 3.3. Impedance Matching
[0165] The energy transfer module 2000 has input and output
impedances generally defined by (1) the duty cycle of the switch
module (i.e., UFT 2002), and (2) the impedance of the storage
module (e.g., capacitor 2010), at the frequencies of interest (e.g.
at the EM input, and intermediate/baseband frequencies).
[0166] Starting with an aperture width of approximately 1/2 the
period of the EM signal being down-converted as a preferred
embodiment, this aperture width (e.g. the "closed time") can be
decreased. As the aperture width is decreased, the characteristic
impedance at the input and the output of the energy transfer module
increases. Alternatively, as the aperture width increases from 1/2
the period of the EM signal being down-converted, the impedance of
the energy transfer module decreases.
[0167] One of the steps in determining the characteristic input
impedance of the energy transfer module could be to measure its
value. In an embodiment, the energy transfer module's
characteristic input impedance is 300 ohms. An impedance matching
circuit can be utilized to efficiently couple an input EM signal
that has a source impedance of, for example, 50 ohms, with the
energy transfer module's impedance of, for example, 300 ohms.
Matching these impedances can be accomplished in various manners,
including providing the necessary impedance directly or the use of
an impedance match circuit as described below.
[0168] Referring to FIG. 48, a specific embodiment using an RF
signal as an input, assuming that the impedance 4812 is a
relatively low impedance of approximately 50 Ohms, for example, and
the input impedance 4816 is approximately 300 Ohms, an initial
configuration for the input impedance match module 4806 can include
an inductor 5006 and a capacitor 5008, configured as shown in FIG.
50. The configuration of the inductor 5006 and the capacitor 5008
is a possible configuration when going from a low impedance to a
high impedance. Inductor 5006 and the capacitor 5008 constitute an
L match, the calculation of the values which is well known to those
skilled in the relevant arts.
[0169] The output characteristic impedance can be impedance matched
to take into consideration the desired output frequencies. One of
the steps in determining the characteristic output impedance of the
energy transfer module could be to measure its value. Balancing the
very low impedance of the storage module at the input EM frequency,
the storage module should have an impedance at the desired output
frequencies that is preferably greater than or equal to the load
that is intended to be driven (for example, in an embodiment,
storage module impedance at a desired 1 MHz output frequency is 2K
ohm and the desired load to be driven is 50 ohms). An additional
benefit of impedance matching is that filtering of unwanted signals
can also be accomplished with the same components.
[0170] In an embodiment, the energy transfer module's
characteristic output impedance is 2K ohms. An impedance matching
circuit can be utilized to efficiently couple the down-converted
signal with an output impedance of, for example, 2K ohms, to a load
of, for example, 50 ohms. Matching these impedances can be
accomplished in various manners, including providing the necessary
load impedance directly or the use of an impedance match circuit as
described below.
[0171] When matching from a high impedance to a low impedance, a
capacitor 5014 and an inductor 5016 can be configured as shown in
FIG. 50. The capacitor 5014 and the inductor 5016 constitute an L
match, the calculation of the component values being well known to
those skilled in the relevant arts.
[0172] The configuration of the input impedance match module 4806
and the output impedance match module 4808 are considered to be
initial starting points for impedance matching, in accordance with
the present invention. In some situations, the initial designs may
be suitable without further optimization. In other situations, the
initial designs can be optimized in accordance with other various
design criteria and considerations.
[0173] As other optional optimizing structures and/or components
are utilized, their affect on the characteristic impedance of the
energy transfer module should be taken into account in the match
along with their own original criteria.
[0174] 3.4 Tanks and Resonant Structures
[0175] Resonant tank and other resonant structures can be used to
further optimize the energy transfer characteristics of the
invention. For example, resonant structures, resonant about the
input frequency, can be used to store energy from the input signal
when the switch is open, a period during which one may conclude
that the architecture would otherwise be limited in its maximum
possible efficiency. Resonant tank and other resonant structures
can include, but are not limited to, surface acoustic wave (SAW)
filters, dielectric resonators, diplexers, capacitors, inductors,
etc.
[0176] An example embodiment is shown in FIG. 60A. Two additional
embodiments are shown in FIG. 55 and FIG. 63. Alternate
implementations will be apparent to persons skilled in the relevant
art(s) based on the teachings contained herein. Alternate
implementations fall within the scope and spirit of the present
invention. These implementations take advantage of properties of
series and parallel (tank) resonant circuits.
[0177] FIG. 60A illustrates parallel tank circuits in a
differential implementation. A first parallel resonant or tank
circuit consists of a capacitor 6038 and an inductor 6020 (tank1).
A second tank circuit consists of a capacitor 6034 and an inductor
6036 (tank2).
[0178] As is apparent to one skilled in the relevant art(s),
parallel tank circuits provide: [0179] low impedance to frequencies
below resonance; [0180] low impedance to frequencies above
resonance; and [0181] high impedance to frequencies at and near
resonance.
[0182] In the illustrated example of FIG. 60A, the first and second
tank circuits resonate at approximately 920 MHz. At and near
resonance, the impedance of these circuits is relatively high.
Therefore, in the circuit configuration shown in FIG. 60A, both
tank circuits appear as relatively high impedance to the input
frequency of 950 MHz, while simultaneously appearing as relatively
low impedance to frequencies in the desired output range of 50
MHz.
[0183] An energy transfer signal 6042 controls a switch 6014. When
the energy transfer signal 6042 controls the switch 6014 to open
and close, high frequency signal components are not allowed to pass
through tank1 or tank2. However, the lower signal components (50
Mhz in this embodiment) generated by the system are allowed to pass
through tank1 and tank2 with little attenuation. The effect of
tank1 and tank2 is to further separate the input and output signals
from the same node thereby producing a more stable input and output
impedance. Capacitors 6018 and 6040 act to store the 50 MHz output
signal energy between energy transfer pulses.
[0184] Further energy transfer optimization is provided by placing
an inductor 6010 in series with a storage capacitor 6012 as shown.
In the illustrated example, the series resonant frequency of this
circuit arrangement is approximately 1 GHz. This circuit increases
the energy transfer characteristic of the system. The ratio of the
impedance of inductor 6010 and the impedance of the storage
capacitor 6012 is preferably kept relatively small so that the
majority of the energy available will be transferred to storage
capacitor 6012 during operation. Exemplary output signals A and B
are illustrated in FIGS. 60B and 60C, respectively.
[0185] In FIG. 60A, circuit components 6004 and 6006 form an input
impedance match. Circuit components 6032 and 6030 form an output
impedance match into a 50 ohm resistor 6028. Circuit components
6022 and 6024 form a second output impedance match into a 50 ohm
resistor 6026. Capacitors 6008 and 6012 act as storage capacitors
for the embodiment. Voltage source 6046 and resistor 6002 generate
a 950 MHz signal with a 50 ohm output impedance, which are used as
the input to the circuit. Circuit element 6016 includes a 150 MHz
oscillator and a pulse generator, which are used to generate the
energy transfer signal 6042.
[0186] FIG. 55 illustrates a shunt tank circuit 5510 in a
single-ended to-single-ended system 5512. Similarly, FIG. 63
illustrates a shunt tank circuit 6310 in a system 6312. The tank
circuits 5510 and 6310 lower driving source impedance, which
improves transient response. The tank circuits 5510 and 6310 are
able store the energy from the input signal and provide a low
driving source impedance to transfer that energy throughout the
aperture of the closed switch. The transient nature of the switch
aperture can be viewed as having a response that, in addition to
including the input frequency, has large component frequencies
above the input frequency, (i.e. higher frequencies than the input
frequency are also able to effectively pass through the aperture).
Resonant circuits or structures, for example resonant tanks 5510 or
6310, can take advantage of this by being able to transfer energy
throughout the switch's transient frequency response (i.e. the
capacitor in the resonant tank appears as a low driving source
impedance during the transient period of the aperture).
[0187] The example tank and resonant structures described above are
for illustrative purposes and are not limiting. Alternate
configurations can be utilized. The various resonant tanks and
structures discussed can be combined or utilized independently as
is now apparent.
[0188] 3.5 Charge and Power Transfer Concepts
[0189] Concepts of charge transfer are now described with reference
to FIGS. 71A-F. FIG. 71A illustrates a circuit 7102, including a
switch S and a capacitor 7106 having a capacitance C. The switch S
is controlled by a control signal 7108, which includes pulses 19010
having apertures T.
[0190] In FIG. 71B, Equation 10 illustrates that the charge q on a
capacitor having a capacitance C, such as the capacitor 7106, is
proportional to the voltage V across the capacitor, where: [0191]
q=Charge in Coulombs [0192] C=Capacitance in Farads [0193]
V=Voltage in Volts [0194] A=Input Signal Amplitude
[0195] Where the voltage V is represented by Equation 11, Equation
10 can be rewritten as Equation 12. The change in charge .DELTA.q
over time t is illustrated as in Equation 13 as .DELTA.q(t), which
can be rewritten as Equation 14. Using the sum-to-product
trigonometric identity of Equation 15, Equation 14 can be rewritten
as Equation 16, which can be rewritten as equation 17.
[0196] Note that the sin term in Equation 11 is a function of the
aperture T only. Thus, .DELTA.q(t) is at a maximum when T is equal
to an odd multiple of .pi. (i.e., .pi., 3.pi., 5.pi., . . . ).
Therefore, the capacitor 7106 experiences the greatest change in
charge when the aperture T has a value of it or a time interval
representative of 180 degrees of the input sinusoid. Conversely,
when T is equal to 2.pi., 4.pi., 6.pi., . . . , minimal charge is
transferred.
[0197] Equations 18, 19, and 20 solve for q(t) by integrating
Equation 10, allowing the charge on the capacitor 7106 with respect
to time to be graphed on the same axis as the input sinusoid
sin(t), as illustrated in the graph of FIG. 71C. As the aperture T
decreases in value or tends toward an impulse, the phase between
the charge on the capacitor C or q(t) and sin(t) tend toward zero.
This is illustrated in the graph of FIG. 71D, which indicates that
the maximum impulse charge transfer occurs near the input voltage
maxima. As this graph indicates, considerably less charge is
transferred as the value of T decreases.
[0198] Power/charge relationships are illustrated in Equations
21-26 of FIG. 71E, where it is shown that power is proportional to
charge, and transferred charge is inversely proportional to
insertion loss.
[0199] Concepts of insertion loss are illustrated in FIG. 71F.
Generally, the noise figure of a lossy passive device is
numerically equal to the device insertion loss. Alternatively, the
noise figure for any device cannot be less that its insertion loss.
Insertion loss can be expressed by Equation 27 or 28. From the
above discussion, it is observed that as the aperture T increases,
more charge is transferred from the input to the capacitor 7106,
which increases power transfer from the input to the output. It has
been observed that it is not necessary to accurately reproduce the
input voltage at the output because relative modulated amplitude
and phase information is retained in the transferred power.
[0200] 3.6 Optimizing and Adjusting the Non-Negligible Aperture
Width/Duration
[0201] 3.6.1 Varying Input and Output Impedances
[0202] In an embodiment of the invention, the energy transfer
signal (i.e., control signal 2006 in FIG. 20A), is used to vary the
input impedance seen by the EM Signal 2004 and to vary the output
impedance driving a load. An example of this embodiment is
described below using a gated transfer module 5101 shown in FIG.
51A. The method described below is not limited to the gated
transfer module 5101.
[0203] In FIG. 51A, when switch 5106 is closed, the impedance
looking into circuit 5102 is substantially the impedance of a
storage module, illustrated here as a storage capacitance 5108, in
parallel with the impedance of a load 5112. When the switch 5106 is
open, the impedance at point 5114 approaches infinity. It follows
that the average impedance at point 5114 can be varied from the
impedance of the storage module illustrated in parallel with the
load 5112, to the highest obtainable impedance when switch 5106 is
open, by varying the ratio of the time that switch 5106 is open to
the time switch 5106 is closed. The switch 5106 is controlled by an
energy transfer signal 5110. Thus the impedance at point 5114 can
be varied by controlling the aperture width of the energy transfer
signal in conjunction with the aliasing rate.
[0204] An example method of altering the energy transfer signal
5106 of FIG. 51A is now described with reference to FIG. 49A, where
a circuit 4902 receives an input oscillating signal 4906 and
outputs a pulse train shown as doubler output signal 4904. The
circuit 4902 can be used to generate the energy transfer signal
5106. Example waveforms of 4904 are shown on FIG. 49C.
[0205] It can be shown that by varying the delay of the signal
propagated by the inverter 4908, the width of the pulses in the
doubler output signal 4904 can be varied. Increasing the delay of
the signal propagated by inverter 4908, increases the width of the
pulses. The signal propagated by inverter 4908 can be delayed by
introducing a R/C low pass network in the output of inverter 4908.
Other means of altering the delay of the signal propagated by
inverter 4908 will be well known to those skilled in the art.
[0206] 3.6.2 Real Time Aperture Control
[0207] In an embodiment, the aperture width/duration is adjusted in
real time. For example, referring to the timing diagrams in FIGS.
64B-F, a clock signal 6414 (FIG. 64B) is utilized to generate an
energy transfer signal 6416 (FIG. 64F), which includes energy
transfer pluses 6418, having variable apertures 6420. In an
embodiment, the clock signal 6414 is inverted as illustrated by
inverted clock signal 6422 (FIG. 64D). The clock signal 6414 is
also delayed, as illustrated by delayed clock signal 6424 (FIG.
64E). The inverted clock signal 6414 and the delayed clock signal
6424 are then ANDed together, generating an energy transfer signal
6416, which is active--energy transfer pulses 6418--when the
delayed clock signal 6424 and the inverted clock signal 6422 are
both active. The amount of delay imparted to the delayed clock
signal 6424 substantially determines the width or duration of the
apertures 6420. By varying the delay in real time, the apertures
are adjusted in real time.
[0208] In an alternative implementation, the inverted clock signal
6422 is delayed relative to the original clock signal 6414, and
then ANDed with the original clock signal 6414. Alternatively, the
original clock signal 6414 is delayed then inverted, and the result
ANDed with the original clock signal 6414.
[0209] FIG. 64A illustrates an exemplary real time aperture control
system 6402 that can be utilized to adjust apertures in real time.
The example real time aperture control system 6402 includes an RC
circuit 6404, which includes a voltage variable capacitor 6412 and
a resistor 6426. The real time aperture control system 6402 also
includes an inverter 6406 and an AND gate 6408. The AND gate 6408
optionally includes an enable input 6410 for enabling/disabling the
AND gate 6408. The RC circuit 6404. The real time aperture control
system 6402 optionally includes an amplifier 6428.
[0210] Operation of the real time aperture control circuit is
described with reference to the timing diagrams of FIGS. 64B-F. The
real time control system 6402 receives the input clock signal 6414,
which is provided to both the inverter 6406 and to the RC circuit
6404. The inverter 6406 outputs the inverted clock signal 6422 and
presents it to the AND gate 6408. The RC circuit 6404 delays the
clock signal 6414 and outputs the delayed clock signal 6424. The
delay is determined primarily by the capacitance of the voltage
variable capacitor 6412. Generally, as the capacitance decreases,
the delay decreases.
[0211] The delayed clock signal 6424 is optionally amplified by the
optional amplifier 6428, before being presented to the AND gate
6408. Amplification is desired, for example, where the RC constant
of the RC circuit 6404 attenuates the signal below the threshold of
the AND gate 6408.
[0212] The AND gate 6408 ANDs the delayed clock signal 6424, the
inverted clock signal 6422, and the optional Enable signal 6410, to
generate the energy transfer signal 6416. The apertures 6420 are
adjusted in real time by varying the voltage to the voltage
variable capacitor 6412.
[0213] In an embodiment, the apertures 6420 are controlled to
optimize power transfer. For example, in an embodiment, the
apertures 6420 are controlled to maximize power transfer.
Alternatively, the apertures 6420 are controlled for variable gain
control (e.g. automatic gain control--AGC). In this embodiment,
power transfer is reduced by reducing the apertures 6420.
[0214] As can now be readily seen from this disclosure, many of the
aperture circuits presented, and others, can be modified as in
circuits illustrated in FIGS. 46 H-K. Modification or selection of
the aperture can be done at the design level to remain a fixed
value in the circuit, or in an alternative embodiment, may be
dynamically adjusted to compensate for, or address, various design
goals such as receiving RF signals with enhanced efficiency that
are in distinctively different bands of operation, e.g. RF signals
at 900 MHZ and 1.8 GHz.
[0215] 3.7 Adding a Bypass Network
[0216] In an embodiment of the invention, a bypass network is added
to improve the efficiency of the energy transfer module. Such a
bypass network can be viewed as a means of synthetic aperture
widening. Components for a bypass network are selected so that the
bypass network appears substantially lower impedance to transients
of the switch module (i.e., frequencies greater than the received
EM signal) and appears as a moderate to high impedance to the input
EM signal (e.g., greater that 100 Ohms at the RF frequency).
[0217] The time that the input signal is now connected to the
opposite side of the switch module is lengthened due to the shaping
caused by this network, which in simple realizations may be a
capacitor or series resonant inductor-capacitor. A network that is
series resonant above the input frequency would be a typical
implementation. This shaping improves the conversion efficiency of
an input signal that would otherwise, if one considered the
aperture of the energy transfer signal only, be relatively low in
frequency to be optimal.
[0218] For example, referring to FIG. 61 a bypass network 6102
(shown in this instance as capacitor 6112), is shown bypassing
switch module 6104. In this embodiment the bypass network increases
the efficiency of the energy transfer module when, for example,
less than optimal aperture widths were chosen for a given input
frequency on the energy transfer signal 6106. The bypass network
6102 could be of different configurations than shown in FIG. 61.
Such an alternate is illustrated in FIG. 57. Similarly, FIG. 62
illustrates another example bypass network 6202, including a
capacitor 6204.
[0219] The following discussion will demonstrate the effects of a
minimized aperture and the benefit provided by a bypassing network.
Beginning with an initial circuit having a 550 ps aperture in FIG.
65, its output is seen to be 2.8 mVpp applied to a 50 ohm load in
FIG. 69A. Changing the aperture to 270 ps as shown in FIG. 66
results in a diminished output of 2.5 Vpp applied to a 50 ohm load
as shown in FIG. 69B. To compensate for this loss, a bypass network
may be added, a specific implementation is provided in FIG. 67. The
result of this addition is that 3.2 Vpp can now be applied to the
50 ohm load as shown in FIG. 70A. The circuit with the bypass
network in FIG. 67 also had three values adjusted in the
surrounding circuit to compensate for the impedance changes
introduced by the bypass network and narrowed aperture. FIG. 68
verifies that those changes added to the circuit, but without the
bypass network, did not themselves bring about the increased
efficiency demonstrated by the embodiment in FIG. 67 with the
bypass network. FIG. 70B shows the result of using the circuit in
FIG. 68 in which only 1.88 Vpp was able to be applied to a 50 ohm
load.
[0220] 3.8 Modifying the Energy Transfer Signal Utilizing
Feedback
[0221] FIG. 47 shows an embodiment of a system 4701 which uses
down-converted Signal 4708B as feedback 4706 to control various
characteristics of the energy transfer module 4704 to modify the
down-converted signal 4708B.
[0222] Generally, the amplitude of the down-converted signal 4708B
varies as a function of the frequency and phase differences between
the EM signal 4504 and the energy transfer signal 4506. In an
embodiment, the down-converted signal 4708B is used as the feedback
4706 to control the frequency and phase relationship between the EM
signal 4504 and the energy transfer signal 4506. This can be
accomplished using the example logic in FIG. 52A. The example
circuit in FIG. 52A can be included in the energy transfer signal
module 4702. Alternate implementations will be apparent to persons
skilled in the relevant art(s) based on the teachings contained
herein. Alternate implementations fall within the scope and spirit
of the present invention. In this embodiment a state-machine is
used as an example.
[0223] In the example of FIG. 52A, a state machine 5204 reads an
analog to digital converter, A/D 5202, and controls a digital to
analog converter, DAC 5206. In an embodiment, the state machine
5204 includes 2 memory locations, Previous and Current, to store
and recall the results of reading A/D 5202. In an embodiment, the
state machine 5204 utilizes at least one memory flag.
[0224] The DAC 5206 controls an input to a voltage controlled
oscillator, VCO 5208. VCO 5208 controls a frequency input of a
pulse generator 5210, which, in an embodiment, is substantially
similar to the pulse generator shown in FIG. 46C. The pulse
generator 5210 generates energy transfer signal 4506.
[0225] In an embodiment, the state machine 5204 operates in
accordance with a state machine flowchart 5219 in FIG. 52B. The
result of this operation is to modify the frequency and phase
relationship between the energy transfer signal 4506 and the EM
signal 4504, to substantially maintain the amplitude of the
down-converted signal 4708B at an optimum level.
[0226] The amplitude of the down-converted signal 4708B can be made
to vary with the amplitude of the energy transfer signal 4506. In
an embodiment where the switch module 6502 is a FET as shown in
FIG. 45A, wherein the gate 4518 receives the energy transfer signal
4506, the amplitude of the energy transfer signal 4506 can
determine the "on" resistance of the FET, which affects the
amplitude of the down-converted signal 4708B. The energy transfer
signal module 4702, as shown in FIG. 52C, can be an analog circuit
that enables an automatic gain control function. Alternate
implementations will be apparent to persons skilled in the relevant
art(s) based on the teachings contained herein. Alternate
implementations fall within the scope and spirit of the present
invention.
[0227] 3.9 Other Implementations
[0228] The implementations described above are provided for
purposes of illustration. These implementations are not intended to
limit the invention. Alternate implementations, differing slightly
or substantially from those described herein, will be apparent to
persons skilled in the relevant art(s) based on the teachings
contained herein. Such alternate implementations fall within the
scope and spirit of the present invention.
[0229] 3.10 Example Energy Transfer Down-Converters
[0230] Example implementations are described below for illustrative
purposes. The invention is not limited to these examples.
[0231] FIG. 53 is a schematic diagram of an exemplary circuit to
down convert a 915 MHZ signal to a 5 MHZ signal using a 101.1 MHZ
clock.
[0232] FIG. 54 shows example simulation waveforms for the circuit
of FIG. 53. Waveform 5302 is the input to the circuit showing the
distortions caused by the switch closure. Waveform 5304 is the
unfiltered output at the storage unit. Waveform 5306 is the
impedance matched output of the down-converter on a different time
scale.
[0233] FIG. 55 is a schematic diagram of an exemplary circuit to
down-convert a 915 MHZ signal to a 5 MHZ signal using a 101.1 MHZ
clock. The circuit has additional tank circuitry to improve
conversion efficiency.
[0234] FIG. 56 shows example simulation waveforms for the circuit
of FIG. 55. Waveform 5502 is the input to the circuit showing the
distortions caused by the switch closure. Waveform 5504 is the
unfiltered output at the storage unit. Waveform 5506 is the output
of the down-converter after the impedance match circuit.
[0235] FIG. 57 is a schematic diagram of an exemplary circuit to
down-convert a 915 MHZ signal to a 5 MHZ signal using a 101.1 MHZ
clock. The circuit has switch bypass circuitry to improve
conversion efficiency.
[0236] FIG. 58 shows example simulation waveforms for the circuit
of FIG. 57. Waveform 5702 is the input to the circuit showing the
distortions caused by the switch closure. Waveform 5704 is the
unfiltered output at the storage unit. Waveform 5706 is the output
of the down-converter after the impedance match circuit.
[0237] FIG. 59 shows a schematic of the example circuit in FIG. 53
connected to an FSK source that alternates between 913 and 917 MHZ,
at a baud rate of 500 Kbaud. FIG. 72 shows the original FSK
waveform 5902 and the down-converted waveform 5904 at the output of
the load impedance match circuit.
4. FREQUENCY UP-CONVERSION
[0238] The present invention is directed to systems and methods of
frequency up-conversion, and applications of same.
[0239] An example frequency up-conversion system 300 is illustrated
in FIG. 3. The frequency up-conversion system 300 is now
described.
[0240] An input signal 302 (designated as "Control Signal" in FIG.
3) is accepted by a switch module 304. For purposes of example
only, assume that the input signal 302 is a FM input signal 606, an
example of which is shown in FIG. 6C. FM input signal 606 may have
been generated by modulating information signal 602 onto
oscillating signal 604 (FIGS. 6A and 6B). It should be understood
that the invention is not limited to this embodiment. The
information signal 602 can be analog, digital, or any combination
thereof, and any modulation scheme can be used.
[0241] The output of switch module 304 is a harmonically rich
signal 306, shown for example in FIG. 6D as a harmonically rich
signal 608. The harmonically rich signal 608 has a continuous and
periodic waveform.
[0242] FIG. 6E is an expanded view of two sections of harmonically
rich signal 608, section 610 and section 612. The harmonically rich
signal 608 may be a rectangular wave, such as a square wave or a
pulse (although, the invention is not limited to this embodiment).
For ease of discussion, the term "rectangular waveform" is used to
refer to waveforms that are substantially rectangular. In a similar
manner, the term "square wave" refers to those waveforms that are
substantially square and it is not the intent of the present
invention that a perfect square wave be generated or needed.
[0243] Harmonically rich signal 608 is comprised of a plurality of
sinusoidal waves whose frequencies are integer multiples of the
fundamental frequency of the waveform of the harmonically rich
signal 608. These sinusoidal waves are referred to as the harmonics
of the underlying waveform, and the fundamental frequency is
referred to as the first harmonic. FIG. 6F and FIG. 6G show
separately the sinusoidal components making up the first, third,
and fifth harmonics of section 610 and section 612. (Note that in
theory there may be an infinite number of harmonics; in this
example, because harmonically rich signal 608 is shown as a square
wave, there are only odd harmonics). Three harmonics are shown
simultaneously (but not summed) in FIG. 6H.
[0244] The relative amplitudes of the harmonics are generally a
function of the relative widths of the pulses of harmonically rich
signal 306 and the period of the fundamental frequency, and can be
determined by doing a Fourier analysis of harmonically rich signal
306. According to an embodiment of the invention, the input signal
606 may be shaped to ensure that the amplitude of the desired
harmonic is sufficient for its intended use (e.g.,
transmission).
[0245] A filter 308 filters out any undesired frequencies
(harmonics), and outputs an electromagnetic (EM) signal at the
desired harmonic frequency or frequencies as an output signal 310,
shown for example as a filtered output signal 614 in FIG. 6I.
[0246] FIG. 4 illustrates an example universal frequency
up-conversion (UFU) module 401. The UFU module 401 includes an
example switch module 304, which comprises a bias signal 402, a
resistor or impedance 404, a universal frequency translator (UFT)
450, and a ground 408. The UFT 450 includes a switch 406. The input
signal 302 (designated as "Control Signal" in FIG. 4) controls the
switch 406 in the UFT 450, and causes it to close and open.
Harmonically rich signal 306 is generated at a node 405 located
between the resistor or impedance 404 and the switch 406.
[0247] Also in FIG. 4, it can be seen that an example filter 308 is
comprised of a capacitor 410 and an inductor 412 shunted to a
ground 414. The filter is designed to filter out the undesired
harmonics of harmonically rich signal 306.
[0248] The invention is not limited to the UFU embodiment shown in
FIG. 4.
[0249] For example, in an alternate embodiment shown in FIG. 5, an
unshaped input signal 501 is routed to a pulse shaping module 502.
The pulse shaping module 502 modifies the unshaped input signal 501
to generate a (modified) input signal 302 (designated as the
"Control Signal" in FIG. 5). The input signal 302 is routed to the
switch module 304, which operates in the manner described above.
Also, the filter 308 of FIG. 5 operates in the manner described
above.
[0250] The purpose of the pulse shaping module 502 is to define the
pulse width of the input signal 302. Recall that the input signal
302 controls the opening and closing of the switch 406 in switch
module 304. During such operation, the pulse width of the input
signal 302 establishes the pulse width of the harmonically rich
signal 306. As stated above, the relative amplitudes of the
harmonics of the harmonically rich signal 306 are a function of at
least the pulse width of the harmonically rich signal 306. As such,
the pulse width of the input signal 302 contributes to setting the
relative amplitudes of the harmonics of harmonically rich signal
306.
[0251] Further details of up-conversion as described in this
section are presented in pending U.S. application "Method and
System for Frequency Up-Conversion," Ser. No. 09/176,154, filed
Oct. 21, 1998, incorporated herein by reference in its
entirety.
5. ENHANCED SIGNAL RECEPTION
[0252] The present invention is directed to systems and methods of
enhanced signal reception (ESR), and applications of same.
[0253] Referring to FIG. 21, transmitter 2104 accepts a modulating
baseband signal 2102 and generates (transmitted) redundant
spectrums 2106a-n, which are sent over communications medium 2108.
Receiver 2112 recovers a demodulated baseband signal 2114 from
(received) redundant spectrums 2110a-n. Demodulated baseband signal
2114 is representative of the modulating baseband signal 2102,
where the level of similarity between the modulating baseband
signal 2114 and the modulating baseband signal 2102 is application
dependent.
[0254] Modulating baseband signal 2102 is preferably any
information signal desired for transmission and/or reception. An
example modulating baseband signal 2202 is illustrated in FIG. 22A,
and has an associated modulating baseband spectrum 2204 and image
spectrum 2203 that are illustrated in FIG. 22B. Modulating baseband
signal 2202 is illustrated as an analog signal in FIG. 22a, but
could also be a digital signal, or combination thereof. Modulating
baseband signal 2202 could be a voltage (or current)
characterization of any number of real world occurrences, including
for example and without limitation, the voltage (or current)
representation for a voice signal.
[0255] Each transmitted redundant spectrum 2106a-n contains the
necessary information to substantially reconstruct the modulating
baseband signal 2102. In other words, each redundant spectrum
2106a-n contains the necessary amplitude, phase, and frequency
information to reconstruct the modulating baseband signal 2102.
[0256] FIG. 22C illustrates example transmitted redundant spectrums
2206b-d. Transmitted redundant spectrums 2206b-d are illustrated to
contain three redundant spectrums for illustration purposes only.
Any number of redundant spectrums could be generated and
transmitted as will be explained in following discussions.
[0257] Transmitted redundant spectrums 2206b-d are centered at
f.sub.1, with a frequency spacing f.sub.2 between adjacent
spectrums. Frequencies f.sub.1 and f.sub.2 are dynamically
adjustable in real-time as will be shown below. FIG. 22D
illustrates an alternate embodiment, where redundant spectrums
2208c,d are centered on unmodulated oscillating signal 2209 at
f.sub.1 (Hz). Oscillating signal 2209 may be suppressed if desired
using, for example, phasing techniques or filtering techniques.
Transmitted redundant spectrums are preferably above baseband
frequencies as is represented by break 2205 in the frequency axis
of FIGS. 22C and 22D.
[0258] Received redundant spectrums 2110a-n are substantially
similar to transmitted redundant spectrums 2106a-n, except for the
changes introduced by the communications medium 2108. Such changes
can include but are not limited to signal attenuation, and signal
interference. FIG. 22E illustrates example received redundant
spectrums 2210b-d. Received redundant spectrums 2210b-d are
substantially similar to transmitted redundant spectrums 2206b-d,
except that redundant spectrum 2210c includes an undesired jamming
signal spectrum 2211 in order to illustrate some advantages of the
present invention. Jamming signal spectrum 2211 is a frequency
spectrum associated with a jamming signal. For purposes of this
invention, a "jamming signal" refers to any unwanted signal,
regardless of origin, that may interfere with the proper reception
and reconstruction of an intended signal. Furthermore, the jamming
signal is not limited to tones as depicted by spectrum 2211, and
can have any spectral shape, as will be understood by those skilled
in the art(s).
[0259] As stated above, demodulated baseband signal 2114 is
extracted from one or more of received redundant spectrums 2210b-d.
FIG. 22F illustrates example demodulated baseband signal 2212 that
is, in this example, substantially similar to modulating baseband
signal 2202 (FIG. 22A); where in practice, the degree of similarity
is application dependent.
[0260] An advantage of the present invention should now be
apparent. The recovery of modulating baseband signal 2202 can be
accomplished by receiver 2112 in spite of the fact that high
strength jamming signal(s) (e.g. jamming signal spectrum 2211)
exist on the communications medium. The intended baseband signal
can be recovered because multiple redundant spectrums are
transmitted, where each redundant spectrum carries the necessary
information to reconstruct the baseband signal. At the destination,
the redundant spectrums are isolated from each other so that the
baseband signal can be recovered even if one or more of the
redundant spectrums are corrupted by a jamming signal.
[0261] Transmitter 2104 will now be explored in greater detail.
FIG. 23A illustrates transmitter 2301, which is one embodiment of
transmitter 2104 that generates redundant spectrums configured
similar to redundant spectrums 2206b-d. Transmitter 2301 includes
generator 2303, optional spectrum processing module 2304, and
optional medium interface module 2320. Generator 2303 includes:
first oscillator 2302, second oscillator 2309, first stage
modulator 2306, and second stage modulator 2310.
[0262] Transmitter 2301 operates as follows. First oscillator 2302
and second oscillator 2309 generate a first oscillating signal 2305
and second oscillating signal 2312, respectively. First stage
modulator 2306 modulates first oscillating signal 2305 with
modulating baseband signal 2202, resulting in modulated signal
2308. First stage modulator 2306 may implement any type of
modulation including but not limited to: amplitude modulation,
frequency modulation, phase modulation, combinations thereof, or
any other type of modulation. Second stage modulator 2310 modulates
modulated signal 2308 with second oscillating signal 2312,
resulting in multiple redundant spectrums 2206a-n shown in FIG.
23B. Second stage modulator 2310 is preferably a phase modulator,
or a frequency modulator, although other types of modulation may be
implemented including but not limited to amplitude modulation. Each
redundant spectrum 2206a-n contains the necessary amplitude, phase,
and frequency information to substantially reconstruct the
modulating baseband signal 2202.
[0263] Redundant spectrums 2206a-n are substantially centered
around f.sub.1, which is the characteristic frequency of first
oscillating signal 2305. Also, each redundant spectrum 2206a-n
(except for 2206c) is offset from f.sub.1 by approximately a
multiple of f.sub.2 (Hz), where f.sub.2 is the frequency of the
second oscillating signal 2312. Thus, each redundant spectrum
2206a-n is offset from an adjacent redundant spectrum by f.sub.7
(Hz). This allows the spacing between adjacent redundant spectrums
to be adjusted (or tuned) by changing f.sub.2 that is associated
with second oscillator 2309. Adjusting the spacing between adjacent
redundant spectrums allows for dynamic real-time tuning of the
bandwidth occupied by redundant spectrums 2206a-n.
[0264] In one embodiment, the number of redundant spectrums 2206a-n
generated by transmitter 2301 is arbitrary and may be unlimited as
indicated by the "a-n" designation for redundant spectrums 2206a-n.
However, a typical communications medium will have a physical
and/or administrative limitations (i.e. FCC regulations) that
restrict the number of redundant spectrums that can be practically
transmitted over the communications medium. Also, there may be
other reasons to limit the number of redundant spectrums
transmitted. Therefore, preferably, the transmitter 2301 will
include an optional spectrum processing module 2304 to process the
redundant spectrums 2206a-n prior to transmission over
communications medium 2108.
[0265] In one embodiment, spectrum processing module 2304 includes
a filter with a passband 2207 (FIG. 23C) to select redundant
spectrums 2206b-d for transmission. This will substantially limit
the frequency bandwidth occupied by the redundant spectrums to the
passband 2207. In one embodiment, spectrum processing module 2304
also up converts redundant spectrums and/or amplifies redundant
spectrums prior to transmission over the communications medium
2108. Finally, medium interface module 2320 transmits redundant
spectrums over the communications medium 2108. In one embodiment,
communications medium 2108 is an over-the-air link and medium
interface module 2320 is an antenna. Other embodiments for
communications medium 2108 and medium interface module 2320 will be
understood based on the teachings contained herein.
[0266] FIG. 23D illustrates transmitter 2321, which is one
embodiment of transmitter 2104 that generates redundant spectrums
configured similar to redundant spectrums 2208c-d and unmodulated
spectrum 2209. Transmitter 2321 includes generator 2311, spectrum
processing module 2304, and (optional) medium interface module
2320. Generator 2311 includes: first oscillator 2302, second
oscillator 2309, first stage modulator 2306, and second stage
modulator 2310.
[0267] As shown in FIG. 23D, many of the components in transmitter
2321 are similar to those in transmitter 2301. However, in this
embodiment, modulating baseband signal 2202 modulates second
oscillating signal 2312. Transmitter 2321 operates as follows.
First stage modulator 2306 modulates second oscillating signal 2312
with modulating baseband signal 2202, resulting in modulated signal
2322. As described earlier, first stage modulator 2306 can effect
any type of modulation including but not limited to: amplitude
modulation frequency modulation, combinations thereof, or any other
type of modulation. Second stage modulator 2310 modulates first
oscillating signal 2304 with modulated signal 2322, resulting in
redundant spectrums 2208a-n, as shown in FIG. 23E. Second stage
modulator 2310 is preferably a phase or frequency modulator,
although other modulators could used including but not limited to
an amplitude modulator.
[0268] Redundant spectrums 2208a-n are centered on unmodulated
spectrum 2209 (at f.sub.1 Hz), and adjacent spectrums are separated
by f.sub.2 Hz. The number of redundant spectrums 2208a-n generated
by generator 2311 is arbitrary and unlimited, similar to spectrums
2206a-n discussed above. Therefore, optional spectrum processing
module 2304 may also include a filter with passband 2325 to select,
for example, spectrums 2208c,d for transmission over communications
medium 2108. In addition, optional spectrum processing module 2304
may also include a filter (such as a bandstop filter) to attenuate
unmodulated spectrum 2209. Alternatively, unmodulated spectrum 2209
may be attenuated by using phasing techniques during redundant
spectrum generation. Finally, (optional) medium interface module
2320 transmits redundant spectrums 2208c,d over communications
medium 2108.
[0269] Receiver 2112 will now be explored in greater detail to
illustrate recovery of a demodulated baseband signal from received
redundant spectrums. FIG. 24A illustrates receiver 2430, which is
one embodiment of receiver 2112. Receiver 2430 includes optional
medium interface module 2402, down-converter 2404, spectrum
isolation module 2408, and data extraction module 2414. Spectrum
isolation module 2408 includes filters 2410a-c. Data extraction
module 2414 includes demodulators 2416a-c, error check modules
2420a-c, and arbitration module 2424. Receiver 2430 will be
discussed in relation to the signal diagrams in FIGS. 24B-24J.
[0270] In one embodiment, optional medium interface module 2402
receives redundant spectrums 2210b-d (FIG. 22E, and FIG. 24B). Each
redundant spectrum 2210b-d includes the necessary amplitude, phase,
and frequency information to substantially reconstruct the
modulating baseband signal used to generated the redundant
spectrums. However, in the present example, spectrum 2210c also
contains jamming signal 2211, which may interfere with the recovery
of a baseband signal from spectrum 2210c. Down-converter 2404
down-converts received redundant spectrums 2210b-d to lower
intermediate frequencies, resulting in redundant spectrums 2406a-c
(FIG. 24C). Jamming signal 2211 is also down-converted to jamming
signal 2407, as it is contained within redundant spectrum 2406b.
Spectrum isolation module 2408 includes filters 2410a-c that
isolate redundant spectrums 2406a-c from each other (FIGS. 24D-24F,
respectively). Demodulators 2416a-c independently demodulate
spectrums 2406a-c, resulting in demodulated baseband signals
2418a-c, respectively (FIGS. 24G-24I). Error check modules 2420a-c
analyze demodulate baseband signal 2418a-c to detect any errors. In
one embodiment, each error check module 2420a-c sets an error flag
2422a-c whenever an error is detected in a demodulated baseband
signal. Arbitration module 2424 accepts the demodulated baseband
signals and associated error flags, and selects a substantially
error-free demodulated baseband signal (FIG. 24J). In one
embodiment, the substantially error-free demodulated baseband
signal will be substantially similar to the modulating baseband
signal used to generate the received redundant spectrums, where the
degree of similarity is application dependent.
[0271] Referring to FIGS. 24G-I, arbitration module 2424 will
select either demodulated baseband signal 2418a or 2418c, because
error check module 2420b will set the error flag 2422b that is
associated with demodulated baseband signal 2418b.
[0272] The error detection schemes implemented by the error
detection modules include but are not limited to: cyclic redundancy
check (CRC) and parity check for digital signals, and various error
detections schemes for analog signal.
[0273] Further details of enhanced signal reception as described in
this section are presented in pending U.S. application "Method and
System for Ensuring Reception of a Communications Signal," Ser. No.
09/176,415, filed Oct. 21, 1998, incorporated herein by reference
in its entirety.
6. UNIFIED DOWN-CONVERSION AND FILTERING
[0274] The present invention is directed to systems and methods of
unified down-conversion and filtering (UDF), and applications of
same.
[0275] In particular, the present invention includes a unified
down-converting and filtering (UDF) module that performs frequency
selectivity and frequency translation in a unified (i.e.,
integrated) manner. By operating in this manner, the invention
achieves high frequency selectivity prior to frequency translation
(the invention is not limited to this embodiment). The invention
achieves high frequency selectivity at substantially any frequency,
including but not limited to RF (radio frequency) and greater
frequencies. It should be understood that the invention is not
limited to this example of RF and greater frequencies. The
invention is intended, adapted, and capable of working with lower
than radio frequencies.
[0276] FIG. 17 is a conceptual block diagram of a UDF module 1702
according to an embodiment of the present invention. The UDF module
1702 performs at least frequency translation and frequency
selectivity.
[0277] The effect achieved by the UDF module 1702 is to perform the
frequency selectivity operation prior to the performance of the
frequency translation operation. Thus, the UDF module 1702
effectively performs input filtering.
[0278] According to embodiments of the present invention, such
input filtering involves a relatively narrow bandwidth. For
example, such input filtering may represent channel select
filtering, where the filter bandwidth may be, for example, 50 KHz
to 150 KHz. It should be understood, however, that the invention is
not limited to these frequencies. The invention is intended,
adapted, and capable of achieving filter bandwidths of less than
and greater than these values.
[0279] In embodiments of the invention, input signals 1704 received
by the UDF module 1702 are at radio frequencies. The UDF module
1702 effectively operates to input filter these RF input signals
1704. Specifically, in these embodiments, the UDF module 1702
effectively performs input, channel select filtering of the RF
input signal 1704. Accordingly, the invention achieves high
selectivity at high frequencies.
[0280] The UDF module 1702 effectively performs various types of
filtering, including but not limited to bandpass filtering, low
pass filtering, high pass filtering, notch filtering, all pass
filtering, band stop filtering, etc., and combinations thereof.
[0281] Conceptually, the UDF module 1702 includes a frequency
translator 1708. The frequency translator 1708 conceptually
represents that portion of the UDF module 1702 that performs
frequency translation (down conversion).
[0282] The UDF module 1702 also conceptually includes an apparent
input filter 1706 (also sometimes called an input filtering
emulator). Conceptually, the apparent input filter 1706 represents
that portion of the UDF module 1702 that performs input
filtering.
[0283] In practice, the input filtering operation performed by the
UDF module 1702 is integrated with the frequency translation
operation. The input filtering operation can be viewed as being
performed concurrently with the frequency translation operation.
This is a reason why the input filter 1706 is herein referred to as
an "apparent" input filter 1706.
[0284] The UDF module 1702 of the present invention includes a
number of advantages. For example, high selectivity at high
frequencies is realizable using the UDF module 1702. This feature
of the invention is evident by the high Q factors that are
attainable. For example, and without limitation, the UDF module
1702 can be designed with a filter center frequency f.sub.C on the
order of 900 MHZ, and a filter bandwidth on the order of 50 KHz.
This represents a Q of 18,000 (Q is equal to the center frequency
divided by the bandwidth).
[0285] It should be understood that the invention is not limited to
filters with high Q factors. The filters contemplated by the
present invention may have lesser or greater Qs, depending on the
application, design, and/or implementation. Also, the scope of the
invention includes filters where Q factor as discussed herein is
not applicable.
[0286] The invention exhibits additional advantages. For example,
the filtering center frequency f.sub.C of the UDF module 1702 can
be electrically adjusted, either statically or dynamically.
[0287] Also, the UDF module 1702 can be designed to amplify input
signals.
[0288] Further, the UDF module 1702 can be implemented without
large resistors, capacitors, or inductors. Also, the UDF module
1702 does not require that tight tolerances be maintained on the
values of its individual components, i.e., its resistors,
capacitors, inductors, etc. As a result, the architecture of the
UDF module 1702 is friendly to integrated circuit design techniques
and processes.
[0289] The features and advantages exhibited by the UDF module 1702
are achieved at least in part by adopting a new technological
paradigm with respect to frequency selectivity and translation.
Specifically, according to the present invention, the UDF module
1702 performs the frequency selectivity operation and the frequency
translation operation as a single, unified (integrated) operation.
According to the invention, operations relating to frequency
translation also contribute to the performance of frequency
selectivity, and vice versa.
[0290] According to embodiments of the present invention, the UDF
module generates an output signal from an input signal using
samples/instances of the input signal and samples/instances of the
output signal.
[0291] More particularly, first, the input signal is under-sampled.
This input sample includes information (such as amplitude, phase,
etc.) representative of the input signal existing at the time the
sample was taken.
[0292] As described further below, the effect of repetitively
performing this step is to translate the frequency (that is,
down-convert) of the input signal to a desired lower frequency,
such as an intermediate frequency (IF) or baseband.
[0293] Next, the input sample is held (that is, delayed).
[0294] Then, one or more delayed input samples (some of which may
have been scaled) are combined with one or more delayed instances
of the output signal (some of which may have been scaled) to
generate a current instance of the output signal.
[0295] Thus, according to a preferred embodiment of the invention,
the output signal is generated from prior samples/instances of the
input signal and/or the output signal. (It is noted that, in some
embodiments of the invention, current samples/instances of the
input signal and/or the output signal may be used to generate
current instances of the output signal.). By operating in this
manner, the UDF module preferably performs input filtering and
frequency down-conversion in a unified manner.
[0296] FIG. 19 illustrates an example implementation of the unified
down-converting and filtering (UDF) module 1922. The UDF module
1922 performs the frequency translation operation and the frequency
selectivity operation in an integrated, unified manner as described
above, and as further described below.
[0297] In the example of FIG. 19, the frequency selectivity
operation performed by the UDF module 1922 comprises a band-pass
filtering operation according to EQ. 1, below, which is an example
representation of a band-pass filtering transfer function.
VO=.alpha..sub.1z.sup.-1VI-.beta..sub.1z.sup.-1VO-.beta..sub.0z.sup.-2VO
EQ. 1
[0298] It should be noted, however, that the invention is not
limited to band-pass filtering. Instead, the invention effectively
performs various types of filtering, including but not limited to
bandpass filtering, low pass filtering, high pass filtering, notch
filtering, all pass filtering, band stop filtering, etc., and
combinations thereof. As will be appreciated, there are many
representations of any given filter type. The invention is
applicable to these filter representations. Thus, EQ. 1 is referred
to herein for illustrative purposes only, and is not limiting.
[0299] The UDF module 1922 includes a down-convert and delay module
1924, first and second delay modules 1928 and 1930, first and
second scaling modules 1932 and 1934, an output sample and hold
module 1936, and an (optional) output smoothing module 1938. Other
embodiments of the UDF module will have these components in
different configurations, and/or a subset of these components,
and/or additional components. For example, and without limitation,
in the configuration shown in FIG. 19, the output smoothing module
1938 is optional.
[0300] As further described below, in the example of FIG. 19, the
down-convert and delay module 1924 and the first and second delay
modules 1928 and 1930 include switches that are controlled by a
clock having two phases, .phi..sub.1 and .phi..sub.2. .phi..sub.1
and .phi..sub.2 preferably have the same frequency, and are
non-overlapping (alternatively, a plurality such as two clock
signals having these characteristics could be used). As used
herein, the term "non-overlapping" is defined as two or more
signals where only one of the signals is active at any given time.
In some embodiments, signals are "active" when they are high. In
other embodiments, signals are active when they are low.
[0301] Preferably, each of these switches closes on a rising edge
of .phi..sub.1 or .phi..sub.2, and opens on the next corresponding
falling edge of .phi..sub.1 or .phi..sub.2. However, the invention
is not limited to this example. As will be apparent to persons
skilled in the relevant art(s), other clock conventions can be used
to control the switches.
[0302] In the example of FIG. 19, it is assumed that .alpha..sub.1
is equal to one. Thus, the output of the down-convert and delay
module 1924 is not scaled. As evident from the embodiments
described above, however, the invention is not limited to this
example.
[0303] The example UDF module 1922 has a filter center frequency of
900.2 MHZ and a filter bandwidth of 570 KHz. The pass band of the
UDF module 1922 is on the order of 899.915 MHZ to 900.485 MHZ. The
Q factor of the UDF module 1922 is approximately 1879 (i.e., 900.2
MHZ divided by 570 KHz).
[0304] The operation of the UDF module 1922 shall now be described
with reference to a Table 1802 (FIG. 18) that indicates example
values at nodes in the UDF module 1922 at a number of consecutive
time increments. It is assumed in Table 1802 that the UDF module
1922 begins operating at time t-1. As indicated below, the UDF
module 1922 reaches steady state a few time units after operation
begins. The number of time units necessary for a given UDF module
to reach steady state depends on the configuration of the UDF
module, and will be apparent to persons skilled in the relevant
art(s) based on the teachings contained herein.
[0305] At the rising edge of .phi..sub.1 at time t-1, a switch 1950
in the down-convert and delay module 1924 closes. This allows a
capacitor 1952 to charge to the current value of an input signal,
VI.sub.t-1, such that node 1902 is at VI.sub.t-1. This is indicated
by cell 1804 in FIG. 18. In effect, the combination of the switch
1950 and the capacitor 1952 in the down-convert and delay module
1924 operates to translate the frequency of the input signal VI to
a desired lower frequency, such as IF or baseband. Thus, the value
stored in the capacitor 1952 represents an instance of a
down-converted image of the input signal VI.
[0306] The manner in which the down-convert and delay module 1924
performs frequency down-conversion is further described elsewhere
in this application, and is additionally described in pending U.S.
application "Method and System for Down-Converting Electromagnetic
Signals," Ser. No. 09/176,022, filed Oct. 21, 1998, issued as U.S.
Pat. No. 6,061,551, which is herein incorporated by reference in
its entirety.
[0307] Also at the rising edge of .phi..sub.1 at time t-1, a switch
1958 in the first delay module 1928 closes, allowing a capacitor
1960 to charge to VO.sub.t-1, such that node 1906 is at VO.sub.t-1.
This is indicated by cell 1806 in Table 1802. (In practice,
VO.sub.t-1 is undefined at this point. However, for ease of
understanding, VO.sub.t-1 shall continue to be used for purposes of
explanation.)
[0308] Also at the rising edge of .phi..sub.1 at time t-1, a switch
1966 in the second delay module 1930 closes, allowing a capacitor
1968 to charge to a value stored in a capacitor 1964. At this time,
however, the value in capacitor 1964 is undefined, so the value in
capacitor 1968 is undefined. This is indicated by cell 1807 in
table 1802.
[0309] At the rising edge of .phi..sub.2 at time t-1, a switch 1954
in the down-convert and delay module 1924 closes, allowing a
capacitor 1956 to charge to the level of the capacitor 1952.
Accordingly, the capacitor 1956 charges to VI.sub.t-1, such that
node 1904 is at VI.sub.t-1. This is indicated by cell 1810 in Table
1802.
[0310] The UDF module 1922 may optionally include a unity gain
module 1990A between capacitors 1952 and 1956. The unity gain
module 1990A operates as a current source to enable capacitor 1956
to charge without draining the charge from capacitor 1952. For a
similar reason, the UDF module 1922 may include other unity gain
modules 1990B-1990G. It should be understood that, for many
embodiments and applications of the invention, these unity gain
modules 1990A-1990G are optional. The structure and operation of
the unity gain modules 1990 will be apparent to persons skilled in
the relevant art(s).
[0311] Also at the rising edge of .phi..sub.2 at time t-1, a switch
1962 in the first delay module 1928 closes, allowing a capacitor
1964 to charge to the level of the capacitor 1960. Accordingly, the
capacitor 1964 charges to VO.sub.t-1, such that node 1908 is at
VO.sub.t-1. This is indicated by cell 1814 in Table 1802.
[0312] Also at the rising edge of .phi..sub.2 at time t-1, a switch
1970 in the second delay module 1930 closes, allowing a capacitor
1972 to charge to a value stored in a capacitor 1968. At this time,
however, the value in capacitor 1968 is undefined, so the value in
capacitor 1972 is undefined. This is indicated by cell 1815 in
table 1802.
[0313] At time t, at the rising edge of .phi..sub.1, the switch
1950 in the down-convert and delay module 1924 closes. This allows
the capacitor 1952 to charge to VI.sub.t, such that node 1902 is at
VI.sub.t. This is indicated in cell 1816 of Table 1802.
[0314] Also at the rising edge of .phi..sub.1 at time t, the switch
1958 in the first delay module 1928 closes, thereby allowing the
capacitor 1960 to charge to VO.sub.t. Accordingly, node 1906 is at
VO.sub.t. This is indicated in cell 1820 in Table 1802.
[0315] Further at the rising edge of .phi..sub.1 at time t, the
switch 1966 in the second delay module 1930 closes, allowing a
capacitor 1968 to charge to the level of the capacitor 1964.
Therefore, the capacitor 1968 charges to VO.sub.t-1, such that node
1910 is at VO.sub.t-1. This is indicated by cell 1824 in Table
1802.
[0316] At the rising edge of .phi..sub.2 at time t, the switch 1954
in the down-convert and delay module 1924 closes, allowing the
capacitor 1956 to charge to the level of the capacitor 1952.
Accordingly, the capacitor 1956 charges to VI.sub.t, such that node
1904 is at VI.sub.t. This is indicated by cell 1828 in Table
1802.
[0317] Also at the rising edge of .phi..sub.2 at time t, the switch
1962 in the first delay module 1928 closes, allowing the capacitor
1964 to charge to the level in the capacitor 1960. Therefore, the
capacitor 1964 charges to VO.sub.t, such that node 1908 is at
VO.sub.t. This is indicated by cell 1832 in Table 1802.
[0318] Further at the rising edge of .phi..sub.2 at time t, the
switch 1970 in the second delay module 1930 closes, allowing the
capacitor 1972 in the second delay module 1930 to charge to the
level of the capacitor 1968 in the second delay module 1930.
Therefore, the capacitor 1972 charges to VO.sub.t-1, such that node
1912 is at VO.sub.t-1. This is indicated in cell 1836 of FIG.
18.
[0319] At time t+1, at the rising edge of .phi..sub.1, the switch
1950 in the down-convert and delay module 1924 closes, allowing the
capacitor 1952 to charge to VI.sub.t+1. Therefore, node 1902 is at
VI.sub.t+1, as indicated by cell 1838 of Table 1802.
[0320] Also at the rising edge of .phi..sub.1 at time t+1, the
switch 1958 in the first delay module 1928 closes, allowing the
capacitor 1960 to charge to VO.sub.t+1. Accordingly, node 1906 is
at VO.sub.t+1, as indicated by cell 1842 in Table 1802.
[0321] Further at the rising edge of .phi..sub.1 at time t+1, the
switch 1966 in the second delay module 1930 closes, allowing the
capacitor 1968 to charge to the level of the capacitor 1964.
Accordingly, the capacitor 1968 charges to VO.sub.t, as indicated
by cell 1846 of Table 1802.
[0322] In the example of FIG. 19, the first scaling module 1932
scales the value at node 1908 (i.e., the output of the first delay
module 1928) by a scaling factor of -0.1. Accordingly, the value
present at node 1914 at time t+1 is -0.1*VO.sub.t. Similarly, the
second scaling module 1934 scales the value present at node 1912
(i.e., the output of the second scaling module 1930) by a scaling
factor of -0.8. Accordingly, the value present at node 1916 is
-0.8*VO.sub.t-1 at time t+1.
[0323] At time t+1, the values at the inputs of the summer 1926
are: VI.sub.t at node 1904, -0.1*VO.sub.t at node 1914, and
-0.8*VO.sub.t-1 at node 1916 (in the example of FIG. 19, the values
at nodes 1914 and 1916 are summed by a second summer 1925, and this
sum is presented to the summer 1926). Accordingly, at time t+1, the
summer generates a signal equal to
VI.sub.t-0.1*VO.sub.t-0.8*VO.sub.t-1.
[0324] At the rising edge of .phi..sub.1 at time t+1, a switch 1991
in the output sample and hold module 1936 closes, thereby allowing
a capacitor 1992 to charge to VO.sub.t+1. Accordingly, the
capacitor 1992 charges to VO.sub.t+1, which is equal to the sum
generated by the adder 1926. As just noted, this value is equal to:
VI.sub.t-0.1*VO.sub.t-0.8*VO.sub.t-1. This is indicated in cell
1850 of Table 1802. This value is presented to the optional output
smoothing module 1938, which smooths the signal to thereby generate
the instance of the output signal VO.sub.t+1. It is apparent from
inspection that this value of VO.sub.t+1 is consistent with the
band pass filter transfer function of EQ. 1.
[0325] Further details of unified down-conversion and filtering as
described in this section are presented in pending U.S. application
"Integrated Frequency Translation And Selectivity," Ser. No.
09/175,966, filed Oct. 21, 1998, incorporated herein by reference
in its entirety.
7. EXAMPLE APPLICATION EMBODIMENTS OF THE INVENTION
[0326] As noted above, the UFT module of the present invention is a
very powerful and flexible device. Its flexibility is illustrated,
in part, by the wide range of applications in which it can be used.
Its power is illustrated, in part, by the usefulness and
performance of such applications.
[0327] Example applications of the UFT module were described above.
In particular, frequency down-conversion, frequency up-conversion,
enhanced signal reception, and unified down-conversion and
filtering applications of the UFT module were summarized above, and
are further described below. These applications of the UFT module
are discussed herein for illustrative purposes. The invention is
not limited to these example applications. Additional applications
of the UFT module will be apparent to persons skilled in the
relevant art(s), based on the teachings contained herein.
[0328] For example, the present invention can be used in
applications that involve frequency down-conversion. This is shown
in FIG. 1C, for example, where an example UFT module 115 is used in
a down-conversion module 114. In this capacity, the UFT module 115
frequency down-converts an input signal to an output signal. This
is also shown in FIG. 7, for example, where an example UFT module
706 is part of a down-conversion module 704, which is part of a
receiver 702.
[0329] The present invention can be used in applications that
involve frequency up-conversion. This is shown in FIG. 1D, for
example, where an example UFT module 117 is used in a frequency
up-conversion module 116. In this capacity, the UFT module 117
frequency up-converts an input signal to an output signal. This is
also shown in FIG. 8, for example, where an example UFT module 806
is part of up-conversion module 804, which is part of a transmitter
802.
[0330] The present invention can be used in environments having one
or more transmitters 902 and one or more receivers 906, as
illustrated in FIG. 9. In such environments, one or more of the
transmitters 902 may be implemented using a UFT module, as shown
for example in FIG. 8. Also, one or more of the receivers 906 may
be implemented using a UFT module, as shown for example in FIG.
7.
[0331] The invention can be used to implement a transceiver. An
example transceiver 1002 is illustrated in FIG. 10. The transceiver
1002 includes a transmitter 1004 and a receiver 1008. Either the
transmitter 1004 or the receiver 1008 can be implemented using a
UFT module. Alternatively, the transmitter 1004 can be implemented
using a LIFT module 1006, and the receiver 1008 can be implemented
using a UFT module 1010. This embodiment is shown in FIG. 10.
[0332] Another transceiver embodiment according to the invention is
shown in FIG. 11. In this transceiver 1102, the transmitter 1104
and the receiver 1108 are implemented using a single UFT module
1106. In other words, the transmitter 1104 and the receiver 1108
share a UFT module 1106.
[0333] As described elsewhere in this application, the invention is
directed to methods and systems for enhanced signal reception
(ESR). Various ESR embodiments include an ESR module (transmit) in
a transmitter 1202, and an ESR module (receive) in a receiver 1210.
An example ESR embodiment configured in this manner is illustrated
in FIG. 12.
[0334] The ESR module (transmit) 1204 includes a frequency
up-conversion module 1206. Some embodiments of this frequency
up-conversion module 1206 may be implemented using a UFT module,
such as that shown in FIG. 1D.
[0335] The ESR module (receive) 1212 includes a frequency
down-conversion module 1214. Some embodiments of this frequency
down-conversion module 1214 may be implemented using a UFT module,
such as that shown in FIG. 1C.
[0336] As described elsewhere in this application, the invention is
directed to methods and systems for unified down-conversion and
filtering (UDF). An example unified down-conversion and filtering
module 1302 is illustrated in FIG. 13. The unified down-conversion
and filtering module 1302 includes a frequency down-conversion
module 1304 and a filtering module 1306. According to the
invention, the frequency down-conversion module 1304 and the
filtering module 1306 are implemented using a UFT module 1308, as
indicated in FIG. 13.
[0337] Unified down-conversion and filtering according to the
invention is useful in applications involving filtering and/or
frequency down-conversion. This is depicted, for example, in FIGS.
15A-15F. FIGS. 15A-15C indicate that unified down-conversion and
filtering according to the invention is useful in applications
where filtering precedes, follows, or both precedes and follows
frequency down-conversion. FIG. 15D indicates that a unified
down-conversion and filtering module 1524 according to the
invention can be utilized as a filter 1522 (i.e., where the extent
of frequency down-conversion by the down-converter in the unified
down-conversion and filtering module 1524 is minimized). FIG. 15E
indicates that a unified down-conversion and filtering module 1528
according to the invention can be utilized as a down-converter 1526
(i.e., where the filter in the unified down-conversion and
filtering module 1528 passes substantially all frequencies). FIG.
15F illustrates that the unified down-conversion and filtering
module 1532 can be used as an amplifier. It is noted that one or
more UDF modules can be used in applications that involve at least
one or more of filtering, frequency translation, and
amplification.
[0338] For example, receivers, which typically perform filtering,
down-conversion, and filtering operations, can be implemented using
one or more unified down-conversion and filtering modules. This is
illustrated, for example, in FIG. 14.
[0339] The methods and systems of unified down-conversion and
filtering of the invention have many other applications. For
example, as discussed herein, the enhanced signal reception (ESR)
module (receive) operates to down-convert a signal containing a
plurality of spectrums. The ESR module (receive) also operates to
isolate the spectrums in the down-converted signal, where such
isolation is implemented via filtering in some embodiments.
According to embodiments of the invention, the ESR module (receive)
is implemented using one or more unified down-conversion and
filtering (UDF) modules. This is illustrated, for example, in FIG.
16. In the example of FIG. 16, one or more of the UDF modules 1610,
1612, 1614 operates to down-convert a received signal. The UDF
modules 1610, 1612, 1614 also operate to filter the down-converted
signal so as to isolate the spectrum(s) contained therein. As noted
above, the UDF modules 1610, 1612, 1614 are implemented using the
universal frequency translation (UFT) modules of the invention.
[0340] The invention is not limited to the applications of the UFT
module described above. For example, and without limitation,
subsets of the applications (methods and/or structures) described
herein (and others that would be apparent to persons skilled in the
relevant art(s) based on the herein teachings) can be associated to
form useful combinations.
[0341] For example, transmitters and receivers are two applications
of the UFT module. FIG. 10 illustrates a transceiver 1002 that is
formed by combining these two applications of the UFT module, i.e.,
by combining a transmitter 1004 with a receiver 1008.
[0342] Also, ESR (enhanced signal reception) and unified
down-conversion and filtering are two other applications of the UFT
module. FIG. 16 illustrates an example where ESR and unified
down-conversion and filtering are combined to form a modified
enhanced signal reception system.
[0343] The invention is not limited to the example applications of
the UFT module discussed herein. Also, the invention is not limited
to the example combinations of applications of the UFT module
discussed herein. These examples were provided for illustrative
purposes only, and are not limiting. Other applications and
combinations of such applications will be apparent to persons
skilled in the relevant art(s) based on the teachings contained
herein. Such applications and combinations include, for example and
without limitation, applications/combinations comprising and/or
involving one or more of: (1) frequency translation; (2) frequency
down-conversion; (3) frequency up-conversion; (4) receiving; (5)
transmitting; (6) filtering; and/or (7) signal transmission and
reception in environments containing potentially jamming
signals.
[0344] Additional examples are set forth below describing
applications of the UFT module in the area of universal platform
modules.
8. UNIVERSAL PLATFORM MODULE (UPM)
[0345] The invention is directed to devices which, generally,
provide some information technology and communicate on a network or
over any other communication medium (such as wireless and wired
communication mediums). In order to communicate, the devices
receive a signal, optionally modify the signal or otherwise process
the signal in an application specific manner, display the
information, allow modification of the information, and then
transmit a modified signal at the same or different frequency or
frequencies. As will be appreciated, at least some of these
operations are optional. A device is often used in an off-line
manner where it is disconnected from the network or networks (or,
more generally, when the device is not in communication with other
devices/external entities).
[0346] A device 2602 is illustrated, for example, in FIG. 32, where
an example UPM 2606 enables communication with networks using
cellular 3210, wireless local loop (WLL) 3215, wireless local area
network (WLAN) 3220, wireline (LAN, WAN, etc.) 3230, and analog
3225 network links. These network links and/or topologies are
described herein for example purposes only, although it should be
understood that the invention is applicable to any communication
medium. Device 2602 communicates using these links to any of the
components (PCs, servers, other devices) which are available on the
respective networks 3212, 3217, 3222, 3227, and 3232. Such
communication may be simultaneous, either actual or apparent.
[0347] The UPM 2606 may include a receiver, transmitter, and/or
transceiver. Such components employ one or more UFT modules for
performing frequency translation operations. See, for example,
FIGS. 10 and 11 in the case of transceivers. See, for example,
FIGS. 7 and 8 for receivers and transmitters.
[0348] 8.1 Conventional Multi-Mode Usage Model
[0349] FIG. 25A illustrates a high level block diagram of an
example conventional multi-mode device 2502. Multi-mode device 2502
includes device resources 2504, a CDMA platform module 2508, and a
Bluetooth platform module 2506. CDMA platform module 2508 is
constructed to perform cellular telephone operations with the
cellular CDMA network 2510. Bluetooth platform module 2506 is
constructed to perform WLAN operations with other Bluetooth devices
on the Bluetooth Network 2512.
[0350] FIG. 25B illustrates a more detailed block diagram of a
platform module 2508a employing a conventional receiver implemented
with heterodyne components. Platform module 2508a frequency
down-converts and demodulates a first EM signal 2514 received by
first antenna 2515. First EM signal 2514 generally comprises a
electromagnetic (EM) signal broadcast at a carrier frequency
modulated by a baseband information signal.
[0351] FIG. 25C illustrates a more detailed block diagram of a
platform module 2508b employing a conventional transmitter
implemented with heterodyne components. Platform module 2508b
operates similarly to platform module 2508a. Platform module 2508b
modulates and frequency up-converts baseband signal 2518, and
outputs an EM signal 2542 that is transmitted by an antenna
2540.
[0352] Conventional platform module 2508, whether implemented as a
receiver or transmitter (and/or transceiver (not shown)), suffers
from the disadvantages of conventional wireless communication
methods and systems. For instance, receivers and transmitters are
conventionally implemented with heterodyne components. As
previously described, heterodyne implementations are complex, are
expensive to design, manufacture, and tune, and suffer from
additional deficiencies well known in the art.
[0353] 8.2 Universal Platform Module of the Present Invention
[0354] FIG. 26 illustrates a high level block diagram embodiment of
an exemplary universal platform enabled device 2602 according to an
embodiment of the present invention.
[0355] Universal platform enabled device 2602 includes device
resources 2604 and a UPM 2606. UPM 2606 comprises at least one UFT
module 2620 (as shown in FIG. 26B). UPM 2606 is shown linking to
various network types: cellular network 2610, WLAN network 2612,
WLL network 2614, and other networks 2616. Other networks 2616
include personal area networks (PANs), other non-IP networks, and
any network resulting without limitation from the connection of
devices through any communication medium, wired or wireless.
[0356] UPM 2606 receives signals and transmits signals using the
UFT module 2620 as described herein.
[0357] In another embodiment, additional UFT modules 2620 may be
employed, as shown in FIG. 26C. Persons skilled in the relevant
art(s) will recognize after reading this disclosure that in
particular applications, additional UFT modules may be used.
[0358] Furthermore, FIG. 26C illustrates another embodiment where
universal platform sub-modules (UPSM) 2622, each containing a UFT
module 2620, are employed. Each UPSM 2622 would be capable of
maintaining one or more links to the various networks/communication
mediums disclosed herein.
[0359] The UPM 2606 of the present invention is also directed to
digital signal applications. In a further embodiment, optional
signal conditioning module 2523 comprises an analog-to-digital
converter (A/D), a digital signal processor (DSP), a
digital-to-analog (D/A) converter, and storage. Optional signal
conditioning module 2523 inputs down-converted baseband signal 2518
to A/D. A/D converts down-converted baseband signal 2518 to a
digital signal on interconnection. DSP can perform any digital
signal processing function on the digital signal for signal
amplification, filtering, error correction, etc. DSP may comprise a
digital signal processing chip, a computer, hardware, software,
firmware, or any combination thereof, or any other applicable
technology known to persons skilled in the relevant art(s). Storage
provides for storing digital signals at any stage prior to
digital-to-analog conversion by D/A. These digital signals include
the digital signal received from A/D, the digital signal to be
output to D/A, or any intermediate signal provided by DSP. The
interconnection may be configured between the components of
optional signal conditioning module 2523 in a variety of ways as
required by the present application, as would be understood by
persons skilled in the relevant art(s).
[0360] D/A inputs the digital signal to be transmitted from
interconnection, and converts it to analog, outputting baseband
signal 2518. Optional signal conditioning module 2523 provides for
digital signal processing and conditioning of a received signal
prior to its re-transmission. Persons skilled in the relevant
art(s) will recognize that a variety of digital signal conditioning
configurations exist for optional signal conditioning module 2523.
Any other digital signal conditioning function may be performed by
optional signal conditioning module 2523, as would be known to
persons skilled in the relevant art(s).
[0361] Furthermore, persons skilled in the relevant art(s) will
recognize that optional signal conditioning module 2523 can be
configured to handle a combination of analog and digital signal
conditioning functions.
[0362] Exemplary embodiments of the UPM 2606 and UPSM 2622 of the
present invention are described below. However, it should be
understood that these examples are provided for illustrative
purposes only. The invention is not limited to these embodiments.
Alternate embodiments (including equivalents, extensions,
variations, deviations, etc., of the embodiments described herein)
will be apparent to persons skilled in the relevant art(s) based on
the teachings contained herein. The invention is intended and
adapted to include such alternate embodiments.
[0363] 8.2.1 Universal Platform Module Embodiments
[0364] The universal platform module of the present invention is
directed to applications of universal platform modules and
sub-modules. The universal platform module of the present invention
may be implemented in devices which are land-based, and air- and
space-based, or based anywhere else applicable. For example, the
universal platform module of the present invention may be
implemented in devices employed in ground stations, satellites,
spacecraft, watercraft, and aircraft. The universal platform module
of the present invention is applicable to any number of common
household consumer appliances and goods, including phones and
wireless modems. The universal platform module of the present
invention may be implemented in any applicable manner known to
persons skilled in the relevant art(s).
[0365] The universal platform module of the present invention is
preferably directed to analog signal applications, although the
invention is also applicable to digital applications. UPSM 3802 in
the example embodiment shown in FIG. 38 is specific to a particular
protocol and a particular bearer combination. The UPSM 3802
includes a receiver 3804 and a transmitter 3808 each including one
or more UFT modules (as indicated by 3806 and 3810) as described
herein and in the cited patent applications. Alternatively, the
UPSM 3802 includes a transceiver having one or more UFT modules as
described herein (as shown in FIG. 37 and discussed below).
[0366] The UPSM 3802 also includes a control module 3812 that
enables the UPSM 3802 to operate in conformance with the particular
protocol/bearer service combination. In particular, the control
module 3812 includes hardware, software, or combinations thereof to
cause the UPSM 3802 to receive, transmit, process, and otherwise
interact with signals according to the particular protocol/bearer
service combination. Implementation of the control module 3812 will
be apparent to persons skilled in the relevant art(s) based on at
least the teachings contained herein.
[0367] Examples of the UPSM 3802 include ones that operate
according to the example protocol/bearer service combinations shown
in FIG. 39. It should be understood that the examples shown in FIG.
39 are provided for illustrative purposes only, and are not
limiting. The invention is intended and adapted to operate with
other protocol/bearer service combinations, and these will be
apparent to persons skilled in the relevant art(s) based on at
least the teachings contained herein.
[0368] Also, FIG. 40 is a representation of groups of communication
links or types. The control module 3812 of the UPSM 3802 enables
the UPSM 3802 to operate in conformance with any such communication
link/type. In particular, the control module 3812 includes
hardware, software, or combinations thereof to cause the UPSM 3802
to receive, transmit, process, and otherwise interact with signals
according to the communication link/type. Implementation of the
control module 3812 will be apparent to persons skilled in the
relevant art(s) based on at least the teachings contained herein.
It should be understood that the examples shown in FIG. 40 are
provided for illustrative purposes only, and are not limiting. The
invention is intended and adapted to operate with other
communication links/types, and these will be apparent to persons
skilled in the relevant art(s) based on at least the teachings
contained herein.
[0369] An example embodiment of a USPM 3802 that operates according
to the WLAN communication type/link is described in greater detail
in U.S. provisional application Ser. No. 60/147,129 filed Aug. 4,
1999, which is herein incorporated by reference in its entirety. It
should be understood that this description is provided for
illustrative purposes only are is not limiting. In particular, the
invention is not limited to this combination.
[0370] An example embodiment of a USPM 3802 that operates according
to the CDMA communication type/link is described in greater detail
in U.S. patent application Ser. No. 09/525,185 filed Mar. 14, 2000
and Ser. No. 09/525,615 filed Mar. 14, 2000, which are herein
incorporated by reference in its entirety. Another example
embodiment of a USPM 3802 that operates according to the CDMA
communication type/link is described in greater detail in U.S.
patent application "Wireless Telephone Using Universal Frequency
Translation," filed Apr. 10, 2000, Attorney Docket Number
1744.0070000, incorporated herein by reference in its entirety. It
should be understood that this description is provided for
illustrative purposes only and is not limiting. In particular, the
invention is not limited to this combination.
[0371] The UPSM 3802; and in particular the control module 3812,
for the WAP/Bluetooth combination, shall now be described in
greater detail. It should be understood that this description is
provided for illustrative purposes only are is not limiting. In
particular, the invention is not limited to this combination.
[0372] FIG. 43 illustrates an embodiment of the invention for the
UPSM 3802 and control module 3812. Control module 3812 includes
sub-modules which contain implementation and operational
instructions for UPSM 3802. In one embodiment, WAP sub-module 4304
and Bluetooth sub-module 4306 are employed such that the UPSM may
operate using either Bluetooth or one of the number of bearer
services available to WAP.
[0373] In an embodiment, WAP sub-module 4304 contains the WAP
protocol stack and specification information about the WAP
architecture. For instance, the wireless application environment
(WAE) or application layer, session layer (WSP), transaction layer
(WTP), security layer (WTLS), and transport layer (WDP). This
information would enable control module 3812 to operate the
components of UPSM 3802 in a manner that conforms to both the
requirements of the protocol, but also to the requirements of the
operating environment. The operating environment includes, but is
not limited to, the available bearer services, content encoders and
decoders employed, available protocol gateways, etc.
[0374] In an embodiment, Bluetooth sub-module 4306 contains the
Bluetooth protocol stack and specification information about the
Bluetooth architecture. For instance, Bluetooth sub-module 4306
includes: 1) the link manager protocol (LMP), which is responsible
for link setup between Bluetooth-enabled devices, including
authentication and encryption; 2) the logical link control and
adaptation protocol (L2CAP), which serves as an adapter between the
upper layer protocols and the Bluetooth baseband protocol and
permits the higher level protocols to transmit and receive L2CAP
data packets; 3) the service discovery protocol (SDP), which
discovers information about the devices and services available in
the local Bluetooth network, and then enables a connection between
two or more Bluetooth-enabled devices; 4) the cable replacement
protocol (RFCOMM); 5) the telephony control protocol (TCS BIN); and
6) the telephony control-AT commands.
[0375] The Bluetooth sub-module 4306 is not limited to these
protocols. Additional protocol and specification information can be
included to enhance the functionality of the UPSM 3802.
Implementation of the sub-modules of control module 3812 will be
apparent to persons skilled in the relevant art(s) based on at
least the teachings contained herein. It should be understood that
the examples shown in FIGS. 39 and 40 are provided for illustrative
purposes only, and are not limiting. The invention is intended and
adapted to operate with other communication links/types, and these
will be apparent to persons skilled in the relevant art(s) based on
at least the teachings contained herein.
[0376] A device containing at least one UPM, which contains at
least one UPSM 3802 of FIG. 43, is capable of linking to wireless
networks using any of the bearer services available for the
protocols for which it is programmed and/or encoded. In one
example, the device is communicating point-of-sale information by
operating the receiver 3804 and transmitter 3808 components of UPSM
3802 for Bluetooth. In a nearly simultaneous fashion, the same
device is switching the same receiver 3804 and transmitter 3808
components of UPSM 3802 using the wireless application protocol
(WAP) to link the device to a cellular network using a CDMA
standard bearer service.
[0377] In an additional embodiment, a device is able to employ WAP
sub-module 4304 to maintain two or more nearly simultaneous links
to the same or different bearer services using the same or
different standards. For instance, a device is using AMPS to send
and receive facsimiles, while a voice call is being maintained over
GSM.
[0378] UPSM 4102 in the example embodiment shown in FIG. 41
contains a control module 4112 to enable the UPSM 4102 to operate
according to multiple protocol/bearer service combinations (FIG.
39) and/or multiple communication link/types (FIG. 40).
[0379] In an embodiment, the UPSM 4102 operates according to one
such protocol/bearer service combination or communication link/type
at any given time. In this embodiment, the UPSM 4102 may operate in
a multi-threaded manner so that it switches between protocol/bearer
service combination or communication link/type over time. This
enables the UPSM 4102 to effectively perform virtual or apparent
simultaneous processing of multiple protocol/bearer service
combinations and/or communication link/types.
[0380] Thus, the control module 4112 enables the UPSM 4102 to
operate in conformance with any combination of protocol/bearer
service combinations and communication link/types. In particular,
the control module 4112 includes hardware, software, or
combinations thereof to cause the UPSM 4102 to receive, transmit,
process, and otherwise interact with signals according to any such
protocol/bearer service combination or communication link/type.
Implementation of the control module 4112 will be apparent to
persons skilled in the relevant art(s) based on at least the
teachings contained herein.
[0381] In the example shown in FIG. 41, the UPSM 4102 includes a
transceiver 4104 having one or more UFT 4106 modules.
Alternatively, the UPSM 4102 could have one or more receivers and
one or more transmitters each having one or more UFT modules. In
some of such embodiments, the UPSM 4102 operates according to one
or more protocol/bearer service combinations and/or communication
link/types simultaneously at any given time. This enables the UPSM
4102 to perform simultaneous processing of multiple protocol/bearer
service combinations and/or communication link/types.
[0382] Examples of the UPSM include ones that operate according to
the example protocol/bearer service combinations shown in FIG. 39.
It should be understood that the examples shown in FIG. 39 are
provided for illustrative purposes only, and are not limiting. The
invention is intended and adapted to operate with other
protocol/bearer service combinations, and these will be apparent to
persons skilled in the relevant art(s) based on at least the
teachings contained herein.
[0383] Also, FIG. 40 is a representation of groups of communication
links or types. The control module 4112 of the UPSM 4102 enables
the UPSM 4102 to operate in conformance with any such communication
link/type. In particular, the control module 4112 includes
hardware, software, or combinations thereof to cause the UPSM 4102
to receive, transmit, process, and otherwise interact with signals
according to the communication link/type. Implementation of the
control module 4112 will be apparent to persons skilled in the
relevant art(s) based on at least the teachings contained herein.
It should be understood that the examples shown in FIG. 40 are
provided for illustrative purposes only, and are not limiting. The
invention is intended and adapted to operate with other
communication links/types, and these will be apparent to persons
skilled in the relevant art(s) based on at least the teachings
contained herein.
[0384] An example embodiment of a USPM 4102 that operates according
to the WLAN communication type/link is described in greater detail
in U.S. provisional application Ser. No. 60/147,129 filed Aug. 4,
1999, which is herein incorporated by reference in its entirety. It
should be understood that this description is provided for
illustrative purposes only are is not limiting. In particular, the
invention is not limited to this combination.
[0385] An example embodiment of a USPM 4102 that operates according
to the CDMA communication type/link is described in greater detail
in U.S. patent application Ser. No. 09/525,185 filed Mar. 14, 2000
and Ser. No. 09/525,615 filed Mar. 14, 2000, which are herein
incorporated by reference in its entirety. Another example
embodiment of a USPM 3802 that operates according to the CDMA
communication type/link is described in greater detail in U.S.
patent application "Wireless Telephone Using Universal Frequency
Translation," filed Apr. 10, 2000, Attorney Docket Number
1744.0070000, incorporated herein by reference in its entirety. It
should be understood that this description is provided for
illustrative purposes only are is not limiting. In particular, the
invention is not limited to this combination.
[0386] UPSM 4102, and in particular the control module 4112, for
the CDMA/GSM combination, shall now be described in greater detail.
It should be understood that this description is provided for
illustrative purposes only are is not limiting. In particular, the
invention is not limited to this combination.
[0387] FIG. 44 illustrates an embodiment of the invention for the
UPSM 4102 and control module 4112. Control module 4112 includes
protocol/bearer service sub-modules (P/BSSM) 4404 which contain
implementation and operational instructions for UPSM 4102. In one
embodiment, any number of P/BSSM 4404 are employed such that the
UPSM may operate using any number of networks.
[0388] In an embodiment, P/BSSM 4404 contains the WAP protocol
stack and specification information about the WAP architecture. For
instance, the wireless application environment (WAE) or application
layer, session layer (WSP), transaction layer (WTP), security layer
(WTLS), and transport layer (WDP). This information would enable
control module 4112 to operate the components of UPSM 4102 in a
manner that conforms to both the requirements of the protocol, but
also to the requirements of the operating environment. The
operating environment includes, but is not limited to, the
available bearer services, content encoders and decoders employed,
available protocol gateways, etc.
[0389] In an embodiment, P/BSSM 4404 contains the Bluetooth
protocol stack and specification information about the Bluetooth
architecture. For instance, P/BSSM 4404 includes: 1) the link
manager protocol (LMP), which is responsible for link setup between
Bluetooth-enabled devices, including authentication and encryption;
2) the logical link control and adaptation protocol (L2CAP), which
serves as an adapter between the upper layer protocols and the
Bluetooth baseband protocol and permits the higher level protocols
to transmit and receive L2CAP data packets; 3) the service
discovery protocol (SDP), which discovers information about the
devices and services available in the local Bluetooth network, and
then enables a connection between two or more Bluetooth-enabled
devices; 4) the cable replacement protocol (RFCOMM); 5) the
telephony control protocol (TCS BIN); and 6) the telephony
control-AT commands.
[0390] The P/BSSM 4404 is not limited to these protocols.
Additional protocol and specification information can be included
to enhance the functionality of the UPSM 4102. Implementation of
the sub-modules of control module 4112 will be apparent to persons
skilled in the relevant art(s) based on at least the teachings
contained herein. It should be understood that the examples shown
in FIGS. 39 and 40 are provided for illustrative purposes only, and
are not limiting. The invention is intended and adapted to operate
with other communication links/types, and these will be apparent to
persons skilled in the relevant art(s) based on at least the
teachings contained herein.
[0391] A device containing at least one UPM, which contains at
least one UPSM 4102 of FIG. 44, is capable of linking to networks
using any of the bearer services available for the protocols for
which it is programmed and/or encoded. In one example, the device
is communicating point-of-sale information by operating the
transceiver 4104 component of UPSM 4102. Simultaneously, the same
device is switching another of the transceiver 4104 components of
UPSM 4102 using the wireless application protocol (WAP) to link the
device to a cellular network using a CDMA standard bearer
service.
[0392] In an additional embodiment, a device is able to employ
P/BSSM 4404 to maintain two or more simultaneous links to the same
or different bearer services using the same or different standards.
For instance, a device is using AMPS to send and receive
facsimiles, while a voice call is being maintained over GSM.
[0393] It is noted that in the embodiments of FIGS. 43 and 44 the
instructions programmed and/or encoded into the sub-modules of the
control modules may be update, upgraded, replaced, and/or modified
in order to provide additional and/or new functionality. The
functionality may take the form of new network availability,
altered performance characteristics, changes in information
exchange formats, etc.
[0394] These example embodiments and other alternate embodiments
(including equivalents, extensions, variations, deviations, etc.,
of the example embodiments described herein) will be apparent to
persons skilled in the relevant art(s) based on the referenced
teachings and the teachings contained herein, and are within the
scope and spirit of the present invention. The invention is
intended and adapted to include such alternate embodiments.
[0395] 8.2.2 Universal Platform Module Receiver
[0396] The following discussion describes down-converting signals
using a Universal Frequency Down-conversion (UFD) Module. The
down-conversion of an EM signal by aliasing the EM signal at an
aliasing rate is described above, and is more fully described in
co-pending U.S. patent application entitled "Method and System for
Down-converting an Electromagnetic Signal," Ser. No. 09/176,022,
issued as U.S. Pat. No. 6,061,551, which is incorporated herein by
reference in its entirety.
[0397] Exemplary embodiments of the UPM receiver are described
below. However, it should be understood that these examples are
provided for illustrative purposes only. The invention is not
limited to these embodiments. Alternate embodiments (including
equivalents, extensions, variations, deviations, etc., of the
embodiments described herein) will be apparent to persons skilled
in the relevant art(s) based on the teachings contained herein. The
invention is intended and adapted to include such alternate
embodiments.
[0398] 8.2.2.1 Universal Platform Module Receiver Embodiments
[0399] FIG. 27A illustrates an embodiment of the receiving UPSM
2706. Receiving UPSM 2706 is described herein for purposes of
illustration, and not limitation. Alternate embodiments (including
equivalents, extensions, variations, deviations, etc., of the
embodiments described herein) will be apparent to persons skilled
in the relevant art(s) based on the teachings contained herein. The
invention is intended and adapted to include such alternate
embodiments.
[0400] Receiving UPSM 2706 of FIG. 27A comprises at least one UFD
module 2702. UFD module 2702 comprises at least one UFT module
2620. Numerous embodiments for receiving UPSM 2706 will be
recognized by persons skilled in the relevant art(s) from the
teachings herein, and are within the scope of the invention.
[0401] FIG. 27B illustrates an embodiment of the receiving UPSM
2706, in greater detail. Receiving UPSM 2706 comprises a UFD module
2702, an optional amplifier 2705, and an optional filter 2707. UFD
module 2702 comprises at least one UFT module 2620.
[0402] UFD module 2702 inputs received signal 2704. UFD module 2702
frequency down-converts received signal 2704 to UFD module output
signal 2708.
[0403] UFD module output signal 2708 is optionally amplified by
optional amplifier 2705 and optionally filtered by optional filter
2707, and a down-converted baseband signal 2516 results. The
amplifying and filtering functions may instead be provided for in
optional signal conditioning module 2523, when present.
[0404] Received signals of a variety of modulation types may be
down-converted directly to a baseband signal by receiving UPSM 2706
of FIG. 27B. These modulation types include, but are not limited to
phase modulation (PM), phase shift keying (PSK), amplitude
modulation (AM), amplitude shift keying (ASK), and quadrature
amplitude modulation (QAM), and combinations thereof.
[0405] In embodiments, UFD module 2702 frequency down-converts
received signal 2704 to a baseband signal. In alternative
embodiments, UFD module 2702 down-converts received signal 2704 to
an intermediate frequency.
[0406] FIG. 27C illustrates an alternative embodiment of receiving
UPSM 2706 comprising a UFD module 2702 that down-converts received
signal 2704 to an intermediate frequency. Receiving UPSM 2706 of
FIG. 27C comprises an intermediate frequency (IF) down-converter
2712. IF down-converter 2712 may comprise a UFD module and/or a UFT
module, or may comprise a conventional down-converter. In this
embodiment, UFD module output signal 2708 is output by UFD module
2702 at an intermediate frequency. This is an offset frequency, not
at baseband. IF down-converter 2712 inputs UFD module output signal
2708, and frequency down-converts it to baseband signal 2710.
[0407] Baseband signal 2710 is optionally amplified by optional
amplifier 2705 and optionally filtered by optional filter 2707, and
a down-converted baseband signal 2516 results.
[0408] Receiving UPSM 2706 may further comprise a third stage 1F
down-converter, and subsequent IF down-converters, as would be
required or preferred by some applications. It will be apparent to
persons skilled in the relevant art(s) how to design and configure
such further IF down-converters from the teachings contained
herein. Such implementations are within the scope of the present
invention.
[0409] 8.2.2.1.1 Detailed UFD Module Block Diagram
[0410] FIG. 28 illustrates an embodiment of UFD module 2702 of FIG.
27 in greater detail. This embodiment is described herein for
purposes of illustration, and not limitation. Alternate embodiments
(including equivalents, extensions, variations, deviations, etc.,
of the embodiments described herein) will be apparent to persons
skilled in the relevant art(s) based on the teachings contained
herein. The invention is intended and adapted to include such
alternate embodiments.
[0411] UFD module 2702 comprises a storage device 2802, an
oscillator 2804, a pulse-shaping circuit 2806, a reference
potential 2808, and a UFT module 2620. As described above, many
embodiments exist for UFD module 2702. For instance, in
embodiments, oscillator 2804, or both oscillator 2804 and
pulse-shaping circuit 2806, may be external to UFD module 2702.
[0412] Oscillator 2804 outputs oscillating signal 2810, which is
input by pulse-shaping circuit 2806. The output of pulse-shaping
circuit 2806 is a control signal 2812, which preferably comprises a
string of pulses. Pulse-shaping circuit 2806 controls the pulse
width of control signal 2812.
[0413] In embodiments, UFT module 2620 comprises a switch. Other
embodiments for UFT module 2620 are within the scope of the present
invention, such as those described above. One terminal of UFT
module 2620 is coupled to a received signal 2704, and a second
terminal of UFT module 2620 is coupled to a first terminal of
storage device 2802. A second terminal of storage device 2802 is
coupled to a reference potential 2808 such as a ground, or some
other potential. In a preferred embodiment, storage device 2802 is
a capacitor. In an embodiment, the switch contained within UFT
module 2620 opens and closes as a function of control signal 2812.
As a result of the opening and closing of this switch, a
down-converted signal, referred to as UFD module output signal
2708, results. Additional details pertaining to UFD module 2702 are
contained in co-pending U.S. patent application entitled "Method
and System for Down-Converting an Electromagnetic Signal," Ser. No.
09/176,022, issued as U.S. Pat. No. 6,061,551, which is
incorporated herein by reference in its entirety.
[0414] 8.2.2.2 In-Phase/Quadrature-phase (I/Q) Modulation Mode
Receiver Embodiments
[0415] FIG. 29 illustrates an exemplary I/Q modulation mode
embodiment of a receiving UPSM 2706, according to the present
invention. This I/Q modulation mode embodiment is described herein
for purposes of illustration, and not limitation. Alternate I/Q
modulation mode embodiments (including equivalents, extensions,
variations, deviations, etc., of the embodiments described herein),
as well as embodiments of other modulation modes, will be apparent
to persons skilled in the relevant art(s) based on the teachings
contained herein. The invention is intended and adapted to include
such alternate embodiments.
[0416] Receiving UPSM 2706 comprises an I/Q modulation mode
receiver 2934, a first optional amplifier 2912, a first filter
2914, a second optional amplifier 2916, and a second filter
2918.
[0417] I/Q modulation mode receiver 2934 comprises an oscillator
2902, a first UFD module 2904, a second UFD module 2906, a first
UFT module 2908, a second UFT module 2910, and a phase shifter
2920.
[0418] Oscillator 2902 provides an oscillating signal used by both
first UFD module 2904 and second UFD module 2906 via the phase
shifter 2920. Oscillator 2902 generates an "I" oscillating signal
2922.
[0419] "I" oscillating signal 2922 is input to first UFD module
2904. First UFD module 2904 comprises at least one UFT module 2908.
In an embodiment, first UFD module 2904 is structured similarly to
UFD module 2702 of FIG. 28, with oscillator 2902 substituting for
oscillator 2804, and "I" oscillating signal 2922 substituting for
oscillating signal 2810. First UFD module 2904 frequency
down-converts and demodulates received signal 2514 to
down-converted "I" signal 2926 according to "I" oscillating signal
2922.
[0420] Phase shifter 2920 receives "I" oscillating signal 2922, and
outputs "Q" oscillating signal 2924, which is a replica of "I"
oscillating signal 2922 shifted preferably by 90.degree..
[0421] Second UFD module 2906 inputs "Q" oscillating signal 2924.
Second UFD module 2906 comprises at least one UFT module 2910. In
an embodiment, second UFD module 2906 is structured similarly to
UFD module 2702 of FIG. 28, with "Q" oscillating signal 2924
substituting for oscillating signal 2810. Second UFD module 2906
frequency down-converts and demodulates received signal 2514 to
down-converted "Q" signal 2928 according to "Q" oscillating signal
2924.
[0422] Down-converted "I" signal 2926 is optionally amplified by
first optional amplifier 2912 and optionally filtered by first
optional filter 2914, and a first information output signal 2930 is
output.
[0423] Down-converted "Q" signal 2928 is optionally amplified by
second optional amplifier 2916 and optionally filtered by second
optional filter 2918, and a second information output signal 2932
is output.
[0424] In the embodiment depicted in FIG. 29, first information
output signal 2930 and second information output signal 2932
comprise down-converted baseband signal 2516 of FIGS. 27A-27C. In
an embodiment, optional signal conditioning module 2523 receives
first information output signal 2930 and second information output
signal 2932. These signals may be separately amplified/conditioned
by optional signal conditioning module 2523. Optionally amplified
and conditioned first information output signal 2930 and second
information output signal 2932 may then be individually modulated
and up-converted, and subsequently individually transmitted by one
or more transmitters. Alternatively, optionally amplified and
conditioned first information output signal 2930 and second
information output signal 2932 may be modulated, up-converted,
recombined into a single signal, and transmitted by a single
transmitting UPSM 3006 as shown in FIG. 30 and discussed herein.
For example, optionally amplified and conditioned first information
output signal 2930 and second information output signal 2932 may be
recombined into an I/Q modulated signal for re-transmission, as
further described below. In embodiments, optionally amplified and
conditioned first information output signal 2930 and second
information output signal 2932 may be modulated by the same or
different modulation schemes before retransmission, or before
recombination and retransmission.
[0425] Alternate configurations for I/Q modulation mode receiver
2934 will be apparent to persons skilled in the relevant art(s)
from the teachings herein. For instance, an alternate embodiment
exists wherein phase shifter 2920 is coupled between received
signal 2704 and UFD module 2906, instead of the configuration
described above. This and other such I/Q modulation mode receiver
embodiments will be apparent to persons skilled in the relevant
art(s) based upon the teachings herein, and are within the scope of
the present invention.
[0426] Reference is made to pending U.S. application Ser. No.
"Method, System, and Apparatus for Balanced Frequency Up-conversion
of a Baseband Signal," Ser. No. 09/525,615, filed Mar. 14, 2000,
for other teachings relating to this I/Q embodiment, which is
herein incorporated by reference in its entirety.
[0427] 8.2.2.3 Unified Down-Convert and Filter Receiver
Embodiments
[0428] As described above, the invention is directed to unified
down-conversion and filtering (UDF). UDF according to the invention
can be used to perform filtering and/or down-conversion
operations.
[0429] Many if not all of the applications described herein involve
frequency translation operations. Accordingly, the applications
described above can be enhanced by using any of the UDF embodiments
described herein.
[0430] Many if not all of the applications described above involve
filtering operations. Accordingly, any of the applications
described above can be enhanced by using any of the UDF embodiments
described herein.
[0431] Accordingly, the invention is directed to any of the
applications described herein in combination with any of the UDF
embodiments described herein.
[0432] For example, a block diagram of a receiving UPSM 2706
incorporating unified down-convert in filtering according to an
embodiment of the present invention is illustrated in FIG. 36.
Receiving UPSM 2706 comprises a UDF module 3602 and an optional
amplifier 3604. UDF Module 3602 both down-converts and filters
received signal 3610 and outputs UDF module output signal 3606. UDF
module output signal 3606 is optionally amplified by optional
amplifier 3604, outputting down-converted baseband signal 2516.
[0433] The unified down-conversion and filtering of a signal is
described above, and is more fully described in co-pending U.S.
patent application entitled "Integrated Frequency Translation And
Selectivity," Ser. No. 09/175,966, issued as U.S. Pat. No.
6,049,706, which is incorporated herein by reference in its
entirety.
[0434] These example embodiments and other alternate embodiments
(including equivalents, extensions, variations, deviations, etc.,
of the example embodiments described herein) will be apparent to
persons skilled in the relevant art(s) based on the referenced
teachings and the teachings contained herein, and are within the
scope and spirit of the present invention. The invention is
intended and adapted to include such alternate embodiments.
[0435] 8.2.2.4 Other Receiver Embodiments
[0436] The UPSM receiver embodiments described above are provided
for purposes of illustration. These embodiments are not intended to
limit the invention. Alternate embodiments, differing slightly or
substantially from those described herein, will be apparent to
persons skilled in the relevant art(s) based on the teachings
contained herein. Such alternate embodiments include, but are not
limited to, down-converting different combinations of modulation
techniques in an "I/Q" mode. Such alternate embodiments fall within
the scope and spirit of the present invention.
[0437] For example, other UPSM receiver embodiments may
down-convert signals that have been modulated with other modulation
techniques. These would be apparent to one skilled in the relevant
art(s) based on the teachings disclosed herein, and include, but
are not limited to, amplitude modulation (AM), frequency modulation
(FM), quadrature amplitude modulation (QAM), time division multiple
access (TDMA), frequency division multiple access (FDMA), code
division multiple access (CDMA), down-converting a signal with two
forms of modulation embedding thereon, and combinations
thereof.
[0438] 8.2.3 Universal Platform Module Transmitter Embodiments
[0439] The following discussion describes frequency up-converting
signals to be transmitted by an UPSM, using a Universal Frequency
Up-conversion (UFU) Module. Frequency up-conversion of an EM signal
is described above, and is more fully described in co-pending U.S.
patent application entitled "Method and System for Frequency
Up-Conversion," Ser. No. 09/176,154, the full disclosure of which
is incorporated herein by reference in its entirety.
[0440] Exemplary embodiments of the UPSM transmitter are described
below, including PM and I/Q modulation modes. However, it should be
understood that these examples are provided for illustrative
purposes only. The invention is not limited to these embodiments.
Alternate embodiments (including equivalents, extensions,
variations, deviations, etc., of the embodiments described herein)
will be apparent to persons skilled in the relevant art(s) based on
the teachings contained herein. The invention is intended and
adapted to include such alternate embodiments.
[0441] 8.2.3.1 Various Modulation Mode Transmitter Embodiments,
Including Phase Modulation (PM)
[0442] FIG. 30A illustrates an exemplary embodiment of the
transmitting UPSM 3006. Transmitting UPSM 3006 is described herein
for purposes of illustration, and not limitation. Alternate
embodiments (including equivalents, extensions, variations,
deviations, etc., of the embodiments described herein) will be
apparent to persons skilled in the relevant art(s) based on the
teachings contained herein. The invention is intended and adapted
to include such alternate embodiments.
[0443] Transmitting UPSM 3006 of FIG. 30A comprises at least one
UFU module 3004. UFU module 3004 comprises at least one UFT module
2620. Numerous embodiments for transmitting UPSM 3006 will be known
to persons skilled in the relevant art(s) from the teachings
herein, and are within the scope of the invention.
[0444] FIG. 30B illustrates in greater detail an exemplary
embodiment of the transmitting UPSM 3006 of FIG. 30A. Transmitting
UPSM 3006 comprises a modulator 3002, a UFU module 3004, and an
optional amplifier 3007.
[0445] Modulator 3002 of transmitting UPSM 3006 receives a baseband
signal 2518. Modulator 3002 modulates baseband signal 2518,
according to any modulation scheme, such as those described above.
FIG. 31 illustrates an embodiment of modulator 3002. In this
exemplary embodiment, the modulation scheme implemented may be
phase modulation (PM) or phase shift keying (PSK) modulation.
Modulator 3002 comprises an oscillator 3102 and a phase modulator
3104. Phase modulator 3104 receives baseband signal 2518 and an
oscillating signal 3106 from oscillator 3102. Phase modulator 3104
phase modulates oscillating signal 3106 using baseband signal 2518.
Phase modulators are well known to persons skilled in the relevant
art(s). Phase modulator outputs modulated signal 3010, according to
PM or PSK modulation.
[0446] In FIG. 30B, modulated signal 3010 is received by UFU module
3004. UFU module 3004 includes at least one UFT module 2620. UFU
module 3004 frequency up-converts the modulated signal, outputting
UFU module output signal 3008.
[0447] When present, optional amplifier 3006 amplifies UFU module
output signal 3008, outputting up-converted signal 3005.
[0448] In alternate embodiments, transmitting UPSM 3006 does not
require a modulator 3002 because UFU module 3004 performs the
modulation function. FIG. 30C illustrates such an alternate
embodiment of transmitting UPSM 3006 of FIG. 30A. Transmitting UPSM
3006 includes a UFU module 3004 and an optional amplifier 3007. UFU
module 3004 includes at least one UFT module 2620. UFU module 3004
frequency modulates and up-converts baseband signal 2518 to UFU
module output signal 3008. For instance, and without limitation,
UFU module 3004 may provide for frequency up-conversion and
modulation in an AM modulation mode. AM modulation techniques and
other modulation techniques are more fully described in co-pending
U.S. patent application entitled "Method and System for Frequency
Up-Conversion," Ser. No. 09/176,154, the full disclosure of which
is incorporated herein by reference in its entirety.
[0449] 8.2.3.1.1 Detailed UFU Module Embodiments
[0450] FIG. 33 illustrates a more detailed exemplary circuit
diagram of an embodiment of UFU module 3004 of FIG. 30A. UFU module
3004 is described herein for purposes of illustration, and not
limitation. Alternate embodiments (including equivalents,
extensions, variations, deviations, etc., of the embodiments
described herein) will be apparent to persons skilled in the
relevant art(s) based on the teachings contained herein. The
invention is intended and adapted to include such alternate
embodiments.
[0451] UFU module 3004 comprises a pulse-shaping circuit 3302, a
first reference potential 3304, a filter 3306, a second reference
potential 3308, a resistor 3310, and a UFT module 2620.
[0452] In FIG. 33, pulse shaping circuit 3302 receives baseband
signal 2518. Pulse shaping circuit 3302 outputs control signal
3314, which is preferably comprised of a string of pulses. Control
signal 3314 controls UFT module 2620, which preferably comprises a
switch. Various embodiments for UFT module 2620 are described
above. One terminal of UFT module 2620 is coupled to a first
reference potential 3304. The second terminal of UFT module 2620 is
coupled through resistor 3310 to a second reference potential 3308.
In a PM or PSK modulation embodiment, second reference potential
3308 is preferably a constant voltage level. In other embodiments,
such as in an amplitude modulation (AM) mode, second reference
potential 3308 may be a voltage that varies with the amplitude of
the information signal.
[0453] The output of UFT module 2620 is a harmonically rich signal
3312. Harmonically rich signal 3312 has a fundamental frequency and
phase substantially proportional to control signal 3314, and an
amplitude substantially proportional to the amplitude of second
reference potential 3308. Each of the harmonics of harmonically
rich signal 3312 also have phase proportional to control signal
3314, and in an PM or PSK embodiment are thus considered to be PM
or PSK modulated.
[0454] Harmonically rich signal 3312 is received by filter 3306.
Filter 3306 preferably has a high Q. Filter 3306 preferably selects
the harmonic of harmonically rich signal 3312 that is at the
approximate frequency desired for transmission. Filter 3306 removes
the undesired frequencies that exist as harmonic components of
harmonically rich signal 3312. Filter 3306 outputs UFU module
output signal 3008.
[0455] Further details pertaining to UFU module 3004 are provided
in co-pending U.S. patent application entitled "Method and System
for Frequency Up-Conversion," Ser. No. 09/176,154, which is
incorporated herein by reference in its entirety.
[0456] 8.2.3.2 In-Phase/Quadrature-Phase (I/Q) Modulation Mode
Transmitter Embodiments
[0457] In FIG. 34, an I/Q modulation mode embodiment is presented.
In this embodiment, two information signals are accepted. An
in-phase signal ("I") is modulated such that its phase varies as a
function of one of the information signals, and a quadrature-phase
signal ("Q") is modulated such that its phase varies as a function
of the other information signal. The two modulated signals are
combined to form an "I/Q" modulated signal and transmitted. In this
manner, for instance, two separate information signals could be
transmitted in a single signal simultaneously. Other uses for this
type of modulation would be apparent to persons skilled in the
relevant art(s).
[0458] FIG. 34 illustrates an exemplary block diagram of a
transmitting UPSM 3006 operating in an I/Q modulation mode. In FIG.
34, baseband signal 2518 comprises two signals, first information
signal 3402 and second information signal 3404. Transmitting UPSM
3006 comprises an I/Q transmitter 3406 and an optional amplifier
3408. I/Q transmitter 3406 comprises at least one UFT module 2620.
I/Q transmitter 3406 provides I/Q modulation to first information
signal 3402 and second information signal 3404, outputting I/Q
output signal 3410. Optional amplifier 3408 optionally amplifies
I/Q output signal 3410, outputting up-converted signal 3005.
[0459] FIG. 35 illustrates a more detailed circuit block diagram
for I/Q transmitter 3406. I/Q transmitter 3406 is described herein
for purposes of illustration, and not limitation. Alternate
embodiments (including equivalents, extensions, variations,
deviations, etc., of the embodiments described herein) will be
apparent to persons skilled in the relevant art(s) based on the
teachings contained herein. The invention is intended and adapted
to include such alternate embodiments.
[0460] I/Q transmitter 3406 comprises a first UFU module 3502, a
second UFU module 3504, an oscillator 3506, a phase shifter 3508, a
summer 3510, a first UFT module 3512, a second UFT module 3514, a
first phase modulator 3528, and a second phase modulator 3530.
[0461] Oscillator 3506 generates an "I"-oscillating signal
3516.
[0462] A first information signal 3402 is input to first phase
modulator 3528. The "I"-oscillating signal 3516 is modulated by
first information signal 3402 in the first phase modulator 3528,
thereby producing an "I"-modulated signal 3520.
[0463] First UFU module 3502 inputs "I"-modulated signal 3520, and
generates a harmonically rich "I" signal 3524 with a continuous and
periodic wave form.
[0464] The phase of "I"-oscillating signal 3516 is shifted by phase
shifter 3508 to create "Q"-oscillating signal 3518. Phase shifter
3508 preferably shifts the phase of "I"-oscillating signal 3516 by
90 degrees.
[0465] A second information signal 3404 is input to second phase
modulator 3530. "Q"-oscillating signal 3518 is modulated by second
information signal 3404 in second phase modulator 3530, thereby
producing a "Q" modulated signal 3522.
[0466] Second UFU module 3504 inputs "Q" modulated signal 3522, and
generates a harmonically rich "Q" signal 3526, with a continuous
and periodic waveform.
[0467] Harmonically rich "I" signal 3524 and harmonically rich "Q"
signal 3526 are preferably rectangular waves, such as square waves
or pulses (although the invention is not limited to this
embodiment), and are comprised of pluralities of sinusoidal waves
whose frequencies are integer multiples of the fundamental
frequency of the waveforms. These sinusoidal waves are referred to
as the harmonics of the underlying waveforms, and a Fourier
analysis will determine the amplitude of each harmonic.
[0468] Harmonically rich "I" signal 3524 and harmonically rich "Q"
signal 3526 are combined by summer 3510 to create harmonically rich
"I/Q" signal 3534. Summers are well known to persons skilled in the
relevant art(s).
[0469] Filter 3532 filters out the undesired harmonic frequencies,
and outputs an I/Q output signal 3410 at the desired harmonic
frequency or frequencies.
[0470] It will be apparent to persons skilled in the relevant
art(s) that an alternative embodiment exists wherein the
harmonically rich "I" signal 3524 and the harmonically rich "Q"
signal 3526 may be filtered before they are summed, and further,
another alternative embodiment exists wherein "I"-modulated signal
3520 and "Q"-modulated signal 3522 may be summed to create an
"I/Q"-modulated signal before being routed to a switch module.
Other "I/Q"-modulation embodiments will be apparent to persons
skilled in the relevant art(s) based upon the teachings herein, and
are within the scope of the present invention. Further details
pertaining to an I/Q modulation mode transmitter are provided in
co-pending U.S. patent application entitled "Method and System for
Frequency Up-Conversion," Ser. No. 09/176,154, which is
incorporated herein by reference in its entirety.
[0471] Reference is made to pending U.S. application Ser. No.
"Method, System, and Apparatus for Balanced Frequency Up-conversion
of a Baseband Signal," Ser. No. 09/525,615, filed Mar. 14, 2000,
for other teachings relating to this I/Q embodiment, which is
herein incorporated by reference in its entirety.
[0472] 8.2.3.3 Other Transmitter Embodiments
[0473] The UPSM transmitter embodiments described above are
provided for purposes of illustration. These embodiments are not
intended to limit the invention. Alternate embodiments, differing
slightly or substantially from those described herein, will be
apparent to persons skilled in the relevant art(s) based on the
teachings contained herein. Such alternate embodiments include, but
are not limited to, combinations of modulation techniques in an
"I/Q" mode. Such alternate embodiments fall within the scope and
spirit of the present invention.
[0474] For example, other UPSM transmitter embodiments may utilize
other modulation techniques. These would be apparent to one skilled
in the relevant art(s) based on the teachings disclosed herein, and
include, but are not limited to, amplitude modulation (AM),
frequency modulation (FM), quadrature amplitude modulation (QAM),
time division multiple access (TDMA), frequency division multiple
access (FDMA), code division multiple access (CDMA), embedding two
forms of modulation onto a signal for up-conversion, etc., and
combinations thereof.
[0475] 8.2.4 Enhanced Signal Reception Universal Platform
Embodiments
[0476] In additional embodiments of the present invention, enhanced
signal reception (ESR) according to the present invention may be
used. As discussed above, the invention is directed to methods and
systems for ESR. Any of the example applications discussed above
can be modified by incorporating ESR therein to enhance
communication between transmitters and receivers. Accordingly, the
invention is also directed to any of the applications described
above, in combination with any of the ESR embodiments described
above. Enhanced signal reception using redundant spectrums is
described above, and is fully described in co-pending U.S. patent
application entitled "Method and System for Ensuring Reception of a
Communications Signal," Ser. No. 09/176,415, which is incorporated
herein by reference in its entirety.
[0477] For example, in an embodiment, transmitting UPSM 3006 may
comprise a transmitter configured to transmit redundant spectrums,
and receiving UPSM 2706 may be configured to receive and process
such redundant spectrums, similarly to the system shown in FIG. 21.
In an alternative embodiment, UPM 2606 may include transceivers
configured to transmit, and to receive and process redundant
spectrums. Accordingly, the invention is directed to any of the
applications described herein in combination with any of the ESR
embodiments described herein.
[0478] These example embodiments and other alternate embodiments
(including equivalents, extensions, variations, deviations, etc.,
of the example embodiments described herein) will be apparent to
persons skilled in the relevant art(s) based on the referenced
teachings and the teachings contained herein, and are within the
scope and spirit of the present invention. The invention is
intended and adapted to include such alternate embodiments.
[0479] 8.2.5 Universal Platform Transceiver Embodiments
[0480] As discussed above, in other embodiments of the present
invention, UPM 2606 may include a transceiver unit, rather than a
separate receiver and transmitter. Furthermore, the invention is
directed to any of the applications described herein in combination
with any of the transceiver embodiments described herein.
[0481] An exemplary embodiment of a transceiving UPSM 3706 of the
present invention is illustrated in FIG. 37. Transceiving UPSM 3706
includes a UFT module 2620. In one embodiment, UPM 2606 includes
more than one transceiver UPSM 3706.
[0482] Transceiving UPSM 3706 frequency down-converts first EM
signal 2514, and outputs down-converted baseband signal 2516. In an
embodiment (not shown), each transceiving UPSM 3706 comprises one
or more UFT modules 2620 at least for frequency
down-conversion.
[0483] Transceiving UPSM 3706 frequency up-converts down-converted
baseband signal 2518. UFT module 2620 provides at least for
frequency up-conversion. In alternate embodiments, UFT module 2620
only supports frequency down-conversion, and at least one
additional UFT module 2620 provides for frequency up-conversion.
The up-converted signal is output by transceiving UPSM 3706.
[0484] Further example embodiments of receiver/transmitter systems
applicable to the present invention may be found in co-pending U.S.
patent application entitled "Method and System for Frequency
Up-Conversion," Ser. No. 09/176,154, incorporated by reference in
its entirety.
[0485] These example embodiments and other alternate embodiments
(including equivalents, extensions, variations, deviations, etc.,
of the example embodiments described herein) will be apparent to
persons skilled in the relevant art(s) based on the referenced
teachings and the teachings contained herein, and are within the
scope and spirit of the present invention. The invention is
intended and adapted to include such alternate embodiments.
[0486] Reference is made to pending U.S. application Ser. No.
"Method, System, and Apparatus for Balanced Frequency Up-conversion
of a Baseband Signal," Ser. No. 09/525,615, filed Mar. 14, 2000,
for other teachings relating to this embodiment, which is herein
incorporated by reference in its entirety.
[0487] 8.2.6 Other Universal Platform Module Embodiments
[0488] The UPM and UPSM embodiments described above are provided
for purposes of illustration. These embodiments are not intended to
limit the invention. Alternate embodiments, differing slightly or
substantially from those described herein, will be apparent to
persons skilled in the relevant art(s) based on the teachings
contained herein. Such alternate embodiments include, but are not
limited to, receiving a signal of a first modulation type and
re-transmitting the signal in a different modulation mode. Another
such alternate embodiment includes receiving a signal of a first
frequency and re-transmitting the signal at a different frequency.
Such alternate embodiments fall within the scope and spirit of the
present invention.
[0489] 8.3 Multi-Mode Infrastructure
[0490] The invention is also directed to multi-mode infrastructure
embodiments for interacting with the devices discussed above. Such
infrastructure embodiments include, but are not limited to,
servers, routers, access points, and any other components for
enabling multi-mode operation as described herein.
[0491] For example, consider a scenario of a commercial airplane.
The passengers traveling in the airplane may have devices where
they (1) receive flight information, (2) receive telephone calls,
and/or (3) receive email. There may be a number of mediums by which
such information can be received. For example, such information
might be received via a wireless telephone network, or via a WLAN
internal to the airplane, or via a short range wireless
communication medium. The airplane may have infrastructure
components to receive and route such information to the passengers'
devices. The infrastructure components include control modules for
enabling such operation.
[0492] In an embodiment, such infrastructure embodiments include
one or more receivers, transmitters, and/or transceivers that
include UFTs as described herein. In embodiments, such
infrastructure embodiments include UPMs and UPSMs as described
herein.
[0493] 8.4 Additional Multi-Mode Teachings
[0494] Additional teachings relating to multi-mode methods,
apparatuses, and systems according to embodiments of the invention
are described in the following applications (as well as others
cited above), which are all herein incorporated by reference in
their entireties:
[0495] "Family Radio System with Multi-Mode and Multi-Band
Functionality," Ser. No. 09/476,093, filed Jan. 3, 2000, Attorney
Docket No. 1744.0260001.
[0496] "Multi-Mode, Multi-Band Communications System," Ser. No.
09/476,330, filed Jan. 3, 2000, Attorney Docket No.
1744.0330001.
9. CONCLUSION
[0497] While various embodiments of the present invention have been
described above, it should be understood that they have been
presented by way of example only, and not limitation. It will be
apparent to persons skilled in the relevant art that various
changes in form and detail can be made therein without departing
from the spirit and scope of the invention. Thus, the breadth and
scope of the present invention should not be limited by any of the
above-described exemplary embodiments, but should be defined only
in accordance with the following claims and their equivalents.
* * * * *