U.S. patent application number 13/758988 was filed with the patent office on 2013-08-22 for peak-to-average power reduction method.
This patent application is currently assigned to NAUTEL LIMITED. The applicant listed for this patent is NAUTEL LIMITED. Invention is credited to Philipp Schmid, Brian Walker.
Application Number | 20130215946 13/758988 |
Document ID | / |
Family ID | 40900741 |
Filed Date | 2013-08-22 |
United States Patent
Application |
20130215946 |
Kind Code |
A1 |
Walker; Brian ; et
al. |
August 22, 2013 |
PEAK-TO-AVERAGE POWER REDUCTION METHOD
Abstract
A method of reducing peak-to-average power in a hybrid signal is
provided. The method determines peaks in power by defining a sample
point by way of a digital vector and an analog vector. The digital
and analog vectors are added together to generate a hybrid vector
which is used to compare the sample point to the maximum desired
peak threshold. An error vector is used to correct the sample point
to a desired power level. Once the sample point has been corrected
it can be added back to the analog signal and transmitted.
Inventors: |
Walker; Brian; (Halifax,
CA) ; Schmid; Philipp; (Hackett's Cove, CA) |
|
Applicant: |
Name |
City |
State |
Country |
Type |
NAUTEL LIMITED; |
|
|
US |
|
|
Assignee: |
NAUTEL LIMITED
Hackett's Cove
CA
|
Family ID: |
40900741 |
Appl. No.: |
13/758988 |
Filed: |
February 4, 2013 |
Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
|
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12810146 |
Jun 22, 2010 |
8369431 |
|
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PCT/CA2008/000169 |
Jan 25, 2008 |
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13758988 |
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Current U.S.
Class: |
375/224 |
Current CPC
Class: |
H04L 27/2614 20130101;
H04B 1/0475 20130101; H04B 2001/0416 20130101; H04L 27/2623
20130101 |
Class at
Publication: |
375/224 |
International
Class: |
H04L 27/26 20060101
H04L027/26 |
Claims
1. A method for peak-to-average power reduction in a hybrid signal
comprising first and second separately modulated signals, the
method comprising the steps of: obtaining a sample point of the
hybrid signal; defining the sample point by way of a first vector
corresponding to the first separately modulated signal and a second
vector corresponding to the second separately modulated signal;
adding the first vector to the second vector to obtain a hybrid
vector; comparing the hybrid vector against a maximum desired peak
threshold to identify peaks in power; determining an error vector
that reduces the identified peaks in power of the hybrid vector to
within the maximum desired peak threshold; adding the error vector
to the second vector to reduce at least one peak in power of the
identified peaks in power, and correcting a constellation and a
spectrum of the second modulated signal following peak
determination and peak reduction to yield a corrected second
modulated signal, wherein said correcting of the constellation and
spectrum comprises the steps of: demodulating the second separately
modulated signal; correcting all carriers in the demodulated
signal; clipping non-carriers to a mask; and modulating the
corrected second separately modulated signal.
2. The method according to claim 1, wherein the first separately
modulated signal is an analog signal and the second separately
modulated signal is a digital signal.
3. The method according to claim 2, wherein the analog signal
comprises a radio modulated baseband carrier and the digital signal
comprises orthogonal frequency division multiplexing (OFDM).
4. The method according to claim 1, further comprising a step of
oversampling the hybrid vector prior to comparing the hybrid vector
against the maximum desired peak threshold.
5. The method according to claim 1, wherein the error vector is
added to the second vector in a direction extending from an origin
of the second vector in a complex plane representation thereof.
6. The method according to claim 5, wherein the error vector is
based on a correction vector comprising a correction function that
applies a delta function to the second vector.
7. The method according to claim 6, wherein the correction function
comprises applying a shifted sine function to the second vector for
peak reduction in-between discrete sample points.
8. The method according to claim 6, wherein the correction function
comprises applying at least one complex frequency to the second
vector for tone injection at varying frequencies.
9. The method according to claim 8, wherein the at least one
complex frequency is orthogonal to symbol carriers.
10. The method according to claim 6, wherein the correction
function comprises applying at least one windowed complex frequency
to the second vector for pulse injection at varying
frequencies.
11. The method according to claim 10, wherein the at least one
windowed complex frequency limits time domain impact and increases
spectral impact.
12. The method according to claim 1, wherein the second vector has
a length, and the error vector is added to the second vector along
the length of the second vector.
13. The method according to claim 1, wherein the error vector is
calculated in parallel and opposed to the first vector.
14. The method according to claim 1, further comprising a step of
correcting a constellation and a spectrum of the error vector.
15. The method according to claim 1, further comprising a step of
adding the first separately modulated signal to a corrected second
separately modulated signal generated by correcting a constellation
and a spectrum of the second modulated signal following peak
determination and peak reduction.
16. The method according to claim 15, further comprising a step of
adding a complex random variable to the demodulated signal prior to
correcting the carriers in the demodulated signal.
17. The method according to claim 15, wherein the step of
demodulating the second separately modulated signal further
comprises: removing pulse shaping of the second separately
modulated signal; and applying a Fast Fourier Transformation
operation on the carriers in the demodulated signal.
18. The method according to claim 15, wherein the step of
modulating the corrected second separately modulated signal further
comprises: applying an Inverse Fast Fourier Transformation to the
corrected second separately modulated signal to yield a transformed
signal; and applying pulse shaping to the transformed signal.
19. A computer readable memory having recorded thereon statements
and instructions for execution by a computer adapted to carry out
the method according to claim 1.
Description
CROSS-REFERENCE TO RELATED APPLICATIONS
[0001] This application is a continuation of U.S. patent
application Ser. No. 12/810,146 filed on Jun. 22, 2010 and
subsequently issued as U.S. Pat. No. 8,369,431 on Feb. 5, 2013,
which is a U.S. national phase under 35 U.S.C. .sctn.371 of
International Patent Application No. PCT/CA2008/000169 filed on
Jan. 25, 2008. The disclosures of the foregoing patent applications
and U.S. patent are hereby incorporated by reference herein in
their respective entireties, for all purposes.
FIELD OF THE INVENTION
[0002] The present invention relates generally to a method for
reducing peak-to-average power in a hybrid signal comprising first
and second separately modulated signals. More specifically, the
invention relates to a peak-to-average power method for use on a
hybrid digital/analog radio frequency signal.
BACKGROUND OF THE INVENTION
[0003] In the United States, the In-Band On-Channel (IBOC)
technology, referred to as HD Radio.TM., has been selected by the
Federal Communication Commission to be the standard for simulcast
digital programming along with traditional analog audio at the same
frequency band. In other jurisdictions, other standards have been
adopted. For example, several European Union countries have
implemented Digital Audio Broadcasting (DAB) for FM broadcasts and
Digital Radio Mondiale (DRM) for AM broadcasts.
[0004] HD Radio.TM. IBOC technology is proprietary to iBiquity
Digital Corporation, which develops and licenses the various
components and technologies required for HD Radio.TM.. As such, the
instructions provided with the equipment and technology, and
training provided by iBiquity forms the common general knowledge in
this field and allows the technology to be put into practice.
[0005] IBOC makes use of orthogonal frequency division multiplexing
(OFDM) signalling. While it can be shown that OFDM provides
substantial benefits in digital wireless communications, one of its
main disadvantages is the fact that in the time domain the
multitude of subcarriers add constructively or destructively almost
at random. This produces a time domain signal with widely varying
power.
[0006] A high level combined broadcast transmission system takes
the output from a full power analog transmitter and combines it
with the signal from a linear digital transmitter before sending it
to the antenna. In this case, the digital power amplifier must be
able to handle the full range of the digital signal's power
fluctuation. In order to make IBOC deployments economically
feasible, peak-to-average power (PAPR) algorithms have been
developed to reduce the power peaks in the digital signal. For
example, U.S. Pat. No. 6,128,350 to Shastri et al., and US Patent
Publication No. 2005/0169411 to Kroeger both describe PAPR
algorithms for use on the digital signal in IBOC systems. These
standard algorithms effectively brings the original 12 dB PAPR
under 8 dB by solely operating on the digital signal.
[0007] Conversely, a low level combined broadcast transmission
system consists of a single combined power amplification chain. In
this case the analog and digital signals are added as digital
complex baseband signals. The addition of the analog signal to the
digital signal generates a hybrid signal and alters the power
characteristics of the combined signal.
[0008] FIGS. 1A-1C illustrate a complex plane, where the X-axis
reflects the baseband signal's real (or in phase--I) component and
the Y-axis represents the signal's imaginary (or quadrature--Q)
component. As shown in FIG. 1A, the output of the FM modulation
process produces a constant envelope signal with varying phase. At
baseband, this signal is represented as a vector 120 in the complex
plane with constant amplitude, which is represented by a circle
107. Any given sample point can be represented by an additive
vector 110, which represents the possible amplitude and phase of
the additive digital signal.
[0009] In theory, as shown in FIG. 1B, the standard PAPR reduction
scheme creates a circle 140 having a radius that is equal to or
less than the distance between the constant FM signal level and the
maximum desired peak threshold 112. Only sample points that fall
within this circle 140 can be certain not to add to the analog
signal 102 constructively, and thus do not require correction.
However, all sample points that fall outside of the circle 140 will
require correction to a point within the circle 140. For example,
sample points 150, 151 and 152, defined by digital vectors 110A,
110B and 110C, respectively, will all require correction to be
within the confines of circle 140.
[0010] However, this form of peak detection results in the digital
signal being unnecessary corrected in a variety of circumstances
and large corrections being applied when much less correction is
required. For example, as shown in FIG. 1C, sample point 152
defined by digital vector 110B would be corrected by correction
vector 160, when in fact no correction would be necessary, since
the actual sample point 152 would fall below the maximum desired
threshold 112.
[0011] Sample point 150, defined by digital vector 110C,
illustrates the situation where a large correction would be applied
to a sample point requiring only a small correction. In this
example, digital vector 110C projects to a point 150 that is just
beyond the maximum desired peak threshold 112. In the standard PAPR
reduction scheme, a large correction 161 would be applied to this
vector 110C to bring the sample point into the circle 140, whereas
in reality a small correction function could have been used to
bring the sample point 150 below the maximum desired peak threshold
112. Only in circumstances where the digital vector could add to
the analog vector in-phase to generate a maximum peak does the
current PAPR reduction scheme apply proper clipping or correction.
For example, sample point 151 defined by digital vector 110A
generates a maximum peak, in which a proper correction vector 162
is applied.
[0012] Accordingly, there is a need to develop a method that does
not unnecessarily reduce peaks in power that fall within the
maximum desired peak threshold and therefore overcomes the
limitations of the prior art.
SUMMARY OF THE INVENTION
[0013] It is an object of the present invention to provide a peak
detection method that overcomes the limitations of the prior art
and is applied to a hybrid signal.
[0014] It is a further object of the present invention to provide a
method for peak detection that takes into account the contribution
of each separately modulated signal and uses this information in
reducing the PAPR in the hybrid signal.
[0015] According to an aspect of the present invention there is
provided a method for peak-to-average power reduction in a hybrid
signal comprising first and second separately modulated signals,
the method comprising the steps of: obtaining a sample point of the
hybrid signal; defining the sample point by way of a first vector
corresponding to the first separately modulated signal and a second
vector corresponding to the second separately modulated signal;
adding the first vector to the second vector to obtain a hybrid
vector; comparing the hybrid vector against a maximum desired peak
threshold to identify peaks in power; and adding an error vector to
the second vector to reduce the peak.
BRIEF DESCRIPTION OF THE DRAWINGS
[0016] These and other features, aspects and advantages of the
present invention will become better understood with regard to the
following description and accompanying drawings wherein:
[0017] FIG. 1A is a complex plane, where the X-axis reflects the in
phase (1) component and the Y-axis represents the signal's
quadrature (Q) component;
[0018] FIG. 1B is a complex plane depicting the addition of a
digital vector to an analog vector in accordance with the prior
art;
[0019] FIG. 1C is a complex plane depicting correction of the
digital vectors in accordance with the prior art;
[0020] FIG. 2 is a block diagram of the peak-to-average power
scheme of the present invention;
[0021] FIG. 3A is a complex plane depicting the addition of a
digital vector to an analog vector in accordance with an embodiment
of the present invention; and
[0022] FIG. 3B is a complex plane depicting the correction of the
hybrid vector in accordance with an embodiment of the present
invention.
DETAILED DESCRIPTION OF THE INVENTION
[0023] The following description is of one particular embodiment by
way of example only and without limitation to the combination of
features necessary for carrying the invention into effect.
[0024] As a representative example, description of the method is
given using hybrid FM IBOC broadcast transmission. However, persons
of ordinary skill in the art will readily understand that the
general method, software and system can be applied to other hybrid
transmission schemes that add two separately modulated signals,
such as an OFDM signal and an existing transmission standard.
[0025] It should be also noted that the present invention can be
carried out as a method, can be embodied in a system, a computer
readable medium or an electrical or electro-magnetic signal.
[0026] As shown in FIG. 2, in a standard low level combined
broadcast transmission system, the digital and analog signals 101,
102 of the FM IBOC broadcast transmission converge to form a hybrid
signal. Each signal 101 and 102 is separately modulated prior to
convergence. In the present example, the digital signal 101 is
modulated in accordance with an IBOC modulation scheme and the
analog signal is modulated using a standard frequency modulation
scheme. Peaks are detected, as shown by block 190, by taking sample
points within the hybrid signal and comparing them against the
maximum desired peak threshold.
[0027] Any peak detected is then reduced, as shown by block 191, to
below the maximum desired peak threshold. From this point the
signal may be further corrected by spectrum and constellation
correction 192 or passed forward without further correction to the
next step in the broadcast stream. Several iterations of the method
can take place before the digital and analog signals 101, 102 are
recombined, as shown by block 193, to be output as a hybrid signal
(block 194).
[0028] In this low level combined broadcast system, it has been
found that if the hybrid signal is also modulated, then a PAPR of
around 3 dB can be achieved even with an increase in carrier levels
of up to 10 dB. Comparatively, using the standard IBOC PAPR
methods, as described in Shastri et al., (U.S. Pat. No. 6,128,350)
and Kroeger (US 2005/0169411), a transmitter capable of handling a
PAPR of up to 4.5 dB will be required to accommodate the 10 dB
increase in digital carrier levels. This will result in a dramatic
increase in transmitter overhead.
[0029] The standard PAPR reduction methods developed for IBOC
broadcast transmission, such as Shastri et al., (U.S. Pat. No.
6,128,350) and Kroeger (US 2005/0169411), are sub-optimal for use
on the hybrid signal 100. This is in part due to the fact that
applying the PAPR reduction algorithms of Shastri et al., (U.S.
Pat. No. 6,128,350) and Kroeger (US 2005/0169411) on the hybrid
signal 100 would obliterate the analog signal 102 content. In order
for PAPR reduction to take place on the hybrid signal 100 the
sections of the signal that contribute to the development of a peak
should be identified.
[0030] According to the present invention a signal peak, which is
defined as a sample point exceeding a maximum desired threshold, is
determined by adding the analog vector to the digital vector. The
resultant hybrid vector is then thresholded against the maximum
desired peak threshold. If the digital signal adds constructively
to the analog signal, then a large correction will be required. A
smaller correction is needed, if the vector addition falls close to
the maximum desired peak and no correction is required if the
digital signal adds destructively to the analog signal and
resultant hybrid vector projects below the maximum desired peak
threshold.
[0031] As shown in FIG. 3A, addition of a digital vector 110 to the
analog vector 109 generates a circular area 113 around the analog
signal point 170. The area of the circle 113 can be further divided
into two sections, namely a no correction area 114 and a correction
area 116. Within correction area 116, a gradient relating to the
amount of correction to be applied covers the area with a large
amount of correction required near the section where the digital
vector 110A would add to the analog vector 109 in-phase. The amount
of correction required would gradually drop off as the digital
vector 110A moved away from the maximum addition situation.
According to the present invention, only if the sample point falls
within the corrections area 116 will a correction be applied to the
signal. However, a majority of the area of the circle defined by
the hybrid vector 111 will not require a correction, since the
sample points will fall below the maximum desired peak threshold
112. For example, as shown in FIG. 3B, sample point 180 falls below
the maximum desired peak threshold 112. Since the sample point 180
is defined by the hybrid vector 111 A, no correction is required
since the vector 111A projects outside the correction areas 115 and
116. Conversely, using the standard PAPR reduction scheme, the same
sample point would be unnecessarily clipped to within the circle
140 (see FIG. 1C).
[0032] If a sample point falls within the correction area 116, near
the maximum desired threshold 112, a lower amount of correction
will be required to bring the signal below the maximum desired peak
threshold 112. For example, sample point 181, shown in FIG. 3B is
slightly higher than the maximum desired peak threshold 112. Since
the sample point 181 is defined by the hybrid vector 111B, only a
slight correction is required, along the hybrid vector 111B, to
bring clip the sample below the maximum desired peak threshold 112.
By introducing a lower amount of correction, the peak detection
method of the present invention can achieve the same maximum
desired peak value with a lower degree of distortion in the
original signal. This allows the signal peak to be reduced further
compared to the standard method of PAPR applied only to the digital
signal 101.
[0033] In situations where the hybrid vector 111 projects
essentially in the same direction as the analog and digital vectors
109, 110, a large correction, essentially the same as with the
standard PAPR reduction scheme, will be required.
[0034] Once the peaks have been detected, a reduction algorithm is
applied to reduce the peaks to a point below the maximum desired
peak threshold 112. In typical PAPR reduction schemes, peaks are
reduced by adding a correction vector to the digital vector to thus
reduce the magnitude of the sample point to below the maximum
desired peak threshold (see FIG. 1C). In the case where a hybrid
vector is used to detect the signal peaks, adding a correction
vector to the hybrid vector will be sub-optimal for the eventual
constellation and spectrum correction steps. Accordingly, peak
correction is achieved by adding an error vector, based on the
correction vector, to the digital vector component of the hybrid
vector.
[0035] In the method, one threshold is used to make a decision to
correct the signal and another value determines the amount of
correction to be applied. This allows the peak to be over-clipped
to ensure that it will not come back to such a level during the
correction phase.
[0036] The person skilled in the art will readily appreciate that
the signal can be corrected using any number of correction
functions known in the art. For example, the correction function
can be accomplished by either hard or soft clipping the digital
signal portion of the hybrid signal. Hard or soft clipping adds a
delta function defined by .delta.(t) e.sup.j.PHI. to the digital
signal, where .PHI. represents the angle of the correction
vector.
[0037] In another embodiment, the correction function may be a real
or complex function, such as a complex frequency. However, the
correction function should present a real point at the peak to be
corrected, so that the correction angle .PHI. can be added to the
point.
[0038] It may also be possible to compute the correction vector in
parallel but opposed to the analog vector so as to preserve the
phase of the analog vector. This introduces asynchronous noise to
the FM modulated signal, but would allow the frequency space of the
analog signal to be employed for peak correction.
[0039] A sin c ( ) function may be included in the generalized peak
correction formula to allow for the delta function to be applied to
the integer sample points, but can be used to shift the delta
function to lie between sample points, should the actual peak not
fall on discrete sample points. This can reduce the need to operate
on an oversampled signal and may prove to be computationally more
effective.
[0040] In one embodiment, additional oversampling for the peak
detection step may be beneficial and even may allow the overall
oversampling factor to be omitted. If a peak is detected in between
samples, the correction function must be shifted accordingly. In
the case of clipping using a delta function, the sin c ( ) function
of the correction function is shifted, which provides non-zero time
domain values across a larger time window.
[0041] Based on the correction vector, an error signal
(representing an error from the original signal) can be generated
by the following general formula:
E [ n ] = K = O length - 1 correctionFunction [ n - k ] C [ k ]
##EQU00001##
[0042] The introduction of an error signal based on the formula
identified above, allows alternate means of peak correction, such
as tone injection or pulse injection. Furthermore, the correction
function may even be determined adaptively and may not be the same
or even static across iterations or individual peaks.
[0043] In order to limit the possibility of the peak re-emerging
while correcting the constellation and spectrum, the correction
vector can be extended further than normal using the above
formulas. Further, the correction vector may be computed along the
original digital vector, rather than to the origin. This would
allow the phase of the digital signal to be preserved.
[0044] The use of an error signal to correct the hybrid signal
allows the shape of the spectrum to be controlled, such that it
requires less eventual constellation and spectrum correction.
Furthermore, additional frequency spectrum may be used to more
effectively reduce peaks. For example, if the extended carrier
spectrum is not used for data carriers, it can be used to hold a
larger portion of the error signal. Depending on the choice of
correction function, the error signal can be small enough that the
constellation and spectrum correction step may be bypassed
altogether.
[0045] Modification of the digital signal in the time domain can
negatively impact the signal constellation, as well as increase
out-of-band noise requiring correction. Unlike the standard PAPR
reduction scheme, different correction functions in the proposed
method will have varying impacts on the constellation and injected
noise level. Some correction functions, such as tone injection, may
safely bypass the constellation and spectrum correction step.
[0046] The constellation and spectrum correction is applied to a
modified version of the digital signal. Alternatively, the combined
error vector, without addition to the digital vector, may be
tracked and a comparable constellation and spectrum correction
applied thereto. This would permit the original digital signal to
pass through the steps in an unmodified form until the error vector
is finally added to the digital signal. Moreover, performing
correction on the error vector rather than the digital vector
allows alternate means of constellation correction. For example,
any of the QPSK constellation points could be rotated back in a
desired boundary region rather than pushing points along the X and
Y axes.
[0047] The basic steps of constellation and spectrum correction
involve: removing the pulse shaping of the IBOC signal; performing
an Fast Fourier Transformation (FFT) operation to demodulate the
OFDM carriers; applying a frequency mask that zeros or reduces
frequency bins not assigned to IBOC carriers; constraining the
constellation of IBOC carrier points back toward the actual signal
point up to a threshold value along both the real and imaginary
axes; correcting the phase of all reference carriers; computing the
Inverse Fast Fourier Transformation (IFFT) to re-modulate the
signal; and re-applying pulse shaping to the symbol.
[0048] The correction of the constellation points should be
performed with respect to the original Quadrature Phase Shift Keyed
(QPSK) point. Basing the correction on the modified symbol itself
can lead to bit errors, as the applied correction function could
have moved the constellation point into another decision
region.
[0049] The process may operate at sample rates greater than the
standard modulator sample rate in order to detect signal peaks more
accurately. The analog FM modulated signal is interpolated to that
rate, while the digital signal is passed to the process in terms of
carrier bitmap describing the QPSK constellation. Each carrier is
represented in terms of the sign bits of the real and imaginary
parts of the constellation point. An oversampled IBOC time domain
symbol can be determined by filling in the constellation points
based on the bitmap and inserting a zero vector prior to the IFFT
step. Standard IBOC pulse shaping can be performed at the output.
The carrier bitmap can also be used as a reference in the
constellation/spectrum correction step later on.
[0050] The digital signal is operated on and passed forward across
iterations, but the analog signal is stored across iterations. Only
on the final iteration of the method is the analog signal added to
the digital signal in a permanent manner. Provided that the signal
content in the FM spectrum is minimized or shaped such as to have
little impact on the FM signal, then the distortion on the FM
signal is minimal.
[0051] During peak reduction, the Root Mean Square (RMS) level of
the digital signal is often reduced. As shown by block 300 in FIG.
3, by scaling the digital signal back to the original RMS level,
the signal power can be maintained. In addition, the boundary
region of the constellation during the constellation correction
step is relaxed.
[0052] Optionally, each digital carrier may be equalized in both
amplitude and phase using conventional equalization techniques. In
this case the analog signal must be equalized prior to passing it
through the PAPR reduction method and the resultant analog and
digital signal should not be equalized in subsequent steps as this
may change the peak characteristics.
[0053] In an embodiment, a complex random variable can be added to
the standard constellation correction prior to correction. Adding a
random variable may aid in finding a better solution across
multiple iterations, since correction is in opposition to the peak
reduction step.
[0054] As a final step in the spectrum and constellation correction
method each IBOC symbol can be scaled so that each peak has a
constant power within each symbol and to limit variability from
symbol to symbol. The scaling level should be chosen at the median
peak level such that half the symbols are scaled up and improve
their constellation and half the symbols are scaled down with a
slight degradation in their constellation. This additional step
should assist in the predistortion process as peaks now occur at a
fixed rate.
[0055] Keeping the algorithm parameters adaptive allows the
algorithm to be adaptively configured for different levels of peak
compression based on external input parameters. For example, if a
transmitter is temporarily unable to produce a given peak power
level, peaks may be compressed harder at a slight degradation in
the signal constellation, but maintaining the same signal
power.
[0056] It will be understood that numerous modifications thereto
will appear to those skilled in the art. Accordingly, the above
description and accompanying drawings should be taken as
illustrative of the invention and not in a limiting sense. It will
further be understood that it is intended to cover any variations,
uses, or adaptations of the invention following, in general, the
principles of the invention and including such departures from the
present disclosure as come within known or customary practice
within the art to which the invention pertains and as may be
applied to the essential features herein before set forth, and as
follows in the scope of the appended claims.
INDUSTRIAL APPLICABILITY
[0057] The present method will allow existing hybrid installations
to increase their carrier levels without needing to upgrade their
entire transmitter. In addition, the present method improves the
overall efficiency of the transmitter, and will have a positive
economic impact for broadcasters.
* * * * *