U.S. patent application number 13/646012 was filed with the patent office on 2013-06-20 for methods and apparatuses for adaptively controlling antenna parameters to enhance efficiency and maintain antenna size compactness.
The applicant listed for this patent is Frank M. Caimi, Ping Chen, Young-Min Jo, Gregory A. O'Neill, JR.. Invention is credited to Frank M. Caimi, Ping Chen, Young-Min Jo, Gregory A. O'Neill, JR..
Application Number | 20130154894 13/646012 |
Document ID | / |
Family ID | 46327052 |
Filed Date | 2013-06-20 |
United States Patent
Application |
20130154894 |
Kind Code |
A1 |
Caimi; Frank M. ; et
al. |
June 20, 2013 |
METHODS AND APPARATUSES FOR ADAPTIVELY CONTROLLING ANTENNA
PARAMETERS TO ENHANCE EFFICIENCY AND MAINTAIN ANTENNA SIZE
COMPACTNESS
Abstract
A communications apparatus. The apparatus comprises a
transmitting antenna, a receiving antenna, a first serial
configuration of a first power amplifier and a first matching
network for producing a first signal, the first power amplifier
operating in a first frequency band, a second serial configuration
of a second power amplifier and a second matching network for
producing a second signal, the second power amplifier operating in
a second frequency band, a first switching element for switchably
supplying the first signal or the second signal to the transmitting
antenna, a first and a second receiver; and a second switching
element for switchably directing a signal received at the receiving
antenna to the first receiver or the second receiver.
Inventors: |
Caimi; Frank M.; (Vero
Beach, FL) ; O'Neill, JR.; Gregory A.; (Rockledge,
FL) ; Chen; Ping; (Greensboro, NC) ; Jo;
Young-Min; (Viera, FL) |
|
Applicant: |
Name |
City |
State |
Country |
Type |
Caimi; Frank M.
O'Neill, JR.; Gregory A.
Chen; Ping
Jo; Young-Min |
Vero Beach
Rockledge
Greensboro
Viera |
FL
FL
NC
FL |
US
US
US
US |
|
|
Family ID: |
46327052 |
Appl. No.: |
13/646012 |
Filed: |
October 5, 2012 |
Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
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13209707 |
Aug 15, 2011 |
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13646012 |
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11623307 |
Jan 15, 2007 |
8000737 |
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13209707 |
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11421878 |
Jun 2, 2006 |
7834813 |
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11623307 |
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11252248 |
Oct 17, 2005 |
7663555 |
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11421878 |
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60619231 |
Oct 15, 2004 |
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Current U.S.
Class: |
343/858 |
Current CPC
Class: |
H01Q 9/0421 20130101;
H01Q 1/50 20130101; H01Q 9/0442 20130101; H01Q 1/243 20130101; H01Q
9/045 20130101; Y10T 29/49016 20150115 |
Class at
Publication: |
343/858 |
International
Class: |
H01Q 1/50 20060101
H01Q001/50 |
Claims
1. A communications apparatus comprising: a transmitting antenna; a
receiving antenna; a first serial configuration of a first power
amplifier and a first matching network for producing a first
signal, the first power amplifier operating in a first frequency
band; a second serial configuration of a second power amplifier and
a second matching network for producing a second signal the second
power amplifier operating in a second frequency band; a first
switching element for switchably supplying the first signal or the
second signal to the transmitting antenna; a first receiver; a
second receiver; and a second switching element for switchably
directing a signal received at the receiving antenna to the first
receiver or the second receiver.
2. The communications apparatus of claim 1 further comprising an
isolation structure intermediate the transmitting antenna and the
receiving antenna.
3. The communications apparatus of claim 2 wherein the isolation
structure further comprises a conductive structure disposed between
the transmitting antenna and the receiving antenna.
4. The communications apparatus of claim 1 further comprising a
dielectric substrate, wherein the transmitting and the receiving
antennas each comprise a conductive structure disposed on the
dielectric substrate and the isolation structure comprises a
conductive structure disposed between the transmitting and the
receiving antennas.
5. The communications apparatus of claim 1 wherein a signal
polarization of the transmitting antenna is different from a signal
polarization of the receiving antenna.
6. The communications apparatus of claim 1 wherein the first
matching network presents a load impedance to the first power
amplifier responsive to a power-related parameter of the first
power amplifier and the second matching network presents a load
impedance to the second power amplifier responsive to a
power-related parameter of the second power amplifier.
7. The communications apparatus of claim 6 wherein the
power-related parameter of the first power amplifier or the
power-related parameter of the second power amplifier comprises a
power amplifier output power, an operating frequency of the
communications device or a voltage standing wave ratio on a
conductive path between the power amplifier and the transmitting
antenna.
8. The communications apparatus of claim 6 wherein the load
impedance presented by the first matching network to the first
power amplifier for controlling an efficiency or a power added
efficiency of the first power amplifier signal and the load
impedance presented by the second matching network to the second
power amplifier for controlling an efficiency or a power added
efficiency of the second power amplifier.
9. The communications apparatus of claim 1 wherein the first
matching network comprises a controllable first matching network
for presenting a controllable load impedance to the first power
amplifier responsive to a power-related parameter of the first
power amplifier, and wherein the second matching network comprises
a controllable second matching network for presenting a
controllable load impedance to the second power amplifier
responsive to a power-related parameter of the second power
amplifier.
10. A communications apparatus comprising: a first antenna having a
resonant frequency in a first frequency band; a second antenna
having a resonant frequency in a second frequency band; a first and
a second power amplifier respectively supplying a first and a
second signal for transmitting; a switching element for switchably
supplying the first or the second signal for transmitting to the
first antenna or to the second antenna responsive to the frequency
of the first and the second signal for transmitting; and an
impedance controller for controlling the impedance of the first and
the second antennas responsive to a power-related parameter.
11. The communications apparatus of claim 10 further comprising a
first and a second receiver connected to the switching element for
supplying a signal received at the first or the second antenna to
the first or the second receiver responsive to a frequency of the
signal received at the first or the second antenna.
12. The communications apparatus of claim 10 wherein the impedance
controller controls the impedance of the first and the second
antennas responsive to the respective power related parameter of
the first and the second power amplifier to control the power added
efficiency or the efficiency of the first and the second power
amplifiers.
13. The communications apparatus of claim 10 further comprising a
first and a second matching network disposed between the respective
first and second power amplifiers and the switching element, the
first and the second matching networks and the impedance controller
operative to control the power added efficiency or the efficiency
of the first and the second power amplifiers.
14. The communications apparatus of claim 10 wherein the first and
the second matching networks and the impedance controller cooperate
to control a load impedance of the first and the second power
amplifiers to broaden a signal bandwidth of the first and the
second signals for transmitting.
15. The communications apparatus of claim 10 wherein the impedance
controller controls the impedance of the first and the second
antennas by controlling lumped reactive components or distributed
reactive components operative with the first or the second
antenna.
16. A communications apparatus comprising: a first antenna having a
resonant frequency in a first frequency band; a second antenna
having a resonant frequency in a second frequency band, the first
and the second antennas presenting an antenna impedance less than
about 50 ohms at a respective resonant frequency; a signal combiner
connected to the first and the second antennas; a first and a
second power amplifier respectively supplying a first and a second
signal for transmitting; and a first switching element for
switchably supplying the first or the second signal for
transmitting to the signal combiner, the signal combiner supplying
the first or the second signal for transmitting to the first
antenna or to the second antenna responsive to the frequency of the
first and the second signal for transmitting; and a first and a
second matching network disposed between the respective first and
second power amplifiers and the switching element, the first and
the second matching networks operative to control the power added
efficiency or the efficiency of the first and the second power
amplifiers.
17. The communications apparatus of claim 16 further comprising a
first and a second receiver connected to the first switching
element for supplying a signal received at the first or the second
antenna to the first or the second receiver responsive to a
frequency of the signal received at the first or the second
antenna.
18. The communications apparatus of claim 16 wherein the first and
the second matching networks control the power added efficiency or
the efficiency of the first and the second power amplifiers
according to a power-related parameter.
19. The communications apparatus of claim 18 wherein the
power-related parameter comprises a power amplifier output power,
an operating frequency of the communications apparatus or a voltage
standing wave ratio.
20. An antenna for use in a communications device, comprising: one
or more resonant elements presenting a first resonant frequency
responsive to operation of the communications device in a first
frequency band, wherein the first resonant frequency is within a
highest frequency band in which the communications device is
capable of operating; and an antenna controller for controlling one
or more antenna operating parameters to present a second resonant
frequency responsive to operation of the communications device in a
second frequency band.
21. The antenna of claim 20 wherein the operating parameters
comprise one of resonant frequency and antenna terminal
impedance.
22. The antenna of claim 20 wherein operation in the first
frequency band is at a first power level and operation in the
second frequency band is at a second power level different from the
first power level.
Description
[0001] This continuation application claims the benefit of the
United States patent application assigned application Ser. No.
13/209,707, filed on Aug. 15, 2011, which is a continuation
application claiming the benefit of the United States patent
application assigned application Ser. No. 11/623,307, filed on Jan.
15, 2007, (now U.S. Pat. No. 8,000,737), which is a
continuation-in-part application claiming the benefit of United
States patent application assigned application Ser. No. 11/421,878,
filed on Jun. 2, 2006 (now U.S. Pat. No. 7,834,813), which is a
continuation-in-part application claiming the benefit of United
States patent application assigned application Ser. No. 11/252,248
filed on Oct. 17, 2005 (now U.S. Pat. No. 7,663,555), which claims
the benefit of the Provisional Patent Application No. 60/619,231
filed on Oct. 15, 2004.
FIELD OF THE INVENTION
[0002] The present invention is related generally to antennas for
wireless communications devices and specifically to methods and
apparatuses for adaptively controlling antenna parameters to
improve performance of the communications device.
BACKGROUND OF THE INVENTION
[0003] It is known that antenna performance is dependent on the
size, shape and material composition of the antenna elements, the
interaction between elements and the relationship between certain
antenna physical parameters (e.g., length for a linear antenna and
diameter for a loop antenna) and the wavelength of the signal
received or transmitted by the antenna. These physical and
electrical characteristics determine several antenna operational
parameters, including input impedance, gain, directivity, signal
polarization, resonant frequency, bandwidth and radiation pattern.
Since the antenna is an integral element of a signal receive and
transmit path of a communications device, antenna performance
directly affects device performance.
[0004] Generally, an operable antenna should have a minimum
physical antenna dimension on the order of a half wavelength (or a
multiple thereof) of the operating frequency to limit energy
dissipated in resistive losses and maximize transmitted or received
energy. Due to the effect of a ground plane image, a quarter
wavelength antenna (or odd integer multiples thereof) operative
above a ground plane exhibits properties similar to a half
wavelength antenna. Communications device product designers prefer
an efficient antenna that is capable of wide bandwidth and/or
multiple frequency band operation, electrically matched (e.g.,
impedance matching) to the transmitting and receiving components of
the communications system, and operable in multiple modes (e.g.,
selectable signal polarizations and selectable radiation
patterns).
[0005] The half-wavelength dipole antenna is commonly used in many
applications. The radiation pattern is the familiar donut shape
with most of the energy radiated uniformly in the azimuth direction
and little radiation in the elevation direction. Frequency bands of
interest for certain communications devices are 1710 to 1990 MHz
and 2110 to 2200 MHz. A half-wavelength dipole antenna is
approximately 3.11 inches long at 1900 MHz, 3.45 inches long at
1710 MHz, and 2.68 inches long at 2200 MHz. The typical gain is
about 2.15 dBi.
[0006] The quarter-wavelength monopole antenna disposed above a
ground plane is derived from the half-wavelength dipole. The
physical antenna length is a quarter-wavelength, but interaction of
the electromagnetic energy with the ground plane (creating an image
antenna) causes the antenna to exhibit half-wavelength dipole
performance. Thus, the radiation pattern for a monopole antenna
above a ground plane is similar to the half-wavelength dipole
pattern, with a typical gain of approximately 2 dBi.
[0007] The common free space (i.e., not above ground plane) loop
antenna (with a diameter of approximately one-third the wavelength
of the transmitted or received frequency) also displays the
familiar donut radiation pattern along the radial axis, with a gain
of approximately 3.1 dBi. At 1900 MHz, this antenna has a diameter
of about 2 inches. The typical loop antenna input impedance is 50
ohms, providing good matching characteristics to the standard 50
ohm transmission line.
[0008] The well-known patch antenna provides directional
hemispherical coverage with a gain of approximately 4.7 dBi.
Although small compared to a quarter or half wavelength antenna,
the patch antenna has a relatively narrow bandwidth. The small size
is only attributable to the velocity of propagation associated with
the dielectric material used between the plates of the patch
antenna.
[0009] Given the advantageous performance of quarter and half
wavelength antennas, conventional antennas are typically
constructed so that the antenna length is on the order of a quarter
wavelength of the radiating frequency and the antenna is operated
over a ground plane, or the antenna length is a half wavelength
without employing a ground plane. These dimensions allow the
antenna to be easily excited and operated at or near a resonant
frequency (where the resonant frequency (f) is determined according
to the equation c=.lamda.f, where c is the speed of light and
.lamda. is the wavelength of the electromagnetic radiation). Half
and quarter wavelength antennas limit energy dissipated in
resistive losses and maximize the transmitted energy. But as the
operational frequency increases/decreases, the operational
wavelength decreases/increases and the antenna element dimensions
proportionally decrease/increase. In particular, as the resonant
frequency of the received or transmitted signal decreases, the
dimensions of the quarter wavelength and half wavelength antenna
proportionally increase. The resulting larger antenna, even at a
quarter wavelength, may not be suitable for use with certain
communications devices, especially portable and personal
communications devices intended to be carried by a user. Since
these antennas tend to be larger than the communications device,
they are typically mounted with a portion of the antenna protruding
from the communications device and thus are susceptible to
breakage.
[0010] The burgeoning growth of wireless communications devices and
systems has created a substantial need for physically smaller, less
obtrusive, and more efficient antennas that are capable of wide
bandwidth or multiple frequency-band operation, and/or operation in
multiple modes (i.e., selectable radiation patterns or selectable
signal polarizations). For example, operation in multiple frequency
bands may be required for operation of the communications device
with multiple communications systems or signal protocols within
different frequency bands. For example, a cellular telephone system
transmitter/receiver and a global positioning system receiver
operate in different frequency bands using different signal
protocols. Operation of the device in multiple countries also
requires multiple frequency band operation since communications
frequencies are not commonly assigned in different countries.
[0011] Smaller packaging of state-of-the-art communications
devices, such as personal communications handsets, does not provide
sufficient space for the conventional quarter and half wavelength
antenna elements. Physically smaller antennas operable in the
frequency bands of interest (i.e., exhibiting multiple resonant
frequencies and/or wide bandwidth to cover all operating
frequencies of the communications device) and providing the other
desired antenna-operating properties (input impedance, radiation
pattern, signal polarizations, etc.) are especially sought
after.
[0012] As is known to those skilled in the art, there is a direct
relationship between physical antenna size and antenna gain, at
least with respect to a single-element antenna, according to the
relationship: gain=(.beta.R) 2+2.beta.R, where R is the radius of
the sphere containing the antenna and .beta. is the propagation
factor. Increased gain thus requires a physically larger antenna,
while users continue to demand physically smaller handsets that in
turn require smaller antennas. As a further constraint, to simplify
the system design and strive for minimum cost, equipment designers
and system operators prefer to utilize antennas capable of
efficient multi-band and/or wide bandwidth operation to allow the
communications device to access various wireless services operating
within different frequency bands or such services operating over
wide bandwidths. Finally, gain is limited by the known relationship
between the antenna operating frequency and the effective antenna
electrical length (expressed in wavelengths). That is, the antenna
gain is constant for all quarter wavelength antennas of a specific
geometry i.e., at that operating frequency where the effective
antenna length is a quarter of a wavelength of the operating
frequency.
[0013] To overcome the antenna size limitations imposed by handset
and personal communications devices, antenna designers have turned
to the use of so-called slow wave structures where the structure's
physical dimensions are not equal to the effective electrical
dimensions. Recall that the effective antenna dimensions should be
on the order of a half wavelength (or a quarter wavelength above a
ground plane) to achieve the beneficial radiating and low loss
properties discussed above. Generally, a slow-wave structure is
defined as one in which the phase velocity of the traveling wave is
less than the free space velocity of light. The wave velocity (c)
is the product of the wavelength and the frequency and takes into
account the material permittivity and permeability, i.e.,
c/((sqrt(.di-elect cons..sub.r)sqrt(.mu..sub.r))=.lamda.f. Since
the frequency does not change during propagation through a slow
wave structure, if the wave travels slower (i.e., the phase
velocity is lower) than the speed of light, the wavelength within
the structure is lower than the free space wavelength. The
slow-wave structure de-couples the conventional relationship
between physical length, resonant frequency and wavelength.
[0014] Since the phase velocity of a wave propagating in a
slow-wave structure is less than the free space velocity of light,
the effective electrical length of these structures is greater than
the effective electrical length of a structure propagating a wave
at the speed of light. The resulting resonant frequency for the
slow-wave structure is correspondingly increased. Thus if two
structures are to operate at the same resonant frequency, as a
half-wave dipole, for instance, then the structure propagating a
slow wave will be physically smaller than the structure propagating
a wave at the speed of light. Such slow wave structures can be used
as antenna elements or as antenna radiating structures.
[0015] As designers of portable communications devices (e.g.,
cellular handsets) continue to shrink device size while offering
more operating features, the requirements for antenna performance
become more stringent. Achieving the next level of performance for
such communications devices requires smaller antennas with improved
performance, especially with respect to radiation efficiency.
Currently, designers struggle to obtain adequate multi-band antenna
performance for the multi-band features of the devices. But as is
known, efficiency and bandwidth are related and a design trade-off
is therefore required. Designers can optimize performance in one
(or in some cases more than one) operating frequency band, but
usually must compromises the efficiency or bandwidth to achieve
adequate performance in two or more bands simultaneously. However,
most portable communications devices seldom require operation in
more than one band at any given time.
[0016] In addition, modern portable communications devices must
maintain size compactness and high efficiency while still
attempting to provide adequate operating time with a limited
battery resource. Antenna compactness and efficiency are therefore
crucial to achieving commercially viable wireless devices.
[0017] The known Chu-Harrington relationship relates the size and
bandwidth of an antenna. Generally, as the size decreases the
antenna bandwidth also decreases. But to the contrary, as the
capabilities of handset communications devices expand to provide
for higher data rates and the reception of bandwidth intensive
information (e.g., streaming video), the antenna bandwidth must be
increased.
[0018] Current wireless communications devices operating according
to the various common communications signal protocols, e.g., GSM,
EDGE, CDMA, Bluetooth. 802.11x and, UWB and WCDMA, suffer operating
deficiencies as set forth below. [0019] A. Poor power amplifier
(PA) efficiency due to sub-optimal PA load impedance (where the
antenna impedance is the PA load impedance) as the PA's output
power changes during operation of the communications device and as
the antenna impedance change as the signal frequency changes.
[0020] B. Poor PA efficiency as set forth in A. above as further
affected by the antenna's relatively narrow bandwidth due its
relatively small size to fit within the available space envelope of
the communications device (i.e., the Chu-Harrington limitation).
[0021] C. Poor PA efficiency due to a sub-optimal PA load impedance
as the hand-effect or proximity effect detunes the antenna resonant
frequency and/or modifies the antenna impedance. [0022] D. Loss of
radiative energy transfer (coupling efficiency) due to a
sub-optimal PA output impedance (i.e., a sub-optimal antenna
impedance) due to the use of a relatively small antenna and it
corresponding relatively narrow bandwidth. [0023] E. Loss of
radiative energy transfer (coupling efficiency) due to detuning of
the antenna resonant frequency caused by the hand-effect or
proximity effect. [0024] F. Poor PA efficiency due to impedance
transformation to a higher value (i.e., 50 ohms) versus a lower
value closer to the natural radiation resistance of the antenna.
[0025] G. Poor efficiency due to impedance transformation from a
lower impedance (the impedance of the PA at rated power) to a
higher impedance (50 ohms for example) characteristic of filters,
antennas and other components operative with the PA.
[0026] The teachings of the present invention are intended to
overcome one or more of these disadvantages and thereby improve
operation of the communications device.
BRIEF DESCRIPTION OF THE INVENTION
[0027] According to one embodiment, the invention comprises a
communications apparatus further comprising a first antenna, a
first serial configuration of a first power amplifier and a first
matching network, a second serial configuration of a second power
amplifier and a second matching network, a switching element for
switchably selecting the first or the second serial configuration
for supplying a signal to the first antenna, the first and the
second power amplifiers supplying a respective first signal of a
first power and a second signal of a second power different than
the first power to the first antenna for transmitting and the first
and the second matching networks presenting respective first and
second impedances to the respective first and second power
amplifiers, the first and the second impedances responsive
respectively to a power-related parameter of the first and the
second signals.
[0028] According to another embodiment, the invention comprises a
communications apparatus further comprising a transmitting antenna,
a receiving antenna, a first serial configuration of a first power
amplifier and a first matching network for producing a first
signal, the first power amplifier operating in a first frequency
band, a second serial configuration of a second power amplifier and
a second matching network for producing a second signal the second
power amplifier operating in a second frequency band, a first
switching element for switchably supplying the first signal or the
second signal to the transmitting antenna, a first receiver, a
second receiver and a second switching element for switchably
directing a signal received at the receiving antenna to the first
receiver or the second receiver.
BRIEF DESCRIPTION OF THE DRAWINGS
[0029] The present invention can be more easily understood and the
advantages and uses thereof more readily apparent when the
following detailed description of the present invention is read in
conjunction with the figures wherein:
[0030] FIG. 1 is a graph illustrating power amplifier efficiency as
a function of power amplifier output power
[0031] FIGS. 2 and 3 are block diagrams of communications devices
according to the teachings of the present invention.
[0032] FIGS. 4 and 5 are schematic diagrams of two embodiments of
components of a communications device according to the teachings of
the present invention.
[0033] FIG. 6 is a perspective view and FIG. 7 is a cross-sectional
view of a handset communications device.
[0034] FIG. 8 is a schematic illustration of an antenna according
to one embodiment of the present invention.
[0035] FIG. 9 is a schematic illustration of parasitic capacitances
of the antenna of FIG. 7.
[0036] FIG. 10 is a schematic illustration of an antenna according
to another embodiment of the present invention.
[0037] FIGS. 11-18 are block diagram illustrations of apparatuses
for controlling one or more antennas according to the teachings of
the present invention.
[0038] FIGS. 19 and 21 are block diagram illustrations of various
antenna control techniques according to the teachings of the
present invention.
[0039] FIG. 22 is a block diagram illustration of a communications
device comprising a controllable high band and low band
antenna.
[0040] FIG. 23 is a perspective view of a front end module
constructed according to the teachings of the present
invention.
[0041] FIG. 24 is a schematic illustration of an antenna having
feed points at spaced apart terminal ends according to the
teachings of the present invention.
[0042] FIG. 25 is a block diagram illustration of a transmit signal
path according to the teachings of the present invention.
[0043] FIG. 26 is a block diagram of an antenna system and
associated components for receiving and transmitting a
communications signal.
[0044] FIGS. 27-30 are block diagrams of various communications
apparatuses for sending and receiving radio frequency signals
according to different embodiments of the present inventions.
[0045] FIG. 31 illustrates a communications apparatus in modular
form for sending and receiving radio frequency signals.
[0046] FIGS. 32-35 are block diagrams of communications apparatuses
for sending and receiving radio frequency signals according to
different embodiments of the present invention.
[0047] In accordance with common practice, the various described
device features are not drawn to scale, but are drawn to emphasize
specific features relevant to the invention Like reference
characters denote like elements throughout the figures and
text.
DETAILED DESCRIPTION OF THE INVENTION
[0048] Before describing in detail the exemplary methods and
apparatuses related to controlling antenna structures and operating
parameters, it should be observed that the present invention
resides primarily in a novel and non-obvious combination of
elements and process steps. So as not to obscure the disclosure
with details that will be readily apparent to those skilled in the
art, certain conventional elements and steps have been presented
with lesser detail, while the drawings and the specification
describe in greater detail other elements and steps pertinent to
understanding the invention.
[0049] The following embodiments are not intended to define limits
as to the structure or method of the invention, but only to provide
exemplary constructions. The embodiments are permissive rather than
mandatory and illustrative rather than exhaustive.
[0050] Antenna tuning control techniques are known in the art to
provide multi-band antenna performance for a multi-band
communications device. The present invention teaches antenna
control methods and apparatuses that overcome sub-optimal antenna
impedance (introduced by the antenna tuning process) and frequency
detuning effects that impair performance of the communications
device.
[0051] According to one embodiment of the present invention, an
antenna is tuned (by controlling its effective electrical length)
to a desired resonant frequency to obviate resonance detuning
caused by the operating environment of the antenna. Retuning the
antenna improves the antenna's performance and thus improves
performance of the communications device.
[0052] It is known that the transmitting power amplifier (PA) of a
communications device is designed to provide a controllable output
power to its load (i.e., the antenna) and to present a desired
output impedance (typically 50 ohms including any impedance
transformation elements). The output power range for which the
power amplifier is designed depends on the operating environment
and the signal protocols employed by the device. The output power
is controlled by device components to permit effective
communications with a receiving device. For example, an output
power of a cellular handset PA is controlled to communicate
effectively with a cellular base station as the handset moves about
the base station coverage area.
[0053] In the prior art, the PA efficiency changes as the power
supplied by the PA to a fixed load impedance (i.e., a fixed antenna
impedance) changes. Further, the PA output power, and thus the PA
efficiency, varies responsive to changes in the load impedance (the
antenna impedance). It is known that although the antenna is
designed to present a nominal 50 ohm impedance, in fact the
impedance varies with signal frequency. For example, the antenna
impedance changes when the signal frequency shifts from the antenna
resonant frequency that is near the center of the antenna's
operating frequency band to a signal frequency near a band edge.
Since the antenna impedance changes with signal frequency, it is
impossible to substantially exactly match the PA output impedance
to the antenna impedance over the operating frequency band. Thus
according to the prior art, the best that can be expected is to
establish a PA output impedance at the conventional 50 ohms, design
the antenna for a 50 ohm impedance at the resonant frequency and
recognize that inefficiencies are introduced into the system when
the signal frequency differs from the resonant frequency. In
summary, in the prior art the PA efficiency may decline as the PA
output power changes and as the signal frequency changes. Reduced
output power efficiency requires more battery power and thus
reduces battery life.
[0054] According to another embodiment of the present invention,
the antenna impedance (the PA load impedance) is controlled to
present an impedance to the PA that improves a power added
efficiency (PAE) of the power amplifier at a commanded PA radio
frequency (RF) output power. That is, the antenna impedance is
controlled as a function of the PA output power. Controlling the
load impedance to present a desired impedance value from a range of
impedance values permits the PA output voltage and current (which
determine the PA output power) to range over values that can be
supplied by the PA power supply, improving the efficiency at any
commanded power level. Since many communications devices operate on
battery power, improving the efficiency extends "talk time" (for a
specific battery size) between battery recharges. Also, controlling
the antenna (load) impedance overcomes the effects of naturally
occurring antenna impedance variations as the signal frequency
changes.
[0055] Yet another embodiment of the present invention controls
both the antenna resonant frequency and impedance to obtain the
combined advantages of both techniques.
[0056] Note that this impedance control technique of the present
invention differs from the prior art impedance matching techniques
of a complex conjugate match (i.e., an output impedance of a first
component is a complex conjugate of an input impedance of a second
component to which it is connected). These prior art techniques are
intended to maximize power transfer from the first component to the
second component at one specific frequency, since the impedance
value is frequency dependent.
[0057] Although there are many measures of PA efficiency for
consideration in the context of the present invention and all are
considered within the scope of the present invention, the preferred
measure appears to be power added efficiency (PAE), defined as the
RF output power less the RF power input to the PA, the resulting
quantity divided by the sum of the DC power supplied to the PA
(i.e., a product of the DC current and the DC voltage) and the RF
input power. Additional measures of PA efficiency (also expressed
as PA gain) can be found at page 63 of the reference entitled
"Microwave Circuit Design Using Linear Techniques and Nonlinear
Techniques," by Vendelin, Pavio and Rohde.
[0058] Generally according to the prior art, the PA output
impedance is a few ohms (3.OMEGA. for a common PA topology), and
must be transformed (by an impedance matching circuit interposed
between the PA and the amplifier) to the input impedance of the
antenna, nominally 50.OMEGA.. Given this requirement for a
relatively large impedance transformation, the reactive network
required to make the transformation has a relatively narrow
bandwidth. Since this specific impedance transformation is not
required according to the present invention, the
bandwidth-narrowing effects of the narrow bandwidth transformation
components are reduced.
[0059] FIG. 1 illustrates a graph of power amplifier PAE as a
function of power amplifier output power (in dBm) for a fixed load
impedance. At maximum power output, the power amplifier PAE is
about 50% (the theoretical maximum efficiency for a power amplifier
operating in a class A mode). As the power output is reduced, the
PAE drops. A curve 96 depicts this PAE reduction when the PA has a
fixed DC bias and supplies a signal to a fixed-impedance, such as a
fixed 50 ohm antenna load impedance. A low PAE is not desired as
the PA does not utilize the available power supply voltage to drive
the load.
[0060] A curve 98 depicts the improved PAE attainable for a PA
augmented with a DC-DC converter, i.e., to control the DC bias
voltage supplied to the PA as the power output decreases. A
DC-to-DC converter responsive to a fixed DC supply voltage
generates a controllable DC voltage for biasing the PA responsive
to the PA power output. This technique increases the PAE as
indicated by the curve 98 depicting a higher PAE than the curve 96.
But this approach requires additional components and adds
complexity to the PA and the communications device with which it
operates.
[0061] It is noted that most cellular phones and other wireless
communications devices commonly operate at moderate power levels.
Statistically, GSM handsets operate at an average output power of
about 18 dBm, where the PAE is typically less than 25% according to
prior art impedance matching techniques as illustrated in FIG.
1.
[0062] To solve the problem of PA inefficiencies associated with
power output level variation and the resulting inefficiencies
(i.e., reduced "talk-time") in operation of the communications
device, in one embodiment the present invention provides dynamic
and adaptive control of the PA load impedance (i.e., the antenna
impedance) responsive to the power output level of the PA.
[0063] In one embodiment the antenna impedance is adjusted,
according to techniques described below, to improves the PA load
impedance (the antenna impedance) responsive to the PA output power
level as the PAE falls during operation of the communications
device. Control of the PA according to the present invention is
intended to permit the PA to use all available power supply
voltage/current to amplify the input signal (less any voltage that
would cause the PA to saturate and clip the input signal) and
extend battery life and talk-time for those communications devices
operating on battery power. Other parameters related to the output
power of the PA (the power of the output signal from the PA) can be
used to control the antenna impedance, including the peak DC
current in the PA output signal.
[0064] As depicted by a curve 100 in FIG. 1, in one embodiment the
present invention adjusts the antenna impedance (antenna terminal
impedance) in discrete steps between a first PAE level of 40% and a
second PAE of about 50%, responsive to the commanded output power.
As the PAE falls to about 40%, the antenna impedance (the load
impedance to the PA) is adjusted to raise the PA PAE back to about
50%. The present invention therefore provides a better PAE than
offered by the prior art techniques. Control of the PA load
impedance according to the teachings of the present invention can
be accomplished in discrete impedance value steps, as indicated in
FIG. 1, or substantially continuously over a range of allowable and
attainable impedance values.
[0065] The PAE values depicted in FIG. 1 are merely exemplary, as
it is known that the actual PAE and the theoretical maximum
possible PAE are determined by many factors, including the
communications protocol and the power amplifier design. Also, the
PA output power may be limited by the available current and voltage
supplied by the power supply. As illustrated in FIG. 1, the PAE is
improved at power levels from about 0 to about 30 dBm, although the
technique can be applied generally to PA's operating at any power
level. Also, the PA PAE can be improved continuously, rather than
discretely as depicted, by continuously modifying the antenna
impedance in response to PA output power level changes. In one
embodiment of the invention, the impedance control is accomplished
by modifying antenna structural features as described elsewhere
herein.
[0066] Certain communications devices comprise an impedance
conversion element between the PA and the antenna. Thus according
to another embodiment of the present invention, in lieu of
controlling the antenna impedance to control the PA efficiency, an
impedance presented to the PA by the impedance conversion element
is controlled to control the PA efficiency.
[0067] In another embodiment of the present invention a processor
or controller controls one or more antenna elements or antenna
components for frequency tuning the antenna and/or for modifying
the antenna's impedance. FIG. 2 illustrates a communications device
103 comprising an antenna 105 for receiving and transmitting
information signals over a radio frequency link 106. In one
embodiment, the communications device 103 comprises a cellular
telephone handset. Signals received by the antenna 105 are
processed by receiving circuits 107 to extract information
contained therein. Information signals for transmitting by the
antenna 105 are produced in the transmitting circuits 109 and
supplied to the antenna 105, via a power amplifier 111, for
transmitting over the radio frequency link 106. A controller 110
controls the receiving and transmitting circuits 107/109.
[0068] An antenna processor/controller 113 (e.g., an antenna
controller) is responsive to a signal supplied by the controller
110 (or alternatively is responsive to the transmitting circuits
109 or the power amplifier 111) that indicates operational
parameters of the communications device 103. Responsive to this
signal, the processor/controller 113 develops a control signal for
controlling frequency tuning and/or impedance controlling elements
117. For example, the processor/controller 113 is responsive to the
signal indicating the PA output power or the operating frequency of
the communications device 103. Responsive thereto, the
processor/controller 113 effects a change to the antenna to change
the antenna impedance and/or the antenna resonant frequency. For
example, the processor/controller 113 selects a location of a feed
point and/or a ground point on the antenna structure to modify the
antenna's impedance and/or changes the antenna's effective
electrical length by controlling radiating segments to effectively
lengthen or shorten the antenna's radiating structure. Responsive
to the change in antenna impedance and/or resonant frequency, the
PAE improves and/or operation of the communications device
improves.
[0069] In an embodiment where the frequency tuning and/or impedance
controlling elements 117 comprise a plurality of controlled
impedance elements (each further comprising one or more inductive
and capacitive elements), the processor/controller 113 switches in
or connects one or more of the impedance elements to the antenna
105 to change the antenna impedance as presented to the PA,
improving the PA PAE at the commanded PA RF power output.
[0070] For example, it may be determined according to the teachings
of the present invention that insertion of a capacitor of a first
value into the antenna circuit improves the PA PAE for operation in
the PCS frequency band and insertion of a capacitor of a second
value improves the PAE for operation in the DCS frequency band. The
appropriate capacitor is inserted into the antenna circuit
responsive to a signal indicating the operational band of the
communications device 103 that is supplied to the antenna
processor/controller 113.
[0071] In yet another embodiment, the processor/controller 113
modifies (e.g., by switching antenna elements and related circuits
in and/or out of the antenna circuit, moving an antenna ground
point relative to its feed point or moving the feed point relative
to the ground point) one or more antenna physical characteristics
(e.g., effective electrical length, feed point location, ground
point location) to modify the antenna resonant frequency (and/or
the antenna terminal impedance) and thereby improve performance of
the communications device 103 for the current operating frequency
band. Thus as can be seen from the examples set forth herein there
are multiple techniques and structural elements that can be
employed to controllably modify the antenna impedance and/or the
antenna resonant frequency to improve operation of the
communications device 103.
[0072] One technique for controlling the antenna resonant frequency
inserts a capacitor in series with the antenna radiating structure,
resulting in an appreciable resonant frequency change while only
slightly changing the antenna impedance. A capacitor placed in
parallel with the antenna radiating structure can also change the
resonant frequency, but may cause a greater change in the antenna
impedance.
[0073] In another embodiment the antenna resonant frequency is
modified under control of the processor/controller 113 by inserting
(switching in) or deleting (switching out) conductive elements of
different lengths from the antenna radiating structure. The control
signal thus modifies the antenna effective electrical length. For
example, meanderline elements having different effective electrical
lengths can be switched in or out of the antenna 105 to alter the
resonant frequency. Such components for effecting this resonant
frequency tuning are described further below.
[0074] The frequency tuning and/or impedance controlling elements
117 of FIG. 2 can comprise elements associated with the antenna 105
or, as illustrated in FIG. 3, can comprise impedance controlling
elements 119 separate from the antenna 105 and interposed between
the PA 111 and the antenna 105. References herein to the element
117 includes the element 119.
[0075] Various operating parameters of the communications device
103 and its components can be determined and responsive thereto a
control signal supplied to the frequency tuning and/or impedance
controlling elements 117. Such parameters include, but are not
limited to, the PA RF output power, the operating frequency of the
communications device and the VSWR on the PA/antenna signal
path.
[0076] In a cellular system application of the present invention,
the power amplifier in the cellular handset is an element of a
closed loop control system with a base station transceiver. When
turned on, the handset RF power is set to a default value (probably
near a maximum output power) and an operating frequency is
selected. When the user places a call, a signal is transmitted on a
control channel to the base station requesting a frequency or time
slot assignment. The base station responds with an assigned
frequency and transmit power for the handset. According to the
teachings of the present invention, the antenna impedance is
adjusted to a desired value responsive to the commanded transmit
power and the antenna is tuned to the proper resonant
frequency.
[0077] During the cellular call, the base station transceiver may
command the handset to reduce or increase its output power and/or
change to transmitting or receiving on a difference frequency,
according to an operating scenario of the communications system and
the handset. The new commanded power output is employed to again
adjust the antenna impedance and/or the antenna resonant frequency.
Thus the base station power command controls the PA to change the
power level of the transmitted signal and also controls the antenna
impedance (the PA load impedance) to present an impedance that
improves the PAE.
[0078] In one embodiment the impedance is controlled to increase
the PA PAE to the maximum PAE of 50%. Unlike the prior art, the PAE
is increased without changing the PA DC bias voltage/current,
although the techniques described do not prevent the use of bias
control or multiple stage switched power amplifiers stages as
currently known in the art.
[0079] In another embodiment, the VSWR (or the forward power) can
be measured and a control signal derived therefrom for controlling
the impedance of the antenna to improve the PAE.
[0080] When the processor/controller 113 adjusts the antenna
resonant frequency as described above, it may then be possible to
reduce the PA output power as the signal strength or the
signal-to-noise ratio at the receiving device may increase
responsive to the resonant frequency change, allowing the power
reduction without impairing signal quality at the receiving end.
The antenna resonant frequency adjustment may also change the
antenna terminal impedance, in turn affecting the power amplifier
PAE. To improve the PAE, the resonant frequency adjustment can
initiate an antenna terminal impedance adjustment (either directly
by modifying antenna structural features or through an intermediate
impedance conversion element) to improve the PAE.
[0081] According to another embodiment, the antenna parameters are
manually adjustable by the user by operation of a discretely
adjustable or a continuously adjustable switching element or
control component that controls the frequency tuning and impedance
controlling elements 117 to change the antenna's resonant length or
the antenna impedance to improve the PA PAE and overall efficiency
of the communications device. Such an embodiment may also include
the processor/controller 113 for automatically adjusting the
frequency tuning and impedance controlling elements 117.
[0082] FIG. 4 illustrates an antenna 120 comprising a conductive
element 124 disposed over a ground plane 128. Switching elements
130, 132, 134 and 136 switchably connect feed conductors 140, 142,
144 and 146 to a respective location on the conductive element 124,
such that a signal source 150 is connected to the conductive
element 124 through the closed switching element 130, 132, 134 or
136. Location of the signal feed relative to the antenna structure
affects the antenna impedance. The switching elements 130, 132, 134
and 136 are configured into an opened or a closed state in response
to a control signal supplied by a power level sensor 160. Such
power level sensors are conventionally associated with commercially
available power amplifiers.
[0083] Likewise, the antenna's connection to ground may be
repositioned by operation of one or more of a plurality of
switching elements that each connect the antenna to ground through
a different conductive element. FIG. 5 illustrates an antenna 180
comprising switching elements 190, 192, 194 and 196 for switchably
connecting conductive elements 200, 202, 204 and 206 to ground.
Appropriate ones of the switching elements 200, 202, 204 and 206
are closed or opened at specific power levels responsive to control
signals supplied by the power level sensor 160 to affect the
antenna impedance and thus the PAE of the PA operative with the
antenna 180.
[0084] Although the teachings of the present invention are
described in conjunction with a PIFA antenna (planar-inverted F
antenna) of FIGS. 4 and 5, the teachings are applicable to other
types of antennas, including monopole and dipole antennas, patch
antennas, helical antennas and dielectric resonant antennas, as
well as combined antennas, such as spiral/patch, meanderline loaded
PIFA, ILA and others.
[0085] The switching elements identified in FIGS. 4 and 5 can be
implemented by discrete switches (e.g., PIN diodes, control field
effect transistors, micro-electro-mechanical systems, or other
switching technologies known in the art) to move the feed tap (feed
terminal) point or the ground tap (ground terminal) point in the
antenna structure, changing the impedance appearing between the
feed and ground terminals, i.e., the impedance seen by the power
amplifier driving the antenna. The switching elements can comprise
organic laminate carriers attached to the antenna to form a module
comprising the antenna and a substrate on which the antenna and its
associated components are mounted. Repositioning of the feed point
by appropriate selection of one or more of the switching elements
may vary the impedance from about five ohms to several hundred ohms
for impedance loading the PA, resulting in more efficient PA
operation as described herein.
[0086] Certain communications devices provide a variety of
communications services and are therefore required to operate in
the multiple frequency bands (sub-bands) as employed by those
services. Most prior art communications devices comprises a single
antenna exhibiting multi-resonant behavior to cover each of the
sub-bands.
[0087] According to the Chu-Harrington relationship, an antenna's
bandwidth decreases as a direct function of decreasing antenna
size. This relationship considers physical antenna distances as
proportional to an operating wavelength. The Chu-Harrington limit
(a widest bandwidth available from an antenna of a specific size)
applies to single band antennas. According to this relationship, a
relatively large single-band conventional antenna is required to
adequately cover the total operating bandwidth of communications
devices that operate in multiple frequency bands. But hand-held
communications devices require relatively small antennas, which
exhibit a narrower bandwidth according to the relationship. It is
also noted that few if any communications devices are required to
operate simultaneously in more than one sub-band.
[0088] When a single antenna presents multiple operating bands, it
may be appropriate to evaluate the Chu-Harrington limit on an
individual band basis. Since the present invention improves the
antenna performance on a per band basis, the Chu-Harrington limit
can be reassessed on a per band basis and the results combined to
yield results for the total bandwidth covered by the antenna.
[0089] According to the teachings of the present invention, the
antenna resonant frequency is tuned to the desired operating
sub-band using any of the various techniques described herein.
Since each of the sub-bands is narrower than the total bandwidth,
the tunable antenna of the present invention can be smaller than
the single large space-hungry antenna that the Chu-Harrington
relationship requires.
[0090] FIG. 6 illustrates a handset or other communications device
240 having an antenna disposed within the device 240 in a region
generally identified by a reference character 242. As is known in
the art, when the handset 240 is held by the user for receiving or
transmitting a signal, the user's hand is placed proximate the
region 242. The distance between the user's hand and the antenna is
determined by the user's hand size and orientation of the hand
relative to the antenna.
[0091] The so-called hand-effect or proximity loading refers to the
affect of the user's hand on antenna performance. When the user's
hand (and head) are proximate the handset and its internal antenna,
the collective dielectric constant of the materials comprising the
hand and the head changes the antenna operating characteristics
from those experienced in a free space environment, i.e. wherein
air surrounds the antenna and thus antenna performance is
determined by the dielectric constant of air. This effect detunes
the antenna resonant frequency, typically lowering the resonant
frequency. The antenna may also be detuned by the configuration of
certain handset mechanical components, such as a folder position
for a folder-type handset and a slider position for a slider-type
handset. The teachings of the present invention can also obviate
the detuning effects of these physical configurations.
[0092] A handset designed for operation in the CDMA band of 824-894
MHz includes an antenna that exhibits a resonant frequency peak
near the band center and an antenna bandwidth that encompasses
most, if not all, of the CDMA frequency band to achieve acceptable
handset performance. But the hand-effect detunes the antenna such
that the resonant frequency is moved to a frequency below the band
center or perhaps even out of the band. The result is impaired
antenna and handset performance since the antenna bandwidth is no
longer coincident with the CDMA frequency band of 824-894 MHz. It
is known that the hand-effect can detune the antenna by up to 40-50
MHz for handsets operating in the CDMA band.
[0093] One known technique for overcoming the hand-effect uses a
wide bandwidth antenna, including the frequencies of interest, i.e.
824-894 MHz, and extending to frequencies both above and below the
band of interest. When the hand-effect detunes the antenna, the
operating frequencies remain within the antenna bandwidth. However,
according to the various principles that govern an antenna's
physical attributes and performance (e.g., the Chu-Harrington
effect), there is a direct relationship between antenna bandwidth
and size, i.e., as the antenna bandwidth increases, the antenna
size increases. But as handset size continues to shrink, the use of
larger antennas to provide wide bandwidth operation is not feasible
and is deemed unacceptable by handset designers and users.
[0094] Another known technique for overcoming the hand-effect
increases the distance 249 (see FIG. 7) between the antenna 250
(mounted on a printed circuit board 252) and the handset case 254.
Increasing this distance by as little as 5 mm appreciably reduces
the hand-effect. However, handset size must be increased to
accommodate the increased distance.
[0095] According to an embodiment of the present invention, a
frequency-tunable active internal communications device (handset)
antenna overcomes certain of the disadvantages associated with the
prior art antennas described above, especially with respect to the
hand-effect and proximity antenna loading of the antenna by the
body or other objects. Tuning the antenna reduces these effects (in
both the transmit and receive modes) and improves the radiated
efficiency of the system, i.e., the antenna, power amplifier and
related components of the communications device. The tuning can be
accomplished responsive to a signal that indicates that the antenna
has been detuned, for example, by the hand effect. For example a
control signal that senses power output of the communications
device, the transmitting frequency or a signal derived from a
near-field probe can be used for tuning the antenna. The tuning can
also be effected by a manually controlled switch operated by the
user. In certain applications, however, the output power (or VSWR)
may be a difficult parameter to use for tuning as signal absorption
by the body can mask the signal detuning. That is, the output power
of VSWR may actually improve while the antenna frequency is detuned
from the desired operating frequency or frequency band.
[0096] FIG. 8 illustrates an antenna 300 (in this example the
antenna 300 comprises a spiral antenna, but the teachings of the
present invention are not limited to spiral antennas) mounted
proximate or above a ground plane 302 disposed within a handset
communications device. The antenna 300 further comprises an inner
spiral segment 300A and an outer spiral segment 300B. A ground
terminal 304 of the antenna 300 is connected to the ground plane
302. The handset comprises signal processing components, not shown,
operative to process a signal received by the antenna 300 when the
handset is operating in the receive mode, and for supplying a
signal to the antenna 300 when the handset is operating in the
transmit mode. A feed terminal 306 is connected between such
additional components and the antenna 300.
[0097] An equivalent circuit 310 of the antenna 300 is illustrated
in FIG. 9, including a signal source 312 representing the signal to
be transmitted by the antenna 300 when the handset is operating in
the transmit mode. The equivalent circuit 310 further includes
parasitic capacitances 316, 318 and 320 formed from coupling
between the inner spiral segment 300A and the ground plane 302, the
outer spiral segment 300B and the ground plane 302, and the inner
spiral segment 300A with the outer spiral segment 300B,
respectively.
[0098] According to the teachings of one embodiment of the present
invention, one or more of these parasitic capacitances is modified
to change the resonant frequency of the antenna 300 and/or the
antenna impedance (relative to the teachings of the present
invention to modify the antenna impedance to improve the PA PAE).
Accordingly, as shown in FIG. 8, the antenna 300 further comprises
a varactor diode 350 (or an electrically controllable capacitor,
not illustrated, in another embodiment) responsive to a variable
voltage source 352 for altering the capacitance of the varactor
diode 350 (or the capacitance of the electrically controllable
capacitor) and thus the capacitance between the antenna 300 and the
ground plane 302. The antenna resonant frequency is accordingly
changed by the capacitance change, which is in turn controlled by
the voltage supplied by the voltage source 352. In one embodiment a
manually operated controller is provided to permit the handset user
to manually adjust the voltage applied to the varactor diode (or
the control voltage for the electrically controllable capacitor) to
tune the antenna 300 for optimum performance. In another
embodiment, the antenna processor/controller 113 (see FIG. 2)
controls the variable voltage source 352 responsive, for example,
to the band, sub-band or frequency at n which the communications
device is operating.
[0099] Changing the capacitance in any region of the antenna 300
will change the antenna's resonant frequency. Changing the
capacitance where the current is maximum or near maximum may cause
a change in the resonant frequency. Also, relatively small
capacitance values can be used to effect the change in high
impedance regions of the antenna, because the reactance of a small
capacitor is more significant in relation to the impedance of the
antenna at the high impedance regions. One area where an impedance
change can be made includes a region proximate the ground and/or
the feed terminals 304/306, and thus the varactor diode 350 is
preferably disposed proximate the ground/feed terminals 304/306. In
addition to the use of a varactor, the capacitance can be changed
by other techniques that are considered within the scope of the
present invention.
[0100] According to another embodiment, an inductance of the
antenna 300 is modified to change the antenna's resonant frequency
(including the fundamental resonant frequency and other resonant
modes). Such an inductance can be in series or in parallel (to
ground) with the antenna 300. Thus either an inductive or a
capacitive reactive component (or both) of the antenna reactance
can be modified to change the resonant frequency.
[0101] According to yet another embodiment, the resonant frequency
is controlled by application of a discrete fixed DC voltage
supplied by a voltage source 362 to the varactor diode 350 (or to
an electrically controllable capacitor) via a switching element
364. See FIG. 10. The switch 364 can be manually operated by the
user or controlled automatically responsive to a performance
parameter or an operating metric that indicates the antenna has
been detuned from its resonant frequency.
[0102] Thus this embodiment provides a discrete resonant frequency
shift in response to the value of the DC voltage when the switching
element is placed in a closed or shorted condition. The invention
further contemplates multiple voltage sources and corresponding
multiple switches to provide multiple capacitance values and thus
multiple resonant frequencies from a single antenna. MEMS switched
or integrated capacitors (for example, an electrically controllable
capacitor) may also be used in this application, as well as any
other capacitive tuning methodology.
[0103] In another embodiment, an RF (radio frequency) probe 400 of
FIG. 11 senses the radiated power in the near field region of a
tunable antenna 404 responsive to the power amplifier 111. An
antenna tuning system, such as those described herein (including
the antenna processor/controller 113 of FIG. 2), tunes the antenna
resonant frequency to maximize the probe response. The tuning may
be in discrete predetermined steps or responsive to maximizing the
sensed near field power. Generally, this technique does not
compensate for absorption losses in material surrounding the
antenna, but corrects for lossless dielectric effects on the
antenna resonant frequency.
[0104] Certain communications devices or handsets are operable
according to multiple system protocols (e.g., CDMA, TDMA, EDGE, GSM
for a cellular system or Bluetooth or IEEE 802.11x), each protocol
assigned to a different frequency band (also referred to as a
sub-band). In the prior art, such a handset includes multiple
antennas, with each antenna designated for operation in one of the
frequency bands or an antenna capable of multiple resonance
behavior. The use of multiple antennas obviously increases handset
size and a single antenna with multiple resonance behavior is not
optimized for any specific frequency, especially if the sub-bands
are spaced apart, thereby degrading performance.
[0105] The present invention tunes a single antenna responsive to
the operating sub-band (by activation of the appropriate switch
element to change the antenna resonant frequency) when it is
desired to operate the handset in a different frequency band, e.g.,
in response to a different cellular protocol. For handsets that
automatically switch to a different available protocol, a handset
controller automatically controls the antenna resonant frequency by
selecting the appropriate DC voltage for the varactor diode 350 (or
another device that presents a controllable capacitance) such that
the antenna resonant frequency is within the selected operating
band.
[0106] Such a multiband antenna according to the present invention
is depicted by a multiband tunable antenna 450 of FIG. 12.
Operational parameters the multiband antenna 450 are controlled in
response to a signal, supplied from the controller 110, indicating
a current operating sub-band of the communications device.
[0107] When the communications device switches between operation in
a first frequency band to operation in a second frequency band, the
impedance presented by the antenna 450 changes and may not be an
optimal impedance for the PA 111, i.e., provide a load impedance
that permits the PA to operate at a desired PAE. An optimal
impedance is less likely if the multiple bands are significantly
spaced apart in frequency. Such a scenario may arise in a handset
where there is a marked decrease in power amplifier PAE when
switching from operation on the GSM band (880-960 MHz) to operation
on the CDMA band (824-894 MHz). For example, the VSWR can increase
and the PAE can decline when operation switches to the second
frequency band. Thus according to one embodiment of the present
invention, both the resonant frequency and the antenna impedance
can be controlled to improve operation of the communications
device, including the PAE of the PA. Of particular value is the use
of a smaller antenna having adequate performance over a band or
subband(s), and control of the resonant frequency and/or the
antenna terminal impedance between the receive and transmit modes
of operation when operating in a different band or subband(s).
[0108] Responsive to a control signal indicating a current
operating band or sub-band the antenna is tuned to a different
resonant frequency and/or the antenna impedance is modified to
present a PA load impedance that raises the PA PAE. The frequency
tuning and/or impedance adjustment can be accomplished by a stub
tuner or combinations of lumped and distributed elements, modifying
the antenna impedance to improve the PA PAE for a requested PA
output power level or retuning the antenna back to its desired
resonant frequency.
[0109] Alternatively, the antenna resonant frequency and/or
impedance can be changed by modifying one or more of the antenna's
effective electrical length, inductance or capacitance, including
modification of these features by using one or more lumped
capacitance or inductance elements, or using the various techniques
described herein. In one application, antenna band tuning as
implemented by the elements of FIG. 12 increased the PA PAE by
about 9%; PAE increases up to about 20% have also been
observed.
[0110] Providing an antenna frequency tuning capability permits
reduction of the antenna volumetric size (the reduction estimated
to be about 1/2) due to the reduced bandwidth requirement, as the
antenna is required to resonate in only one band or sub-band at any
time. Simulations indicate that in certain applications antenna
resonant frequency tuning alone may produce the desired PAE gain,
without the need to control the antenna impedance, i.e., the PA
load impedance, while maintaining sufficient bandwidth to cover
each band or sub-band, thereby taking advantage of the potential
for reduced antenna volume.
[0111] FIG. 13 illustrates another embodiment of the present
invention wherein an impedance of one or both of a filter 460 and
an antenna 465 are controllable to improve the PAE of the power
amplifier 111 as the power amplifier output power changes as
described above. A switch assembly 462 selects elements of the
filter 460 to effect a filter input impedance change. Similarly, a
switch assembly 464 selects elements of the antenna 465 to effect
an antenna impedance change.
[0112] Generally, the filter is controlled in accordance with its
filtering functions, e.g., filtering out-of-band harmonic
frequencies within a frequency band with minimal insertion loss.
Controlling the filter also assists in presenting a desired PA load
impedance (in conjunction with the antenna impedance) to achieve
the desired PA PAE.
[0113] Any of several different signals produced by the
communications device can be used to control the switch assemblies
462 and 464. In the illustrated embodiment a control signal derived
from a power sensor 468 is supplied to an encoder/multiplexer 470
for producing a control signal for each switch assembly 462 and
464. Responsive to the control signal, the switches 462 and 464
(illustrated as mechanical switches but implementable as
electronic, mechanical or electromechanical switches) are
configured to present the desired impedance for their respective
controlled devices. Techniques and components for controlling the
antenna impedance as described elsewhere herein can be applied to
the FIG. 13 embodiment to control the filter input and/or output
impedances and the antenna impedance.
[0114] FIG. 14 illustrates certain elements of a dual-band
communications device 480 capable of operating in both the GSM band
of 850/960 MHz and in the GSM band of 1800/1900 MHz. When operating
in the former GSM band, the signal to be transmitted is supplied to
an antenna 484 though a power amplifier 486 and a properly
configured transmit/receive control switch 487. When operating in
the latter GSM band, the signal to be transmitted is supplied to
the antenna 484 through a power amplifier 488 and a different
configuration of the transmit/receive control switch 487. The
antenna 484 comprises a radiating structure 490 and controllable
antenna elements 491 that permit adjustment of the antenna's
resonant frequency and/or its impedance.
[0115] A control signal supplied by the controller 110 controls the
power amplifiers 486/488 and the controllable antenna elements 485
responsive to the desired operating band or sub-band and the PA
output power. The control signal controls the elements 485 to
present an antenna impedance that provides a desired PAE for the
PA's 486/488. Additionally, the control signal controls the
elements 491 to present an antenna resonant frequency within the
operating frequency band or sub-band.
[0116] Although described in conjunction with a communications
device operating in one of the GSM bands, the teachings of the
present invention as described in conjunction with the
communications device 480 also applicable to other signal
transmission protocols, i.e., EGSM, CDMA, DCS, PCS, EDGE etc. and
other non-cellular communications systems and protocols.
[0117] Providing the capability to tune the antenna in a
communications device also permits use of smaller antenna
structures while the antenna structures (and their associated
components, such as the PA) operate at a higher PAE than prior art
antennas. Although not apparent, this is a direct result of the
Chu-Harrington relationship between bandwidth and antenna volume.
Generally, a smaller antenna exhibits a narrower bandwidth, but if
the antenna resonant frequency is controllable to a current
operating band of the communications device, then a wide band
antenna capable of acceptable operation in all frequency bands in
which the communications device operates is not required. A smaller
(and therefore likely more efficient) antenna can be employed in
the communications device if the antenna's operating band or
sub-band is selectable responsive to the operating band or
sub-band. For example, in a half duplex communications system
(different transmit and receive frequencies), a position of the
transmit/receive control switch commands the antenna to change its
resonant frequency to the operative sub-band depending on whether
the wireless device is in the transmit or receive state. This
technique allows most antennas to be reduced in volume by about a
factor of 1/2 and commensurately increases the antenna's PAE.
[0118] According to another embodiment, for half-duplex
communication protocols a communications device processor selects
either the receive or the transmit portion of the band (sub-band)
depending on the handset operational mode and supplies a control
signal to the antenna to alter one or more antenna parameters, by
techniques described herein, to modify the antenna resonant
frequency and/or the antenna impedance. Since the sub-bands have a
narrower bandwidth than the full band over which the communications
device operates, antenna size can be reduced according to this
embodiment.
[0119] What is not obvious to those trained in the art is that the
embodiments of the present invention permit use of a smaller
antenna within the communications device, while improving antenna
performance (e.g., PAE) over the operating bandwidth. The ability
to alter or select antenna performance parameters (e.g., resonant
frequency) in response to an operating frequency of the
communications device obviates the requirement for an antenna that
is capable of operating in all possible bands, and further permits
use of a smaller adaptive antenna without sacrificing antenna
performance. In fact, antenna performance may be improved. At a
minimum, constructing a smaller antenna and using the teachings of
the present invention to improve its performance, overcomes the
known performance limitations of the smaller antenna. Thus smaller
handsets can be designed for use with smaller antennas, without
sacrificing antenna and handset performance. To improve antenna
performance, the processor can improve the feed point, ground
point, impedance, antenna configuration or antenna effective length
for a given operating condition (e.g., signal polarization or
signal protocol) or operating frequency.
[0120] Advantages obtained according to the present invention are:
1) smaller antenna size; and 2) improved antenna PAE over the
operating bandwidth due to adaptive control of the antenna
configuration based on the current operating bandwidth.
[0121] Antenna tuning can also overcome the detuning due to hand or
other proximity effects. It is well known that antenna frequency
can shift when the user brings body parts or other objects in
proximity to the handset or wireless communications device. Two
physical phenomena occur in that case, both resulting in poorer
handset signal reception and transmission. The first effect is
detuning of the antenna resonance caused by proximal capacitive
loading of the antenna. The second is absorption of signals caused
by resistive loss mechanisms (including complex-valued dielectric
constants) associated with dielectric properties of the proximate
biological or other substances (wood, paper, water, etc.).
[0122] Operating wireless handheld devices in proximity to the
human body often results in over 7 dB of loss in the far field
radiated signal. At least 3 dB of loss is attributable to
absorption, as verified by published simulation studies. A portion
of the remaining loss may be therefore be attributable to antenna
detuning effects (4 db or more).
[0123] The present invention actively tunes the antenna, but may
not correct for the aforementioned loss due to absorption of the
radiated field components. Nevertheless, this approach improves the
handset receive or transmit performance by several decibels.
Current reduction of radiated signal performance due to hand/head
loading is typically from -3 dBi to over -10 dBi. Estimates are
that 4 dB or more added gain may result from the near field
controlled tuning technique of the present invention.
[0124] This embodiment can be implemented by altering the inductive
or capacitive tuning elements in the antenna, such as by
controlling frequency tuning and impedance controlling elements 502
of an antenna 504 responsive to a proximity sensor 506, as
illustrated in FIG. 15. The embodiment can also be implemented by
changing the effective electrical length of the antenna as
described above.
[0125] In another embodiment, the proximity sensor 506 supplies a
control signal to an antenna impedance control circuit 512 (see
FIG. 16) for controlling the impedance seen by the power amplifier
111 into an antenna 514 or for controlling the resonant frequency
of the antenna 514.
[0126] The proximity sensor 506 comprises a sensor that detects the
presence of the body or a body part using an optical sensor, a
capacitive sensor or another sensing device. In response to that
control signal, the antenna is tuned to a predetermined frequency
to offset the detuning caused by the proximate object and partially
compensating the loss due to the detuning. In another embodiment,
the proximate sensor is replaced with a near-field RF probe for
supplying a control signal that tunes the antenna to maximize the
near field signal.
[0127] In another embodiment, the sensor 506 comprises a component
for detecting a configuration of a handset communications device.
For example, a slider type handset and a flip type handset can be
in an open or closed position, influencing operation of the antenna
504. By determining the handset configuration, the antenna can be
controlled to improve antenna and handset performance.
[0128] In yet another embodiment, the present invention comprises
an antenna resonant frequency tuning component for use during
manufacture of the communications device to reduce resonant
frequency variations in the manufacturing processes.
[0129] Such a resonant frequency tuning component comprises a
plurality of tuning components (a matrix of components, for
example) such as the frequency tuning and impedance controlling
elements 117 (see FIG. 2) or the tunable antenna 404 (see FIG. 11)
as described above, that are controllable to compensate the
expected range of resonant frequency and bandwidth variability
resulting from production variations. During the production stage,
the tuning components are configured to set the desired resonant
frequencies for optimum performance (PAE, VSWR, etc). In one
embodiment, a tuning matrix comprises a passive assembly with
fusible links that are opened (blown) to insert matrix components
into the antenna circuit. In another embodiment active device
switches (control field effect transistors,
micro-electro-mechanical systems (MEMS) or other switch
technologies known in the art) are utilized to insert components
into the antenna circuit by closing one or more of the switching
devices.
[0130] FIG. 17 illustrates a primary radiating structure 550 of an
antenna. Switches 552 (e.g., fusible links, transistor switches)
switchably connect one or more of the tuning components 556A, 556B,
556C and 556D to various locations on the primary radiating
structure 550 to control one or more of the antenna impedance and
the resonant frequency. The switches can be permanently opened or
closed after manufacturing and testing the primary radiating
structure 550 to overcome the effects of manufacturing variations.
In another embodiment, the switches 552 are controlled by a
controller associated with a communications apparatus with which
the primary radiating structure 550 operates, the controller
responsive to operating characteristics of the communications
apparatus to control the switches 552 and thereby control operation
of the antenna, in particular, the antenna resonant frequency and
impedance.
[0131] The teachings of the present invention can also be applied
to a communications device providing antenna diversity. That is,
each of the diverse antennas includes components to effectuate a
change in reactance or a change in effective electrical length to
control the antenna resonant frequency.
[0132] As illustrated in FIG. 18, a communications device 600
includes two antennas 602 and 604, each responsive to an antenna
controller 610 and 612 for controlling the respective antenna
resonant frequency and/or impedance according to the various
teachings and embodiments of the present invention. A diversity
controller 618 determines which one of the antennas 610 and 612 is
operative at any given time (in the receive mode, the signals can
be combined to produce a composite received signal). A processor
executing an appropriate algorithm controls the antenna controllers
210 and 212 and the diversity controller 218 to improve a signal
quality metric of the communications device.
[0133] FIGS. 19-21 illustrate additional configurable or
controllable antennas that offer the capability to overcome or at
least reduce the effects of undesirable conditions within the
antenna's operating environment. An antenna 700 in FIG. 19
comprises a meanderline structure 702 further comprising a
plurality of meanderline segments 702A, a first terminal end
connected to a feed 704 and a second terminal end connected to a
radiating structure 706. Exemplary taps 710 connected to one or
more of the meanderline segments 702A are connected to ground by
closing an associated switch 714 under control of an antenna
controller 718. Connecting one or more of the meanderline segments
702A to ground influences one or more of the antenna resonant
frequency, bandwidth and input impedance.
[0134] The meanderline structure 702 is a slow wave structure where
the physical dimensions of the conductor comprising the meanderline
structure 702 are not equal to its effective electrical dimensions.
Generally, a slow-wave conductor or structure is defined as one in
which the phase velocity of the traveling wave is less than the
free space velocity of light. The phase velocity is the product of
the wavelength and the frequency and takes into account the
material permittivity and permeability of the material on which the
meanderline structure is formed, i.e., c/((sqrt(.di-elect
cons..sub.r)sqrt(.mu..sub.r))=.lamda.f. Since the frequency remains
unchanged during propagation through the slow wave meanderline
structure 702, if the wave travels slower (i.e., the phase velocity
is lower) than the speed of light in a vacuum (c), the wavelength
of the wave in the structure is lower than the free space
wavelength. The slow-wave structure de-couples the conventional
relationships among physical length, resonant frequency and
wavelength, permitting use of a physically shorter conductor since
the wavelength of the wave traveling in the conductor is reduced
from its free space wavelength.
[0135] The feed 704 is connected to receive and transmit circuits
720 via a 1.times.X RF switch 722 of the communications device
operative with the antenna 700. The receive and transmit circuits
700, known in the art, comprise one or more low noise amplifiers
and associated receiving, demodulating and decoding components for
determining the information signal from a signal received by the
antenna 700, and further comprise one or more power amplifiers,
modulating and coding components producing a transmitted signal
responsive to an information signal.
[0136] Certain components of the receive and transmit circuits 720
are frequency sensitive and thus for optimum performance of the
communications device the appropriate frequency sensitive
components must be selected responsive to the operating band and
mode of the communications device. The 1.times.X switch 722,
controlled by a control signal provided by the circuits 720 over a
control conductor 724 or by a control signal from the antenna
controller 718, provides the capability to connect the antenna 700
to the appropriate frequency-sensitive components of the receive
and transmit circuits 700. Additionally, it is desired to configure
the antenna controller 718 to improve performance of the antenna
700 responsive to the operational mode of the communications
device. For example, when the communications device is operative in
a receive mode in a first frequency band, the 1.times.X switch 722
is configured to connect receiving components optimized for
operation in the first frequency band to the antenna 700. Further,
the antenna controller 718 is configured to control the switches
714 to improve operation of the antenna 700 for receiving signals
in the first frequency band. In an exemplary embodiment,
optimization of antenna performance suggests that the switches 714
are configured to present an antenna impedance that improves PAE of
the operative receiving circuits 720.
[0137] In one embodiment the antenna 700 of FIG. 19 is formed on or
within a dielectric substrate. Thus the permittivity and the
permeability of the dielectric material comprising the substrate
affect the properties of the meanderline structure 702, and thus
the properties of the antenna 700. In such an embodiment the
antenna 700 can be formed as a module for simplified insertion and
connection to the associated circuits of a communications device,
such as the handset or communications device 240 of FIG. 6. Use of
the module antenna also promotes repeatability during the
manufacturing process to ensure proper physical placement and
connection of the antenna.
[0138] In one embodiment, the switches 714 are implemented by
connecting one or more of the taps 710 to ground through an
inductor (not shown) to establish a DC ground for each tap 710.
[0139] In a FIG. 20 embodiment, an antenna 750 comprises a
configurable signal feed structure comprising the meanderline
structure 702. Antenna operating characteristics (e.g., antenna
impedance, gain, radiation pattern) are determined by closing one
of a plurality of switches 754 under control of the antenna
controller 718.
[0140] FIG. 21 illustrates an antenna 800 comprising a meanderline
structure 802 further comprising a plurality of meanderline
segments 802A and exemplary switches 808 controlled by the antenna
controller 718 to provide discrete resonant frequency tuning of the
antenna 800. Since the meanderline structure 802 forms a portion of
the antenna and therefore influences the antenna parameters,
including the resonant frequency, shorting one or more of the
meanderline segments 802A changes the resonant length and thus the
resonant frequency of the antenna 800. One or more of the switches
808 can be closed to tune the antenna 800 to a desired frequency.
Generally, tuning by operation of the switches 808 results in
discrete, rather than continuous, tuning of the resonant
frequency.
[0141] In an exemplary operational mode, the 1.times.X switch 722
is controlled to connect the appropriate frequency-sensitive
components of the receive and transmit circuits 720 to the antenna
800, responsive to the current operational parameters of the
communications device. The resonant frequency of the antenna 800 is
also controlled by configuring the switches 808, under control of
the antenna controller 718, to establish an antenna resonant
frequency that is the same as the operating frequency of the
selected frequency-sensitive components.
[0142] The various switching elements identified in FIGS. 19-21 can
be implemented by discrete switches (e.g., PIN diodes, control
field effect transistors, micro-electro-mechanical systems, or
other switching technologies known in the art). The switching
elements can comprise organic laminate carriers attached to the
antenna to form a module comprising the antenna (e.g., the
meanderline structures and the radiating structures), the
controlling switches and the 1.times.X switch on a single
dielectric substrate.
[0143] FIG. 22 illustrates a band switched antenna structure 900
comprising respective low band and high band antennas 902 and 904.
Impedance controlling circuits 906 and 907 connect the low band
antenna 902 to a switching terminal 908 of a radio frequency (RF)
switch 910. Respective transmit and receive terminals 912 and 914
of the RF switch 910 are connected respectively to a serial
connection of a low band power amplifier 920 and a filter 922, and
to a serial connection of a first band low noise amplifier (LNA)
928 and a filter 930.
[0144] Respective transmit and receive terminals 932 and 934 of the
RF switch 910 are connected respectively to the serially connected
low band power amplifier 920 and filter 922 and to the serially
connected second band LNA 938 and filter 940. A switching terminal
941 is operable to select either the input terminal 932 or the
input terminal 934.
[0145] Generally, the impedance controlling circuits 906 and 907
are dissimilar to a present a selectable antenna (load) impedance
to the low band power amplifier 920 that improves its operation.
Typically, the power amplifier 920 operates in two frequency bands,
each presenting a different PA output impedance. It is therefore
desired to provide a selectable impedance (the impedance
controlling circuits 906 or 907).
[0146] In one embodiment, the impedance controlling circuit 906
comprises a series connection of a first and a second capacitor at
a common terminal, with an inductor connected between the common
terminal and ground. In one embodiment, the impedance controlling
circuit 907 comprises a series connection of a first and a second
inductor at a common terminal, with a capacitor connected between
the common terminal and ground. In other embodiments different
impedance controlling circuits can be used depending on the
impedance of the low band antenna 902 and the impedance of the PA
920.
[0147] The high band antenna 904 is connected to a switching
terminal 950 through the impedance controlling circuit 906 and to a
switching terminal 954 through the impedance controlling circuit
907. Respective transmit and receive terminals 960 and 962 of the
RF switch 910 are connected respectively to a serially connected
high band power amplifier 964 and filter 966 and to a serially
connected third band LNA 970 and filter 972.
[0148] Respective transmit and receive terminals 978 and 980 of the
RF switch 910 are connected respectively to the serially connected
high band power amplifier 964 and filter 966, and to a serially
connected fourth band LNA 984 and filter 986.
[0149] The filters 930, 940, 972 and 986 associated with the LNA'S
function in the conventional manner to remove noise and out-of-band
frequency components from the received signal, with the pass band
of each filter 930, 940, 972 and 986 dependent on the operational
band of its associated LNA.
[0150] The operational mode of the switched antenna 900 is
determined by operation of the communications device with which the
antenna 900 functions. When operating in the low band (i.e., low
frequency operation) receive mode, either the switching terminal
908 is configured to connect the low band antenna 902 and the
impedance controlling circuit 906 to the filter 930 and the first
band LNA 928, or the switching terminal 941 is configured to
connect the low band antenna 902 and the impedance controlling
circuit 907 to the filter 940 and the second band LNA 938. A
configuration of the switching terminals 908 and 941 is controlled
by an antenna controller (not shown in FIG. 22) based on the
operating characteristics of the communications device. In
particular, if the communications device can operate in two
different low band frequencies, one of the switching terminals 908
or 941 is operative to connect the associated LNA 928 or 938,
respectively, to the low band antenna 902 responsive to the
operating low-band frequency.
[0151] During operation in the low frequency band transmit mode,
the PA 920 is connected to the low band antenna 902 through one of
the impedance controlling circuits 906 and 907 via the selected
configuration of the RF switch 910, that is via either the terminal
912 or the terminal 932, as determined by one of the impedance
controlling circuits 906 or 907 that improves the PAE of the power
amplifier 920. In another embodiment, the impedance controlling
circuits 906 and 907 are also controllable to change the impedance
seen by the associated power amplifier to improve the PAE of that
power amplifier.
[0152] During operation of the switched antenna 900 in the high
frequency band, the switching terminals 950 and 954 are controlled
to connect either the LNA 970 or the LNA 984 to the high band
antenna 904 in the receive mode or to connect the high band PA 964
to the high band antenna 904 through one of the impedance
controlling circuits 906 and 907.
[0153] As discussed elsewhere herein, according to the prior art it
is usually the intent of the communications device designer to
transform the impedances of the components in the transmit and
receive signal paths to a nominal 50 ohms to improve device
performance. Since these components are typically individually
procured and assembled, the presented impedance values may differ
substantially from 50 ohms and the transformation to 50 ohms may
result in undesired bandwidth limitations as also discussed
above.
[0154] Additionally, the layout of the components and connecting
conductors (which may present other than a 50 ohm impedance) tends
to cause the impedance to vary from the desired 50 ohms. Since the
load is usually a complex impedance, reactive components or
transmission line lengths will change the load at the power
amplifier depending on the line length, layout, component
selection, filter type, etc. Finally the antenna supplier has no
control and little influence over design features and components in
the transmit and receive signal paths that can substantially
influence antenna performance.
[0155] In addition to performance degradation due to these
impedance mismatches, it is also known that interaction of the
antenna's near electric and magnetic fields with components in the
communications device can result in: a) lower radiation PAE due to
excitation of unwanted currents in proximate elements that impose
electrically resistive loss mechanisms and b) dielectric loading
effects on antenna elements that influence its resonant
frequency.
[0156] To overcome these effects on antenna performance, the
present invention teaches a radio frequency module embedding one or
more components of the serial component string including one or
more of transmitting and receiving circuits, a low noise amplifier,
a power amplifier, filters and connecting elements connecting these
components to the antenna. The impedance presented by the module
components is substantially consistent among all the module
components (and likely not the conventional 50 ohms) to improve
signal receiving and transmission performance, overcoming the
effects of impedance variations and mismatches of the prior art. An
exemplary module is illustrated in FIG. 23 and described in the
accompanying text.
[0157] The module also improves power amplifier PAE (resulting in
longer talk time between battery charges). Use of the module
reduces development time to market and lowers manufacturing and
component integration costs since all components are embedded in
the module and its fabrication is repeatable.
[0158] A modular embodiment of the switched antenna 900 of FIG. 22
is illustrated in FIG. 23, wherein a module 1000 comprises a front
end electronics module 1002 (comprising in one embodiment the
impedance controlling circuits 906 and 907, the RF switch 910, the
filters 922, 966, 930, 940, 972 and 986, the power amplifiers 920
and 964 and the low noise amplifiers 928, 938, 970 and 984 or any
combination of these elements), an organic (or other) laminate
material 1004, the low band and high band antennas 902 and 904
(preferably constructed from an appropriate length of conductive
material, including a conductive flex film material and either
printed on or subtractively removed from one or more surfaces of
the laminate 1004) and a carrier 1008. In another embodiment the
passive components of the impedance controlling circuits 906 and
907 and the passive components of the filters 922, 966, 930, 940,
972 and 984 are formed as passive elements within the material of
the laminate 1004. Candidate laminate material include known PCB
compounds and epoxy materials both with and without the fiber glass
filler material. Printed circuit board material and flex film
material can be used in lieu of the organic laminate material.
[0159] In an embodiment in which the low and high band antennas
operate in respective frequency bands of 824-960 MHz and 1710-1990
MHz, the modular switched antenna 900 (i.e., the laminate material)
is about 28 mm long, about 15 mm wide and about 7 mm high,
presenting an antenna volume about one-half to one-quarter the
volume of prior art multiband antennas. Embodying the various
antenna control techniques taught herein in modular form provides
more efficient packaging, simpler insertion into a communications
device, lower cost, better reliability and better performance. In
particular, the design and layout processes associated with use of
the module in the communications device are substantially reduced.
Further the selectable/controllable/tunable features of the various
antenna embodiments described herein provide a higher PA PAE over
the operating bandwidth than the prior art multiband antennas.
[0160] Advantageously, within the module 1000 it is not necessary
to transform the impedance values of connected components to the
conventional 50 ohms. Instead, the transmission line lengths and
the impedance presented by the transmission lines are selected to
provide the desired impedance transformations between two
components connected by the transmission lines.
[0161] In CDMA systems, active tuning of the antenna as described
herein presents an impedance to the PA via the duplexer
intermediate the antenna and the PA. The various schemes according
to which the phase, amplitude and/or impedance of the antenna are
adjusted to improve the PAE can take into account the transmission
characteristics of the duplexer and associated interconnect
transmission lines to the antenna and the PA. The
frequency-dependent characteristics of the duplexer can therefore
be considered when adjusting the antenna impedance. Alternatively,
frequency variant tuning of the duplexer can be employed, in
addition to tuned elements at the antenna. To improve the amplifier
PAE at less than rated load, power dependent tuning of the duplexer
itself can be used as well.
[0162] As a result, it is preferred to include the antenna,
phase/amplitude/impedance tuning components, duplexer, and
associated control components as part of a module, such as the
module 1000 of FIG. 23. The module functions, as described, to
present a load to the PA at operating frequencies that optimizes
the PA efficiency. In another embodiment some degree of mistuning
may be employed to adjust for antenna proximity effects (e.g.,
proximate relation of the users had and body to the antenna) during
operation.
[0163] Inclusion of tuning components at the antenna (as described
in various embodiments described above) is also an acceptable
solution for many problems currently encountered in portable device
RF design for CDMA systems. The functions described above, such as
optimizing the PA efficiency for GSM operation, tuning to maintain
antenna resonance in the presence of proximal dielectrics (human
body, tables, etc), band-selectable tuning (no sub bands in CDMA)
to allow reduction of the antenna physical volume, and generally,
tuning to present a more constant impedance (better match) versus
operating frequency, are all possible byproducts of the inclusion
of tuning components.
[0164] According to another antenna control embodiment of the
present invention, antenna spatial diversity is achieved by
selectively driving a radiating structure 1100, see FIG. 24, from
either a terminal end 1104 or a terminal end 1108. A meanderline
radiator structure is illustrated as merely an exemplary
embodiment.
[0165] With a switch 1112 in a configuration represented by a
reference character 1112A and a switch 1120 is in a configuration
1120B, a feed 1114 is coupled to the terminal end 1104, resulting
in a current minimum at the terminal end 1108 and a current maximum
at the terminal end 1104. Reconfiguring the switch 1112 to a
configuration 1112B and configuring the switch 1120 closing the
switch 1120 shifts the current maximum to the end 1108 and the
current minimum to the end 1104. Changing the location of the
current maximum and current minimum alters the antenna pattern
(phase center) to achieve spatial diversity.
[0166] The switches 1112 and 1120 are controlled by control signals
generated in other elements of the communications device. For
example, if the signal-to-noise ratio of the received signal falls
below an identified threshold (or the bit error rate of the
received signal exceeds a predetermined threshold) the switch
configurations are reversed in an effort to improve
performance.
[0167] As described elsewhere herein, one embodiment of a
conventional communications device operative with a single antenna
employs a serial component string (signal path) comprising the
power amplifier (and the low noise amplifier in the receiving
mode), a switch plexor (for use with the GSM protocol) or duplexer
(for use with the CDMA protocol) the antenna impedance controlling
element and the antenna. The switch plexor or duplexer switches
into the serial string of the appropriate power amplifier or low
noise amplifier responsive to operating conditions.
[0168] It is known that an actual nominal antenna impedance can
range between about 20 ohms and several ohms as a function of
frequency over its operating bandwidth. The output impedance of the
power amplifier is typically a few ohms (about 3 to 7 ohms and
usually complex) and varies with output power as described above.
To accommodate the impedance variations in the signal path and
recognizing that in any case the impedance varies with frequency,
the antenna impedance is transformed to an impedance that improves
the power amplifier PAE. Specifically, the optimum impedance is
selected from a locus of points that are generated as a function of
the signal frequency supplied to the antenna and the commanded RF
power output from the PA. The optimum impedance is the value that
allows the power amplifier to operate at optimum PAE, i.e.,
producing an output signal that uses the available supply
voltage/current without signal clipping or saturation.
[0169] Conventionally, the power amplifier impedance is transformed
to about 50 ohms. It is therefore desired for the antenna to
present a 50 ohm impedance (by transforming the antenna radiation
resistance, typically about 15 ohms, to 50 ohms) such that when
connected by a 50 ohm transmission line to the power amplifier, the
antenna provides a satisfactory load for the PA. By utilizing 50
ohm interconnects in the signal path between the PA and the
antenna, insertion and cascading of conventional filters and
switching elements (and any other signal processing elements in the
signal path such as bias circuits, RF connectors, transmission
lines, transmit/receive switches) is facilitated and maximum power
is transferred from the power amplifier to the antenna.
[0170] It is also known that large impedance transformations (e.g.,
3 to 50 ohms) can reduce the signal bandwidth, where the bandwidth
reduction is a direct function of the ratio of the two impedances.
One known technique to overcome the bandwidth reduction employs
multistage matching where the total impedance transformation is
accomplished in sequential stages, each stage matching two
impedances of a lower ratio than the ratio of the total impedance
transformation, as described by the Fano matching criteria.
[0171] To overcome the effects of these impedance mismatches and
impedance variations, according to one embodiment of the present
invention the power amplifier output impedance is not transformed
to 50 ohms, but instead to a value close to the antenna radiation
resistance or to an intermediate value between 50 ohms and the PA
output impedance. In another embodiment in which a filter is
interposed between the power amplifier and the antenna, the
impedances of both the power amplifier and the antenna are
transformed to the filter impedance. Transforming to an impedance
lower than 50 ohms reduces the concomitant bandwidth reduction as
the ratio of the two impedances is lower.
[0172] FIG. 25 illustrates this aspect of the invention in which a
filter and/or switch plexer 1150 is interposed between a power
amplifier 1152 and an antenna 1154. Impedance transformation
components 1160 transform the output impedance Zout=n of the power
amplifier 1152 to an impedance m, wherein the switch plexer and/or
filter 1150 has an input impedance Zin=m and an output impedance
Zout=p. Impedance transformation components 1164 transform the
impedance presented by the switch plexer and/or filter 1150 to the
antenna input impedance Zin=q. Preferably all of the series
equivalent characteristic impedance values, n, m, p and q are less
than 50 ohms. Therefore the bandwidth reduction associated with
these impedance transformations is less than the prior art systems
where all the impedances are transformed to 50 ohms. It is also
possible to design an antenna to provide a closer impedance match
to the output impedance of the PA, thereby eliminating the need
impedance transform to an artificially specified value, thereby
optimizing the performance of the PA, filter, switchplexer (or
diplexer) and elements in the antenna chain. The benefit of this
approach is lower loss in the transmission and receiving paths and
greater bandwidth.
[0173] In a preferred embodiment, the various elements illustrated
in FIG. 25 are formed as a radio frequency antenna/power amplifier
module, comprising a dielectric material surrounding an integrated
circuit, wherein the electronic components of the elements 1150,
1160 and 1164 are formed within the integrated circuit. A fixed
pre-positioning of the PA 1152 relative to the other components
included within the module provides the best performance for the
modularized elements.
[0174] The filter components of the element 1150 may be implemented
as passive components within the module, and therefore are not
necessarily formed in the integrated circuit.
[0175] To improve the power amplifier's performance, a PA load
impedance that improves the PAE over an appropriate bandwidth is
determined. The impedance of one or more of the module elements is
transformed to present that load impedance to the PA and the
impedance transformation components 1160 and 1164 are controlled to
match impedances between elements (except the PA 1152).
[0176] Another embodiment of the present invention teaches
modularization of a front end module (FEM) 1200 illustrated in
block diagram form in FIG. 26. The FEM 1200 comprises an antenna
1204 and routing switches 1206. A receive path comprises a receive
filter 1208 and a low nose amplifier 1210. A transmit path
comprises a transmit filter 1214 and a power amplifier 1218. In
another embodiment, the FEM 1200 further comprises the impedance
transformation components illustrated in FIG. 24 for improving the
bandwidth response of the FEM 1200.
[0177] The LNA 1210 and the PA 1218 are further connected to an RF
integrated circuit (RFIC) 1230 comprising conventional components
associated with processing the outgoing signal in the transmit mode
and the incoming signal in the receive mode, e.g., up and down
frequency conversion, modulation and demodulation and signal
frequency synthesis. A baseband processor 1240 decodes the baseband
signal provided by the RFIC 1230 in the receive mode to produce the
information signal. In the transmit mode, the baseband processor
1240 encodes the information signal and supplies the encoded signal
to the RFIC 1230. In the receive mode, the baseband processor 1240
receives the baseband signal from the RFIC 1230, decoding same to
produce the information signal.
[0178] Use of the FEM 1200 reduces time-to-market for the
manufacturer of the communications device since the components and
functionality are conveniently supplied in modular form. Reduced
manufacturing costs (fewer components to inventory and track,
simpler designs required) and manufacturing repeatability are also
realized by use of the FEM 1200.
[0179] In one embodiment, the FEM 1200 incorporates the beneficial
dynamically selected antenna impedance values for loading the PA at
different power levels, thus improving PA operating PAE, as
described above. PAE improvements, which have been shown by the
inventors to be 10% to 20%, lengthen the handset "talk" time as
battery life is extended.
[0180] The teachings of the present invention related to antenna
impedance control can also be applied to control the VSWR of the
signal provided by the PA to the antenna for transmission. An
actual VSWR can be measured by known techniques and compared to a
desired VSWR. The antenna impedance is controllable responsive to
the actual VSWR to achieve the desired VSWR.
[0181] FIGS. 27-29 illustrate various antenna and related
components suitable for use with a CDMA communications protocol;
FIG. 30 illustrates an antenna isolation technique suitable for use
with certain embodiments of the present invention; FIGS. 31 and 32
illustrate antennas and related components suitable for use with a
GSM communications protocol.
[0182] FIG. 27 illustrates a transmitting and receiving system 1500
suitable for use with the CDMA air interface. The system 1500
comprises a high band antenna 1502 operative generally in the
frequency bands of about 1850-1910 MHz (uplink) and 1930-1990 MHz
(downlink) and a low band antenna 1506 operative generally in the
frequency band of about 824-849 MHz (uplink) and 869-894
(downlink). As applied to the cellular and PCS services, a CDMA
uplink signal is transmitted (for example from a handset to a base
station) on one of the uplink frequencies and the downlink signal
(for example from the base station to the handset) is transmitted
on one of the downlink frequencies. Thus the system 1500 of FIG. 27
is capable of sending and receiving signals in either of the high
or low frequency bands. But since the transmit and receive
functions use the same antenna an isolating device (a duplexer for
example) is required to isolate the transmit and receive paths.
[0183] A high band receiver 1510 is connected to the high band
antenna 1502 via a serial connection of an impedance matching
network 1514 and a duplexer 1518. In a preferred embodiment, the
matching network 1514 matches the high band antenna impedance (as
transformed through the duplexer 1518) to 50 ohms, since the high
band receiver typically operates from a 50 ohm input. In the
illustrative embodiment of FIG. 27, the matching network 1514
matches a 20 ohm antenna impedance to 50 ohms. Although the
impedance matching network 1514 can be designed to accommodate
matching of various impedance values, it is known that impedance
matching tends to reduce the signal bandwidth in direct proportion
to the difference between the two impedance values that are
matched, unless complex multistage matching elements are
employed.
[0184] The system 1500 further comprises a high-power amplifier
1530 (providing an output power P1) connected to the high band
antenna 1502 via a serial string of a matching network 1534, a
switch 1538 and the duplexer 1518. A low-power amplifier 1540
(providing an output power P2) is also connected to the high band
antenna 1502 via a serial string of a matching network 1544, the
switch 1538 and the duplexer 1518. Depending on the power output
level of the power amplifiers 1530 and 1540, the PA output
impedance can range from about 3 ohms to about 2000 ohms.
[0185] As described above, the load impedance seen by the power
amplifier affects the power amplifier efficiency. According to an
embodiment of the invention described above, the impedance of an
antenna connected to the PA is controlled to present an impedance
that maximizes the PAE.
[0186] In the embodiment of FIG. 27, the power amplifier 1530 is
selected as the operative power amplifier (responsive to a control
signal not illustrated and configuration of the switch 1538 to a
state 1538A) when a relatively high-power output signal is required
for the effective communications in the high frequency band. The PA
1530 thus supplies a relatively high-power output signal P1. When
supplying the signal P1, an exemplary load impedance of about 3
ohms maximizes the PAE of the power amplifier 1530. Thus it is
desired for the matching network 1534 to transform the impedance
seen looking into the switch 1538 (for example about 20 ohms as
indicated in FIG. 27) to about 3 ohms to maximize the PAE of PA
1530.
[0187] For relatively low power operation in the high frequency
band, the PA 1540 is operative, as controlled by a control signal
not illustrated in FIG. 27 and configuration of the switch 1538 to
a state 1538B, to deliver a low-power output signal P2. Due to the
difference in the power of the signals P1 and P2, the optimum load
impedance for maximizing the PAE of the PA 1540 is different than
the optimum impedance for maximizing the PAE of the PA 1530. In the
exemplary embodiment of FIG. 27, the impedance is indicated to be
greater than about 3 ohms and can range to about 2000 ohms
dependent on the power in the output signal P2. Thus the matching
network 1544 transforms the exemplary switch/antenna impedance of
about 20 ohms to the PA 1540 output impedance to maximize its
PAE.
[0188] Although the power amplifiers 1530 and 1540 are described as
supplying a discrete output power level P1 or P2 that determines
the load impedance for maximum PAE, it is known by those skilled in
the art that the teachings of the invention apply to other output
power levels and output impedance values. In other embodiments of
the invention, the power amplifiers operate to supply output
signals having a power level different than the exemplary P1 and P2
power levels, and thus different load impedance values are required
to optimize the PAE of the power amplifiers.
[0189] As is known, the duplexer 1518 must provide sufficient
isolation between the signals present at its two input ports 1518A
and 1518B, since according to the CDMA protocol the transmitting
and receiving components may be simultaneously active. Thus
duplexer isolation prevents the transmitted signal from bleeding
into the receive components and the received signal from bleeding
into the transmit components. When the system 1500 is operating in
a receive mode, the duplexer 1518 must present a relatively high
impedance at the terminal 1518A. Similarly, when the system 1500 is
transmitting through the high band antenna 1502 a relatively high
impedance is seen at the terminal 1518B.
[0190] The low-band antenna 1506 is similarly connected to a
duplexer 1560 having a port 1560A connected to a serial string of a
matching network 1564 and a low-band receiver 1568. A port 1560B of
the duplexer 1560 is connected to a common terminal 1572A of a
switch 1572. A terminal 1572B of the switch 1572 is further
switchably connected to a serial string comprising a matching
network 1576 and a high-power amplifier 1580 (supplying a
relatively high-power output signal P3); a terminal 1572C is
switchably connected to a serial string comprising a matching
network 1584 and a low-power amplifier 1588 (supplying a relatively
low-power output signal P4).
[0191] The matching networks 1576 and 1584 see the impedance of the
low-band antenna as transformed through the duplexer 1560 and the
switch 1572, and transform this impedance to increase the PAE of
the operative high-power amplifier 1580 or the low-power amplifier
1588. In the presented exemplary embodiment a load impedance of
about 3 ohms maximizes the PAE of the PA 1580 at the power level of
the signal P3 and a load impedance of greater than about 3 ohms
maximizes the PAE of the PA 1588.
[0192] The impedance values set forth in FIG. 27 (and all Figures
presented herein) are merely exemplary, although it is expected
that the output impedance of a low power amplifier (1540 and 1588)
would be greater than the output impedance of a high power
amplifier (1530 and 1580). The design of the high-band and low-band
antennas, the duplexers, the receivers, the power amplifiers, and
the switches all impact the impedances seen at the matching network
terminals. Further, the power level of the power amplifier output
signals determine the load impedance that maximizes the PA PAE. It
is generally known, however, that duplexer size increases when
designed to operate into a lower impedance load or source
impedances. It is therefore preferable to use relatively large
impedances in conjunction with the duplexers of FIG. 27 to maintain
a reasonable duplexer size for use in a communications device,
especially for use in hand held communications devices.
[0193] The matching networks 1514 and 1564 are both indicated as
matching to a presented 20 ohm source impedance. But in another
embodiment the high and low band antennas 1502 and 1506 may present
different impedances at resonance and thus the matching networks
1514 and 1564 may see different source impedances for
transformation to a suitable impedance for their respective
receiver 1510 and 1568.
[0194] In one embodiment, each of the antennas 1502 and 1506
comprises an antenna presenting a relatively low impedance. In this
embodiment signal bandwidth loss is reduced compared with an
embodiment employing antennas that present a 50 ohm impedance at
resonance. Since the impedance seen from the input terminal of each
of the matching networks 1534, 1544, 1576 and 1584 is lower when
low impedance antennas are used, the difference between the input
and output impedances is reduced and the bandwidth of the impedance
transformation is therefore increased. In another embodiment the
antenna impedance is switched between receive and transmit
functions to reduce the impedance transformation ratio required
between the antenna and the receiver.
[0195] Preferably, the switches 1538 and 1572 present a
sufficiently low resistance to limit the power losses they
introduce into the signal path.
[0196] The matching networks 1514, 1534, 1544, 1576 and 1584 (and
other matching networks illustrated in the various Figures) may
comprise both impedance transformation components and signal filter
components. Further, the receivers 1510 and 1568 (and the other
receivers illustrated in the various Figures) may comprise both
receiver and filter functionalities.
[0197] In one embodiment, the components illustrated in FIG. 27 are
fabricated in a modular form, with the electronics components
disposed within a dielectric substrate and the antenna components
disposed on outer surfaces of the substrate.
[0198] FIG. 28 illustrates a system 1598 sharing certain common
elements with the system 1500 of FIG. 27 and suitable for CDMA
operation. As can be seen, the system 1598 comprises a single
antenna 1600 connected to the duplexers 1518 and 1560 through a
combiner 1602, which in one embodiment is an element of the antenna
structure. Operation of the combiner 1602 is frequency dependent
such that high band received signals are supplied from the antenna
1600 to the duplexer 1518 and low band received signals are
supplied from the antenna to the duplexer 1560. Depending on the
operating frequency and the signal power required, one of the
high-power amplifiers 1530 and 1580 (preferably optimized for
supplying a signal in the high-band spectrum) or the low-power
amplifiers 1540 and 1588 (preferably optimized for supplying a
signal in the low-band spectrum) can supply a signal to the
combiner (through their respective duplexers 1518 and 1560) for
transmission by the antenna 1600.
[0199] FIG. 29 illustrates a system 1720 including a receive
antenna 1721 and a transmit antenna 1722 appropriately isolated by
an isolation structure 1723 as further described below. Either the
high-band receiver 1510 or the low-band receiver 1568 is connected
to the receiving antenna 1721 via a filter 1724, a switch 1725 and
respective matching networks 1726 and 1728. The matching networks
may be required to match an impedance of the receivers 1510 and
1568 (which may not be identical) to a source impedance seen
looking into the switch 1725. Since the receive antenna will likely
present a first impedance when operating in the high frequency band
and a second different impedance when operating in the low
frequency band, the matching networks 1726 and 1728 typically match
to different impedance values Z10 and Z11 ohms as indicated.
[0200] As can be appreciated, the system 1720 is applicable to CDMA
systems where the switch 1725 is controlled to a state to receive
signals depending upon whether the signal is in the CDMA high band
(1930-1990 MHz) or the CDMA low band (869-894 MHz).
[0201] A filter 1740, a switch 1744 and respective matching
networks 1748 and 1752 are responsive to a signal supplied by a
high-band power amplifier 1754 and by a low-band power amplifier
1756.
[0202] The frequency-dependent filters 1724 and 1740 can provide
additional isolation between the receive and transmit operating
frequencies, i.e., in addition to the isolation provided by the
isolation structure 1723.
[0203] The power amplifiers 1754 and 1756 may operate at different
output power levels and therefore to maximize the PAE they may be
operated at different load impedances, Z12 and Z13 ohms as
indicated in FIG. 29. Thus the matching network 1748 transforms an
impedance of Z14 ohms to Z12 ohms for the high band-power amplifier
1754 and the matching network 1752 transforms an impedance of Z15
ohms to Z13 ohms for the low-band power amplifier 1756. Typically,
the transmit antenna 1722 presents a high-band impedance when
operating at a high-band frequency and a different low-band
impedance when operating at a low-band frequency. Thus the
impedances Z14 and Z15 may not be equal.
[0204] In another embodiment of the invention, the matching
networks 1748 and 1752 are controllable to present different load
impedances to the power amplifiers 1754 and 1756 to optimize or at
least improve the PAE of each power amplifier 1754 and 1756 (i.e.,
improve the PAE or efficiency over the efficiency absent use of the
controllable matching networks 1748 and 1752.)
[0205] In one embodiment of the system 1720, the transmit and
receive antennas 1721 and 1722, the filters 1723 and 1740, and the
switches 1724 and 1744 can be incorporated into a single antenna
module. In another embodiment, only the receive and transmit
antennas 1721 and 1722 are incorporated into the module.
[0206] FIG. 30 illustrates a system 1757 derived from the system
1720 of FIG. 29 and further comprising a high-band high-power PA
1760, a high-band low-power PA 1761, a low-band high-power PA 1762
and a low-band low-power PA 1763 and their respective matching
networks 1764, 1765, 1766 and 1767. A switch 1768 selectably
connects one of the PA's 1760, 1761, 1762 and 1763 to the transmit
antenna 1722 via the filter 1740. As in the embodiments discussed
elsewhere herein, the matching networks 1764, 1765, 1766 and 1767
are configured (either a fixed or a controllable configuration) to
provide a load impedance to the PA's 1760, 1761, 1762 and 1763 to
maximize the PAE of each PA according to the operating power level
(or another power-related parameter, for example, a power amplifier
output power, an operating frequency of a communications device
operative with the system 1757 wherein operation of the power
amplifiers is responsive to the operating frequency of the
communications device or a voltage standing wave ratio on a
conductive path between the power amplifier and the transmitting
antenna) of the PA.
[0207] FIG. 31 illustrates an example of the isolation structure
1723 of FIGS. 29 and 30. A dielectric substrate 1770 supports an
antenna 1772 (in this exemplary embodiment the antenna 1772
comprises a meanderline antenna) and a dielectric substrate 1776
supports an antenna 1778 (in this exemplary embodiment the antenna
1778 comprises a PIFA antenna). An isolation structure comprises a
conductive structure 1880 disposed between the substrates 1770 and
1776. In the illustrated embodiment the conductive structure
comprises a generally U-shaped conductive structure. In another
embodiment (not illustrated) the conductive structure comprises a
sheet disposed between the substrates 1770 and 1776. In still
another embodiment (not illustrated) the substrates 1770 and 1776
are replaced by a dielectric sheet (a flex film dielectric sheet,
for example) with a conductive surface sandwiched between the
dielectric sheets. The antennas 1772 and 1778 are disposed on
outside surfaces of the dielectric sheets.
[0208] In another embodiment of the systems 1720 and 1757 of FIGS.
29 and 30, isolation between the receive and transmit antennas 1721
and 1722 is provided by signal polarization diversity, i.e. the two
antennas 1721 and 1722 propagate signals with different signal
polarizations to achieve the desired isolation. For example, a
first antenna propagating a horizontally polarized signal and a
second antenna propagating a vertically polarized signal may
provide the desired signal isolation in lieu of the isolation
structure 1723 in FIGS. 29 and 30.
[0209] A system 1850 of FIG. 32 is suitable for use with any
protocol employing a time division multiple access scheme, such as
the GSM protocol, to separate transmit and receive operations. A
switchplexer 1851 comprises a plurality of selectable terminals
each responsive to a matching network/filter 1852, 1854, 1856 and
1858. The matching network/filter 1852 and 1854 are responsive
respectively to a high-band receiver 1860 and a low-band receiver
1868. In another embodiment (not illustrated) the system 1850
further comprises a GPS receiver. The matching network/filters 1856
and 1858 are responsive respectively to a high-power amplifier 1870
and a low-power amplifier 1872. In another embodiment the PA's 1870
and 1872 are combined (e.g., using CMOS (complimentary metal oxide
semiconductor field effect transistors) technologies) with a
corresponding single matching network/filter configuration.
[0210] When the system 1850 is operative with a communications
device, a configuration of a switch common terminal 1851A is
controlled according to the operational mode (receive or transmit)
and the operating frequency (high band or low band) of the
communications device. The common terminal 1851A is connected to a
matching network/combiner 1875 to supply the selected signal to
antennas 1880/1884 in the transmit mode or to receive signals from
the antennas 1880/1884 in the receive mode. The matching
network/combiner 1875 may comprise a high and low pass filter to
direct the high and low band frequency signals as desired.
Alternatively, the functionality of the matching network/combiner
1875 can be integrated with the antennas 1880 and 1884 using
parasitic coupling or direct coupling of different resonant antenna
elements.
[0211] In the receive mode the matching network/combiner 1875
supplies the received signal to the common terminal 1851A of the
switchplexer 1851 for feeding to either the high-band receiver 1860
via the matching network/filter 1852 or to the low-band receiver
1868 via the matching network/filter 1854, as determined by the
state of the switchplexer 1851. The matching networks/filters 1852
and 1854 transform the source impedance they see to the input
impedance of the respective receivers 1860 and 1868.
[0212] In the transmitting mode, the signal to be transmitted is
supplied from either the high-power PA 1870 or the low power PA
1872. Based on their operating output power, the maximum PAE of the
power amplifiers 1870 and 1872 is achieved when the load impedance
is Z20 and Z21 ohms, as indicated, respectively. The matching
network/filter 1856 provides the load impedance of Z20 ohms to the
PA 1870 by transforming its source impedance (as seen looking into
the switchplexer 1851 from the matching network/filter 1856) to Z20
ohms. Similarly, the matching element/filter 1858 presents a load
impedance of Z21 ohms by transforming its source impedance (as seen
looking into the switchplexer 1851 from the matching network/filter
1858) to Z21 ohms.
[0213] Within the system 1850, an impedance of each antenna 1880
and 1884 is controllable responsive to an antenna impedance
controller 1888 further responsive to a control signal. As
described above, controlling the antenna impedance to provide an
optimal load impedance for the power amplifiers 1870 and 1872
improves the power amplifier efficiency and hence extends battery
life of the communications device in which the system 1850 is
embedded. The control signal can be derived from a baseband
controller representative of the PA output power or by a band
select signal that identifies the currently operative band for the
communications device. In one embodiment the antennas 1880 and 1884
are formed on a common substrate or formed on separate substrates
and bonded together, forming an antenna module. The antenna module
may be referred to as a variable impedance antenna module since the
impedance controller 1888 controls the impedance presented by the
antennas 1880 and 1884.
[0214] Thus several techniques are presented for controlling the
load impedance of the PA's 1870 and 1872 to maximize the PAE. Each
of the matching networks/filters 1856 and 1858 can be controlled in
real time responsive to the output power of the respective PA to
achieve a desired or maximum PAE. Alternatively, each of the
matching networks/filters 1856 and 1858 can provide a fixed load
impedance for the respective PA that will maximize the PAE based on
an average or expected value of the output power. Alternatively,
the matching networks/filters 1856 and 1858 operate as band pass
filters and provide a fixed impedance suitable for the switchplexer
1851, while the antenna controller 1888 presents an impedance to
maximize the PAE.
[0215] Thus to improve the efficiency of the power amplifiers 1870
and 1872, the load impedance of each can be controlled by operation
of the respective matching network/filter 1856 and 1858. Further,
the antenna impedance can be controlled by the impedance controller
1888 to present a different source impedance to the matching
networks/filters 1856 and 1858, which in turn transform the source
impedance to a PA load impedance to maximizes the PAE for each PA
1870 and 1872.
[0216] The number of receiving and transmitting elements in the
system 1850 can be easily extended as indicated. In one embodiment,
the receivers, power amplifiers and matching networks/filters can
be manufactured in the form of a module.
[0217] FIG. 33 illustrates a system 1900 sharing common elements
with the system 1850 of FIG. 32. In one embodiment, the system 1900
employs a non-50 ohm signal transmission chain as indicated by the
exemplary ".about.20.OMEGA." designation between the switchplexer
common terminal 1851A and a combiner 1904. Antennas presenting such
a "low" impedance are referred to as low impedance antennas and are
capable of providing a low impedance over their operating
bandwidth. In one embodiment the antennas 1880 and 1884 are formed
on a common substrate or formed on separate substrates and bonded
together, forming an antenna module. The antenna module may be
referred to as a low impedance antenna module.
[0218] In the receiving mode the matching networks/filters 1852 and
1854 transform their source impedance to the load impedance for the
high-band and low-band receivers 1860 and 1868. Also, the matching
networks 1856 and 1858 can transform their source impedance to a
load impedance that controls or maximizes the PAE (or efficiency)
for the respective power amplifier 1870 and 1872. Further, in one
embodiment the matching networks/filters 1856 and 1858 provide a
controllable range of impedance transformations to provide a range
of load impedances for the power amplifiers 1870 and 1872.
[0219] Certain elements within the various embodiments presented in
FIGS. 27-33 can be formed or implemented in a module by forming or
mounting multiple components on a common substrate. In particular,
the high and low band antennas 1880 and 1884, the combiner 1875 and
the impedance controller 1888 of FIG. 32 can be physically combined
into a modular element. Similarly, the high band antenna 1880, the
low band antenna 1884 and the combiner 1904 can be combined to form
a module in the embodiment of FIG. 33. The switchplexer 1851 can
also be included within the module. As those skilled in the art
recognize, other elements (switches and filters, for example) can
be included within such a module to simplify design and assembly of
the presented systems.
[0220] The modular implementation provides fixed interconnections
and parts placement that avoids performance degradation from
transmission line (conductor) lengths variations, filter
characteristic variations and parasitic effects due to coupling
between components. Component characteristics are matched at the
time of module design, thereby limiting mismatch losses. The fixed
phase shift through the radio frequency component chain at each
operating frequency is known and can be compensated as required.
The fixed phase shift is also beneficial for PA stability over
presented mismatches due to environmental effects and changes
(e.g., the proximity effect).
[0221] The module's radio frequency portion (i.e., the front end
where many of the physical layout-induced performance variations
arise) offers known performance characteristics, reducing design
time of the communications device and therefore time to market.
[0222] In certain industrial designs (e.g., laptop computers) the
modular approach can reduce transmission line length, and thus
losses in the transmission lines, as the antenna(s) and power
amplifier(s) are located in proximate relationship. A high-speed
bus (such as an optical fiber) can be used to supply the signal to
be transmitted from the baseband/modulating components to the power
amplifiers.
[0223] Thus the modularized system offers the communications device
designer a physically stable and operationally predictable
component for insertion into a communications device.
[0224] Although the power amplifiers of the various presented
embodiments have been described as supplying a signal having a
discrete output power level (e.g., signals P1 and P2) that
determines the load impedance for maximum PAE, the teachings of the
invention are not so limited and can be applied to other output
power levels and to power amplifiers capable of supplying a signal
having a power within a range of power levels. The load impedance
that maximizes the PAE is different dependent on the PA output
power of the power amplifier. Therefore, the various presented
matching networks, if capable of transforming only a single source
impedance to an output impedance may not assure a maximum PAE at
all output power levels. In another embodiment a matching network
that can transform the source impedance to a selectable output
impedance may be preferred to maximize the PAE at all possible PA
output power levels.
[0225] FIG. 34 illustrates a dual band communications apparatus
2000 comprising the high band receiver 1860 and a high band power
amplifier 2006 selectably connected to a high pass filter 2008 via
a transmit/receive switching element 2012. Responsive to a
condition of the switching element 2012, the antenna 1880,
connected to the filter 2008, supplies a received signal to the
high band receiver 1860 or transmits a signal supplied by the power
amplifier 2006. When incorporated into a multiband communications
device, the operating mode of the communications apparatus 2000
(and the condition of the switching element 2012) is controlled by
a signal representing the operating mode (receiving or
transmitting) of the communications device.
[0226] For low band operation, the communications apparatus 2000
further comprises the low band receiver 1868, a low band power
amplifier 2020, a switching element 2022, a low pass filter 2026
and the low band antenna 1884. The components associated with low
band operation operate similarly to those associated with high band
operation as described above.
[0227] Use of the filters 2008 and 2026 and the dedicated high band
and low band antennas 1880 and 1884 in the communications apparatus
2000 avoids the need for a switchplexer, such as the switchplexer
1851 illustrated in FIG. 32. The switchplexer is a relatively
expensive element and therefore its elimination is a cost reduction
(and space reduction) advantage, especially for low-cost
communications apparatuses. Additionally, use of the high band and
the low band antennas 1880 and 1884, respectively, allows each to
be designed for optimum performance in its operating band.
[0228] Preferably, each antenna 1880 and 1884 is designed for a 50
ohm match within its operating band. Typically, the power
amplifiers 2006 and 2020 prefer a low load impedance and the
receivers 1860 and 1868 prefer a higher (source) impedance. In the
embodiment of FIG. 34, the high band receiver 1860 and the high
band power amplifier 2006 are matched to a fixed impedance of 50
ohms of the antenna 1880 and any intervening components, such as
the filter 2008 and the switching element 2012. Similarly, the low
band receiver 1868 and the low band power amplifier 2020 are
matched to a fixed impedance of 50 ohms of the antenna 1884 and any
intervening components, such as the filter 2026 and the switching
element 2008.
[0229] In yet another embodiment, the impedance presented by the
antennas 1880 and 1884 are controllable, for example by use of the
impedance controller 1888 of FIG. 32, to control the load impedance
presented to the respective power amplifier 2006 and 2020 to
control the efficiency of the power amplifiers 2006 and 2020.
[0230] FIG. 35 illustrates a communications apparatus 2040
comprising two high band antennas 2008 (one for transmitting and
one for receiving), two low band antennas 1884 (one for
transmitting and one for receiving), the high pass filter 2008 and
the low pass filter 2026. The four antennas and respective filters
provide an equivalent functionality to the diplexer/switchplexer
and the switches of the embodiments described above and can be
optimized for performance with the associated power amplifier or
receiver. Another embodiment includes the impedance controller
1888, to control the impedance of the antennas 1880 and 1884 as
presented to the respective power amplifier 2006 and 2020 to
control the efficiency of the power amplifiers 2006 and 2020.
[0231] The presented embodiments describe the inventions with
reference to the GSM and CDMA air protocols, and in particular, the
receivers, power amplifiers, antennas, etc., are described as
operating according to those protocols. But the inventions are not
limited to those protocols, as the teachings can extended for use
with EGSM, PCS and DCS, 802.11x and other protocols.
[0232] While the present invention has been described with
reference to preferred embodiments, it will be understood by those
skilled in the art that various changes may be made and equivalent
elements may be substituted for the elements thereof without
departing from the scope of the invention. The scope of the present
invention further includes any combination of elements from the
various embodiments set forth herein. In addition, modifications
may be made to adapt a particular situation to the teachings of the
present invention without departing from its essential scope.
Therefore, it is intended that the invention not be limited to the
particular embodiments disclosed, but that the invention will
include all embodiments falling within the scope of the appended
claims.
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