U.S. patent application number 12/034916 was filed with the patent office on 2008-11-13 for control apparatus for electric vehicles.
This patent application is currently assigned to DENSO CORPORATION. Invention is credited to Tsuneyuki EGAMI, Shingo KAWASAKI.
Application Number | 20080281480 12/034916 |
Document ID | / |
Family ID | 39970277 |
Filed Date | 2008-11-13 |
United States Patent
Application |
20080281480 |
Kind Code |
A1 |
EGAMI; Tsuneyuki ; et
al. |
November 13, 2008 |
CONTROL APPARATUS FOR ELECTRIC VEHICLES
Abstract
A motor control unit controls the input electric power of a MG
unit to thereby suppress variations of a system voltage and
stabilize the system voltage. The torque control of an AC motor and
the input electric power control of the MG unit are executed
independently from each other, so that the torque control and the
input electric power control are stabilized. Further, torque
variation zeroing control for correcting a phase of a pulse
waveform voltage is executed so that a difference between a first
estimated torque computed based on a torque control detection
current vector of the AC motor and a second estimated torque
computed based on a detection motor current vector is reduced to
zero. Thus, uncomfortable torque variation is suppressed in a
transient condition of the input electric power control of the MG
unit.
Inventors: |
EGAMI; Tsuneyuki;
(Gamagori-city, JP) ; KAWASAKI; Shingo;
(Kariya-city, JP) |
Correspondence
Address: |
NIXON & VANDERHYE, PC
901 NORTH GLEBE ROAD, 11TH FLOOR
ARLINGTON
VA
22203
US
|
Assignee: |
DENSO CORPORATION
Kariya-city
JP
|
Family ID: |
39970277 |
Appl. No.: |
12/034916 |
Filed: |
February 21, 2008 |
Current U.S.
Class: |
701/22 ;
180/65.31; 180/65.8; 318/148; 903/906 |
Current CPC
Class: |
B60L 15/025 20130101;
B60L 2210/14 20130101; B60W 10/08 20130101; B60W 20/00 20130101;
B60W 2510/086 20130101; B60L 2270/145 20130101; B60L 50/16
20190201; B60L 2210/20 20130101; B60L 2220/14 20130101; B60K 6/445
20130101; Y02T 10/7072 20130101; B60W 2510/083 20130101; Y10S
903/906 20130101; B60L 50/13 20190201; B60W 20/10 20130101; Y02T
10/64 20130101; B60L 50/61 20190201; Y02T 10/70 20130101; H02P
21/05 20130101; Y02T 10/72 20130101; Y02T 10/62 20130101; B60W
2710/08 20130101 |
Class at
Publication: |
701/22 ;
180/65.8; 318/148; 180/65.3; 903/942; 903/906 |
International
Class: |
B60W 10/08 20060101
B60W010/08; B60L 9/18 20060101 B60L009/18; B60L 11/08 20060101
B60L011/08; B60W 20/00 20060101 B60W020/00 |
Foreign Application Data
Date |
Code |
Application Number |
May 9, 2007 |
JP |
2007-124336 |
Claims
1. A control apparatus for an electric vehicle comprising: a
conversion means that converts a voltage supplied by a DC power
source into a system voltage appearing on a power supply line; an
MG unit that includes an inverter connected to the power supply
line and drives an AC motor; a torque and power control means for
controlling a torque of the AC motor and an input electric power of
the MG unit by supplying the AC motor with a pulse waveform
voltage, which commutates the AC motor at every predetermined
electric angle, based on a torque command value of the AC motor and
an input electric power command value of the MG unit; and a system
voltage control means for stabilizing the system voltage by
outputting the input electric power command value to the torque and
power control means, so that a system voltage variation which is a
variation from a target value of the system voltage is suppressed
by input electric power control of the MG unit, wherein the torque
and power control means includes: current separation means for
separating a torque control detection current related to torque
control of the AC motor from a detection motor current flowing in
the AC motor; torque control means for computing a first estimated
torque of the AC motor based on the torque control detection
current, setting a torque control phase command value of the pulse
waveform voltage based on the first estimated torque and the torque
command value, and outputting, as torque control pulse waveform
information, both of the torque control phase command value and a
predetermined duty ratio; power control means for setting and
outputting, as electric power control pulse waveform information,
both a phase correction value and a duty ratio correction value,
the electric power control pulse waveform information being for
correcting the torque control pulse waveform information so that
the input electric power of the MG unit is controlled to the input
electric power command value independently of the input electric
power of the MG unit required to generate torque of the AC motor
based on the torque command value and the input electric power
command value; pulse waveform voltage generation means for
outputting to the inverter a pulse waveform voltage signal, which
is to be applied to the AC motor, based on the torque control pulse
waveform information, the electric power control pulse waveform
information and the electric angle of the AC motor; and torque
variation zeroing control means for computing a second estimated
torque of the AC motor based on the detection motor current and
controlling a difference between the first estimated torque and the
second estimated torque to zero substantially, thereby to suppress
torque variation of the AC motor in a transient condition of input
electric power control of the MG unit.
2. The control apparatus according to claim 1, wherein the current
separation means computes the torque control detection current
based on at least a basic waveform voltage of the pulse waveform
voltage to be applied to the AC motor, a basic waveform current of
the detection motor current and the torque control pulse waveform
information.
Description
CROSS REFERENCE TO RELATED APPLICATION
[0001] This application is based on and incorporates herein by
reference Japanese Patent Application No. 2007-124336 filed on May
9, 2007.
FIELD OF THE INVENTION
[0002] The present invention relates to a control apparatus for an
electric vehicle including a system for converting a voltage
supplied by a DC power source into a system voltage by using a
voltage converter and for driving an AC motor by applying the
system voltage to the AC motor through an inverter.
BACKGROUND OF THE INVENTION
[0003] As disclosed in documents such as U.S. Pat. No. 7,099,756
(JP 2004-274945A), in an electric vehicle having AC motors mounted
therein to serve as an energy source of the vehicle, the AC motors
are each capable of serving as a motor for driving wheels of the
vehicle as well as a motor driven by an engine to generate power.
As the above system, a control apparatus for the electric vehicle
includes a voltage boosting converter for raising a voltage
supplied by a DC power source, which is implemented by a secondary
battery, to a high DC voltage appearing on a power supply line
connected to the AC motors through inverters. The inverters are
capable of serving as a component for converting the raised DC
voltage appearing on the power supply line into an AC voltage for
driving one of the AC motors as well as a component for converting
the AC voltage into a DC voltage supplied back or restored to the
secondary battery through the voltage boosting converter, which
lowers the level of the DC voltage.
[0004] In the above system, in order to stabilize the voltage
appearing on the power supply line, the voltage boosting converter
controls the voltage appearing on the power supply line to a target
voltage. Further, at the same time, a smoothing capacitor connected
to the power supply line smoothes the voltage appearing on the
power supply line.
[0005] When a relation between electric power driving one of the AC
motors and electric power generated by the other AC motor
considerably varies due to changes in vehicle operating state or
another reason, however, a voltage variation caused by a change in
such relation as a voltage variation of the power supply line
cannot be absorbed by the voltage boosting converter and/or the
smoothing capacitor. Thus, the voltage appearing on the power
supply line becomes excessively high. As a result, it is likely
that electronic equipment connected to the power supply line is
damaged. In order to cope with this problem, there is provided a
method for enhancing the effect of stabilizing the voltage
appearing on the power supply line by using an improved voltage
boosting converter with better performance and a smoothing
capacitor with a larger capacitance. By adoption of this method,
however, the voltage boosting converter with better performance and
the smoothing capacitor with a larger capacitance will inevitably
raise the cost of the control apparatus for an electric vehicle.
Thus, demands for a system having a small size and a low cost
cannot be met. The above relation between the power driving one of
the AC motors and the power generated by the other AC motor is also
referred to as a balance of power between the power driving one of
the AC motors and the power generated by the other AC motor.
[0006] It is proposed for controlling the inverter to make a sum of
energies (or balance of electric power) of the two AC motors equal
to 0 at the time the connection between the DC power source and the
voltage boosting converter is cut off by using a relay in the event
of a failure occurring in the DC power source. However, this method
is provided as a countermeasure to a failure occurring in the DC
power source and is capable of enhancing the effect of stabilizing
the voltage appearing on the power supply line in a normal state of
the power supply. In addition, even if an attempt is made to
control the inverter to make the sum of energies (or the balance of
power) of the two AC motors equal to 0 in a normal state, it is
difficult to control the inverter to make the sum of energies (or
the balance of power) of the two AC motors equal to 0 in the
following cases.
[0007] In the first place, one of the AC motors is linked to a
driving shaft of the electric vehicle and the other AC motor is
linked to an output shaft of the internal combustion engine, that
is, the two AC motors are linked to members having different
operations. In the second place, the effect of a processing delay
of the control executed on the inverter becomes larger, for
example, during a transient condition in which the operating state
of the electric vehicle changes. The AC motor linked to the
internal combustion engine is not capable of obviating power
variations caused by changes of a torque generated by the internal
combustion engine. This fact makes it even more difficult to
control the inverter to make the sum of energies of the two AC
motors equal to zero (0).
SUMMARY OF THE INVENTION
[0008] It is thus an object of the present invention to improve a
control apparatus for an electric vehicle to be capable of
stabilizing a voltage appearing on a power supply line in small
size and low cost and to be capable of reducing a torque variation
to nearly zero in a transient condition of controlling an input
power to a motor unit.
[0009] According to one aspect, in a control apparatus for an
electric vehicle, a voltage supplied by a DC power source into a
system voltage appearing on a power supply line is converted and an
MG unit includes an inverter connected to the power supply line and
drives an AC motor. A torque of the AC motor and an input electric
power of the MG unit are controlled by supplying the AC motor with
a pulse waveform voltage, which commutates the AC motor at every
predetermined electric angle, based on a torque command value of
the AC motor and an input electric power command value of the MG
unit. The system voltage is stabilized by outputting the input
electric power command value to the torque and power control means,
so that a system voltage variation which is a variation from a
target value of the system voltage is suppressed by input electric
power control of the MG unit.
[0010] Specifically, in controlling the torque and the input
electric power of the MG unit, a torque control detection current
related to torque control of the AC motor is separated from a
detection motor current flowing in the AC motor. A first estimated
torque of the AC motor is computed based on the torque control
detection current, a torque control phase command value of the
pulse waveform voltage is set based on the first estimated torque
and the torque command value, and both of the torque control phase
command value and a predetermined duty ratio are output as torque
control pulse waveform information. Both a phase correction value
and a duty ratio correction value are set and output as electric
power control pulse waveform information. The electric power
control pulse waveform information is for correcting the torque
control pulse waveform information so that the input electric power
of the MG unit is controlled to the input electric power command
value independently of the input electric power of the MG unit
required to generate torque of the AC motor based on the torque
command value and the input electric power command value. A pulse
waveform voltage signal, which is to be applied to the AC motor, is
output to the inverter based on the torque control pulse waveform
information, the electric power control pulse waveform information
and the electric angle of the AC motor. A second estimated torque
of the AC motor is computed based on the detection motor current,
and a difference between the first estimated torque and the second
estimated torque is controlled to zero substantially, thereby to
suppress torque variation of the AC motor in a transient condition
of input electric power control of the MG unit.
BRIEF DESCRIPTION OF THE DRAWINGS
[0011] The above and other objects, features and advantages of the
present invention will become more apparent from the following
detailed description made with reference to the accompanying
drawings. In the drawings:
[0012] FIG. 1 is a block diagram showing a driving system for an
electric vehicle in accordance with one embodiment of the present
invention;
[0013] FIG. 2 is a block diagram showing a motor control apparatus
of the driving system for an electric vehicle shown in FIG. 1;
[0014] FIG. 3 is a block diagram showing a torque and power control
unit of the motor control apparatus shown in FIG. 2;
[0015] FIG. 4 is a graph showing a method of separating a detection
current for torque control from a detection motor current; and
[0016] FIG. 5 is a block diagram showing a torque variation zeroing
control unit of the torque and power control part shown in FIG.
3.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT
[0017] Referring first to FIG. 1, an electric vehicle 11 has an
internal combustion engine 12 in addition to a first AC motor 13
and a second AC motor 14. Thus, the electric vehicle 11 is an
engine/motor hybrid vehicle. The engine 12 and the second AC motor
14 are employed as drive power sources for driving the electric
vehicle 11. Power generated by a crankshaft 15 of the engine 12 is
divided into two paths by a planetary gear set 16. The planetary
gear set 16 includes a sun gear 17, a planetary gear 18 and a ring
gear 19. The sun gear 17 rotates at its radial center. The
planetary gear 18 rotates along a circumference external to the sun
gear 17 while revolving around its radial center The ring gear 19
rotates along a circumference external to the planetary gear 18.
The planetary gear 18 is linked to the crankshaft 15 of the engine
12 through a carrier not shown in the figure. On the other hand,
the ring gear 19 is linked to a rotation shaft of the second AC
motor 14. The sun gear 17 is linked to the first AC motor 13.
[0018] A secondary battery serving as a DC power source 20 is
connected to a voltage boosting converter 21. The voltage boosting
converter 21 is a component having a function for increasing a DC
voltage output by the DC power source 20 in order to generate a DC
system voltage supplied between an electric power supply line 22
and a ground line 23 as well as a function for decreasing the
system voltage in order to return or restore power to the DC power
source 20. A smoothing capacitor 24 for smoothing the system
voltage and a voltage sensor 25 serving as a voltage detection
means for detecting a value of the system voltage are connected
between the power supply line 22 and the ground line 23. A current
sensor 26 serving as a current detection means is placed on the
power supply line 22 as a means for detecting a current flowing
through the power supply line 22.
[0019] In addition, a three-phase first inverter 27 and a
three-phase second inverter 28 are also connected between the power
supply line 22 and the ground line 23. The three-phase first
inverter 27 and the three-phase second inverter 28 are each a
three-phase inverter of a voltage control type. The three-phase
first inverter 27 drives the first AC motor 13, whereas the
three-phase second inverter 28 drives the second AC motor 14. The
three-phase first inverter 27 and the first AC motor 13 form a
first motor driving unit 29, which operates as a first MG unit 29.
Similarly, the three-phase second inverter 28 and the second AC
motor 14 form a second motor driving unit 30, which operates as a
second MG unit 30.
[0020] A main control unit 31 is a computer for executing overall
control on the electric vehicle. The main control unit 31 acquires
signals output by a variety of sensors and switches in order to
detect an operating state of the electric vehicle. The sensors and
the switches include an accelerator sensor 32, a shift position
switch 33, a brake switch 34 and a vehicle speed sensor 35. The
accelerator sensor 32 is a sensor for detecting an accelerator
operation amount representing an operation amount of an
acceleration pedal. The shift position switch 33 is a sensor for
detecting gear shift position of the electric vehicle The gear
shift position can be a parking position (P), a reverse driving
position (R), a neutral position (N) or a forward driving position
(D). The brake switch 34 is a switch for detecting a braking
operation. The vehicle speed sensor 35 is a sensor for detecting a
value of the travel speed of the electric vehicle. The main control
unit 31 exchanges control and data signals with an engine control
unit 36 and a motor control unit 374 driving the engine control
unit 36 and the motor control unit 37 to control the engine 12, the
first AC motor 13 and the second AC motor 14 in accordance with the
operating state of the electric vehicle. The engine control unit 36
is for controlling the operation of the engine 12, whereas the
motor control unit 37 is for controlling the operations of the
first AC motor 13 and the second AC motor 14.
[0021] Next, control of the first AC motor 13 and the second AC
motor 14 is described by referring to FIGS. 2 to 5. The first AC
motor 13 and the second AC motor 14 are each a three-phase
permanent-magnet synchronous motor having a permanent magnet in its
inside. The first AC motor 13 and the second AC motor 14 have
respectively rotor rotation position sensors 39 and 40 each used
for detecting the rotation position of the rotor of the motor. On
the basis of three-phase voltage command signals UU1, UV1 and UW1
output by the motor control unit 37, the first inverter 27 of the
voltage control type converts the DC system voltage appearing on
the power supply line 22 into three-phase AC voltages U1, V1 and W1
for driving the first AC motor 13. The DC system voltage appearing
on the power supply line 22 is generated by the voltage boosting
converter 21. A U-phase current sensor 41 is a sensor for detecting
a U-phase current iU1 of the first AC motor 13, whereas a W-phase
current sensor 42 is a sensor for detecting a W-phase current iW1
of the first AC motor 13.
[0022] Similarly, on the basis of three-phase voltage command
signals UU2, UV2 and UW2 output by the motor control unit 37, the
three-phase second inverter 28 of the voltage control type converts
the DC system voltage appearing on the power supply line 22 into
three-phase AC voltages U2, V2 and W2 for driving the second AC
motor 14. A U-phase current sensor 43 is a sensor for detecting a
U-phase current iU2 of the second AC motor 14, whereas a W-phase
current sensor 44 is a sensor for detecting a W-phase current iW2
of the second AC motor 14.
[0023] It is to be noted that the first AC motor 13 and the second
AC motor 14 each also function as an electric power generator, when
the first AC motor 13 and the second AC motor 14 are driven by the
three-phase first inverter 27 and the three-phase second inverter
28 respectively to generate a negative torque. For example, when
the electric vehicle 11 is being decelerated, AC electric power
generated by the second AC motor 14 as kinetic energy is converted
into DC power by the three-phase second inverter 28 and the DC
power is stored in the DC power source 20. Normally, a portion of
mechanical power of the engine 12 is transferred to the first AC
motor 13 by way of the planetary gear 18, causing the first AC
motor 13 to operate as a generator for generating electric power
corresponding to the portion of the power of the engine 12. The
electric power generated by the first AC motor 13 is supplied to
the second AC motor 14, causing the second AC motor 14 to operate
as a motor. The power of the engine 12 is divided into two paths by
the planetary gear set 16. When a torque applied to the ring gear
19 of the planetary gear set 16 is greater than a torque required
by a running operation of the electric vehicle, the first AC motor
13 functions as a motor, drawing power for the engine 12. In this
case, the second AC motor 14 functions as a generator generating
power to be supplied to the first AC motor 13. Thus, each of the
first AC motor 13 and the second AC motor 14 operates as a
motor/generator (MG).
[0024] In the MG control, the motor control unit 37 executes torque
control for the first AC motor 13, torque control for the second AC
motor 14, and the system voltage stabilization control for
controlling the input power of the second AC motor 14 so that
variation or fluctuation in the system voltage may be suppressed.
The motor control unit 37 executes the torque control for the
second AC motor 14 and the input power control for the second MG
unit 30 independently from each other. In this instance, the motor
control unit 37 controls the second AC motor 14 not to vary its
torque in the transient condition of the input power control of the
second MG unit 30. For this purpose, the motor control unit 37
computes a first estimated torque of the second AC motor 14 based
on a torque control detection current (detected current for torque
control) related to the torque control of the second AC motor 14,
and also computes a second estimated torque of the second AC motor
14 based on a detection motor current (detected motor current)
flowing in the second AC motor 14. The motor control unit 37 then
executes torque variation zeroing control so that a difference
between the first estimated torque and the second estimated torque
is controlled to zero substantially.
[0025] The motor control unit 37 executes motor control (torque
control, system voltage stabilization control) and conversion power
control as described below.
(Motor Control)
[0026] When the smoothing capacitor 24 has been sufficiently
pre-charged, that is, pre-charging the smoothing capacitor 24 has
been completed, after the start of system operation, the motor
control unit 37 releases the motor control system from the
shut-down state and executes the motor control (torque control,
system voltage stabilization control).
[0027] As shown in FIG. 2, in execution of the torque control on
the first AC motor 13, the motor control unit 37 generates the
three-phase voltage command signals UU1, UV1 and UW1 by a
sinusoidal-waveform PWM control method on the basis of a torque
command value T1* output by the main control unit 31, the U-phase
current iU1 and the W-phase current iW1 of the first AC motor 13 as
well as the rotor rotation position .theta.1 of the first AC motor
13 as described below. The U-phase current iU1 and the W-phase
current iW1 are signals output by the current sensors 41 and 42
respectively, whereas the rotor rotation position .theta.1 is a
signal output by the rotor rotation position sensor 39.
[0028] The signal output by the rotor rotation position sensor 39
as the signal representing the rotor rotation position .theta.1 of
the first AC motor 13 is supplied to a first rotation speed
computation unit 45 for computing a first rotation speed N1 of the
first AC motor 13. Then, in order to apply current feedback control
to each of a d-axis current id1 and a q-axis current iq1
independently of each other in the d-q coordinate system set as a
rotation coordinate system of the rotor of the first AC motor 13, a
first torque control current computation unit 46 computes a torque
control current vector it1* representing a d-axis torque control
current idt1* and a q-axis torque control current iqt1* by using
typically map data or a mathematical equation as a vector according
to the torque command value T1* and the rotation speed N1 of the
first AC motor 13.
[0029] Subsequently a first current control unit 47 computes an
actual current vector i1 (d-axis current id1 and the q-axis current
iq1) on the basis of the U-phase current iU1 and W-phase current
iW1 of the first AC motor 13 as well as the rotor rotation position
.theta.1 of the first AC motor 13 as described below. As described
above, the U-phase current iU1 and the W-phase current iW1 are
signals output by the current sensors 41 and 42 respectively,
whereas the rotor rotation position .theta.1 is the signal output
by the rotor rotation position sensor 39. Then, the first current
control unit 47 computes a d-axis command voltage Vd1* by execution
of proportional-and-integral (P-I) control for reducing a
difference .DELTA.id1 between the d-axis torque control current
idt1* and an actual d-axis current id1, and computes a q-axis
command voltage Vq1* by execution of P-I control for reducing a
difference .DELTA.iq1 between the q-axis torque control current
iqt1* and an actual q-axis detection motor current iq1. Finally,
the first current control unit 47 converts the d-axis command
voltage Vd1* and the q-axis command voltage Vq1* into the
three-phase voltages and further to pulse-width-modulated (PWM)
three-phase voltage command signals UU1, UV1 and UW1, and then
outputs the three-phase voltage command signals UU1, UV1 and UW1 to
the first inverter 27.
[0030] Thus, the torque control for the first AC motor 13 is
executed to realize the torque command value T1* output by the main
control unit 31.
[0031] In execution of torque control on the second AC motor 14, on
the other hand, the motor control unit 37 generates the three-phase
voltage command signals UU2, UV2 and UW2 by a pulse (rectangular)
waveform control method on the basis of a torque command value T2*
output by the main control unit 31, the U-phase current iU2 and
W-phase current iW2 of the second AC motor 14 as well as the rotor
rotation position .phi.2 of the second AC motor 14. As described
below, the U-phase current iU2 and the W-phase current iW2 are
signals output by the current sensors 43 and 44 respectively,
whereas the rotor rotation position .phi.2 is the signal output by
the rotor rotation position sensor 40. Under the pulse waveform
control method, the second AC motor 14 is controlled by commutating
the current supply at every predetermined angle in terms of the
electric angle of the second AC motor 14.
[0032] At this time, an input electric power of the second MG unit
30 is controlled to an input electric power command value P2*
independently of an input electric power of the second MG unit 30
required for the torque generation of the second AC motor 14. Thus,
the system voltage control is executed in order to suppress
variations in the system voltage by controlling an input electric
power of the second MG unit 30 (second AC motor 14) while
sustaining the torque generated by the second AC motor 14 at a
constant value (torque command value T2*).
[0033] Specifically, first of all, the signal output by the rotor
rotation position sensor 40 as the signal representing the rotor
rotation position .phi.2 of the second AC motor 14 is supplied to a
second rotation speed computation unit 48 for computing a rotation
speed N2 of the second AC motor 14. Further, a system voltage
target value computation unit 50 computes a target value Vs* of the
system voltage, whereas the voltage sensor 25 supplies a detection
value Vs of the system voltage to a first low pass filter 51 for
carrying out a low pass filtering process to pass only low
frequency signal included in the detection value Vs of the system
voltage. Subsequently, a subtractor 52 computes a difference
.DELTA.Vs between the target value Vs* of the system voltage and a
detection value Vsf output by the low pass filtering process as the
detection value of the system voltage, supplying the difference
.DELTA.Vs to the a P-I controller (power operation amount
computation means) 53 for computing by execution of P-I control an
input electric power command value P2* of the second AC motor 14 as
an amount that reduces the difference .DELTA.Vs between the target
value Vs* of the system voltage and the detection value Vsf output
by the low pass filtering process as the detection value of the
system voltage.
[0034] Thereafter, the torque command value T2* of the second AC
motor 14, the input electric power command value P2* for the second
MG unit 30 and the like are input to a torque and power control
unit 49.
[0035] As shown in FIG. 3, in this torque and power control unit
49, the current iU2 and iW2 (output signals of the current sensors
43 and 44) of the U-phase and W-phase of the second AC motor 14 are
applied to a fourth low pass filter 70 to perform a low pass
filtering process to pass only low frequency signal of the currents
iU2 and iW2 of the U-phase and the W-phase of the second AC motor
14. Then, a coordinate conversion unit 71 computes a detection
motor current vector i2 (d-axis detection motor current id2, a
q-axis detection motor current iq2) of the current flowing in the
second AC motor 14 in the rotor rotation coordinate system based on
the U-phase current iUf2 and the W-phase current iWf2 of the second
AC motor 14 after being subjected to the low pass filtering process
and the rotor rotation position .phi.2 of the second AC motor
14.
[0036] For independently controlling the torque of the second AC
motor 14 and the input electric power of the MG unit 30 from each
other, a current separation unit 72 separates a torque control
detection current vector it2 (d-axis detection current idt2, q-axis
detection current iqt2) which is related to torque control from a
detection motor current vector i2 (d-axis detection motor current
id2, a q-axis detection motor current iq2).
[0037] Here, with reference to FIG. 4, a method of separating the
detection motor current vector i2 into the torque control detection
current vector it2 (torque control detection current vector it2)
and the input electric power control detection current vector ip2
(detection current vector ip2 for input electric power control) is
described.
[0038] Here, .omega. is an electrical angular velocity, L is an
inductance, R is an armature coil resistance and .phi. is a linkage
flux. A voltage vector V0 is computed by multiplying the electric
angular velocity .omega. and the linkage flux .phi..
[0039] A basic waveform voltage vector V2* of a pulse waveform
voltage applied to the second AC motor 14 is computed from final
pulse waveform control information (final phase command value
.phi.2, final duty ratio D2). A basic waveform voltage vector Vt2*
of the torque control pulse waveform voltage is computed from the
basic waveform voltage vector V2* of the pulse waveform voltage and
torque control pulse waveform information (phase command value
.phi.t2 and basic duty ratio Dt2) described later.
[0040] Further, a basic waveform voltage vector Vp2* of the input
electric power control pulse waveform voltage is computed from the
basic waveform voltage vector V2* of the pulse waveform voltage and
the basic waveform voltage vector Vt2* of the input electric power
control pulse waveform voltage.
[0041] At a moment when the phase difference is .alpha. between the
voltage vector (V2*-V0) and the current vector i2, and R and
.omega.L are not almost changing, a triangle A formed by the three
current vectors i2, it2 and ip2 is similar to a triangle B formed
by the three voltage vectors (V2*-V0), (Vt2*-V0) and Vp2*.
Therefore, the similarity ratio R of the triangle A by the current
vectors to the triangle B by the voltage vectors becomes a value
obtained by dividing the magnitude of the current vector 12 by the
magnitude of the voltage vector (V2*-V0).
R=|i2|/|V2-V0|
[0042] That is, the triangle A formed by the three current vectors
i2, it2 and ip2 is a triangle which works to advance the angle by
.alpha. in the direction of each side of the triangle B formed by
the three voltage vectors (V2*-V0), (Vt2*-V0) and Vp2*, and to
multiply each side by R times.
[0043] It is, therefore, possible to compute the torque control
detection current vector it2 (d-axis detection current idt2, q-axis
detection current iqt2) by computing a vector that advances the
angle by .alpha. in the direction of the voltage vector (Vt2*-V0)
and multiplies the magnitude of the vector thereof by R times. It
is, further, possible to compute the input electric power control
detection current vector ip2 (d-axis detection current idp2, q-axis
detection current iqp2) by finding a vector that advances the angle
by .alpha. in the direction of the voltage vector Vp2* and
multiplies the magnitude of the vector thereof by R times.
[0044] Thus, as shown in FIG. 3, after separating the torque
control detection current vector it2 is separated from the
detection motor current vector i2 by the current separation unit
72, a first torque estimation unit 73 computes a first estimated
torque Tt2, which is an estimated value of torque generated by the
second AC motor 14, based on the torque control detection current
vector it2 (d-axis detection current idt2, q-axis detection current
iqt2) of the second AC motor 14.
[0045] Then, a subtractor 74 computes a difference .DELTA.Tt2
between the torque command value T2* and the first estimated torque
Tt2 of the second AC motor 14. This difference .DELTA.Tt2 is input
to a P-I controller 75 thereby to compute the phase command value
.phi.t2 of the torque control pulse waveform voltage by the P-I
control or the like so that the difference .DELTA.Tt2 between the
torque command value T2* and the first estimated torque Tt2 is
reduced. A duty setting unit 76 sets a basic duty ratio Dt2 (for
example, 50%) of the torque control pulse waveform voltage. These
phase command value .phi.t2 for torque control and the basic duty
ratio Dt2 are output as the torque control pulse waveform
information. Thus, the subtractor 74, P-I controller 75, duty
setting unit 76 and the like operate as torque control means.
[0046] A power computation unit 80 computes an input electric power
P2 of the second MG unit 30 based on the detection motor current
vector i2 (id2, iq2) of the second AC motor 14, the torque control
detection current vector it2 (idt2, iqt2), the torque control pulse
waveform information (.phi.t2, Dt2), the final pulse waveform
control information (.phi.2, D2), the rotor rotation position
.theta.2 and the like.
[0047] Then, a subtractor 81 computes a difference .DELTA.p2
between the input electric power command value P2* and the input
electric power P2 of the second MG unit 30. This difference
.DELTA.P2 is input to a P-I controller 82 thereby to compute a duty
correction value Dp2 by the P-I control or the like so that the
difference .DELTA.P2 between the input electric power command value
P2* and the input electric power P2 is reduced. Thus, the duty
correction value Dp2 is set to correct the torque control basic
duty ratio Dt2 so that the input electric power P2 of the second MG
unit 30 is controlled to the input electric power command value
P2*.
[0048] A phase correction value computation unit 83 computes a
phase correction value .phi.p2 in correspondence to the duty
correction value Dp2 mathematically or by using mapped data. The
phase correction value .phi.p2 for correcting the phase command
value .phi.t2 for torque control is set, so that the torque
variation of the second AC motor 14 generated due to the correction
of the duty ratio of the pulse waveform voltage by the duty
correction value Dp2 is suppressed by the correction of the phase
of the pulse waveform voltage. Then, a torque variation zeroing
control unit 85 computes a final phase correction value .phi.p2.
These phase correction value .phi.p2 and the duty ratio correction
value Dp2 are output as the pulse waveform information for electric
power control. Thus, the electric power computation unit 80, the
subtractor 81, the P-I controller 82, the phase correction value
computation unit 83 and the like operate as electric power control
means.
[0049] After the torque control pulse waveform information (phase
command value .phi.t2, basic duty ratio Dt2) and the electric power
control pulse waveform information (phase correction value .phi.p2,
duty ratio correction value Dp2) are computed separately from each
other, an adder 78 computes a final phase command value .phi.2
(=.phi.t2+.phi.p2) by adding the phase correction value (p2 to the
phase correction value .phi.t2 for torque control of the pulse
voltage. An adder 77 computes a final duty ratio D2 (=Dt2+Dp2) of
the pulse waveform voltage by adding the duty ratio correction
value Dp2 to the basic duty ratio Dt2 of the pulse waveform
voltage. These final phase command value .phi.2 and final duty
ratio Dt are output as the final pulse waveform control
information.
[0050] Then a pulse waveform voltage generation unit 79 computes
the three-phase voltage command signals UU2, UV2 and UW2 (pulse
waveform voltage signals) based on the final phase command value
.phi.2 and the final duty ratio Dt of the pulse waveform voltage,
and a rotor rotation position .phi.2 and a rotation speed N2 of the
second AC motor 14. These three-phase voltage command signals UU2,
UV2, UW2 are output to the inverter 28.
[0051] As described above, the torque control is executed to
control the torque of the second AC motor 14 so as to realize the
torque command value T2* output from the main control unit 31.
Further; while maintaining the torque of the second AC motor 14
constant (torque command value T2*), the system voltage
stabilization control is executed to suppress variation in the
system voltage so that the difference .DELTA.Vs between the target
value Vs* of the system voltage and the detection value Vsf is
reduced by executing the input electric power control to vary the
electric power input to the second MG unit 30 (second AC motor 14).
In this case, the P-I controller 53 and the like units operate as
system voltage control means.
[0052] Here, in the transient condition of the input electric power
control of the second MG unit 30, when the current vector i2 of the
second AC motor 14 greatly deviates from a constant torque curve (a
curve representing a current vector which generates the same
torque), uncomfortable torque fluctuation will be caused.
[0053] To counter this problem, a second torque estimation unit 84
computes a second estimated torque T2, which is an estimated torque
that will be generated by the second AC motor 14, based on the
detection motor current vector i2 (d-axis detection motor current
id2, d-axis detection motor current iq2) of the second AC motor 14.
Then, the torque variation zeroing control unit 85 executes the
torque variation zeroing control so that the difference .DELTA.Tp2
between the first estimated torque Tt2 and the second estimated
torque T2 is reduced to zero.
[0054] Specifically, as shown in FIG. 5, a subtractor 86 computes
the difference .DELTA.Tp2 between the first estimated torque Tt2
and the second estimated torque T2. This difference .DELTA.Tp2 is
applied to a P-I controller 87, which computes by P-I control or
the like a correction value .phi.p22 so that the difference
.DELTA.Tp2 between the first estimated torque Tt2 and the second
estimated torque T2 is reduced. An adder 88 computes a final phase
correction value .phi.p2 by adding the correction value .phi.p22 to
the phase correction value .phi.p2. Thus, the phase correction
value .phi.p2 is corrected so that the difference .DELTA.Tp2
between the first estimated torque Tt2 and the second estimated
torque T2 is reduced to zero substantially.
[0055] With such processing of the torque variation zeroing control
unit 85, the current vector i2 of the second AC motor 14 is changed
along the constant torque curve so that the torque of the second AC
motor 14 is not varied in the transient time of the input electric
power control of the second MG unit 30.
(Conversion Power Control)
[0056] After the start of system operation and the smoothing
capacitor 24 has been sufficiently pre-charged, the motor control
unit 37 halts the above conversion voltage control, and changes the
operation over to conversion power control to control the output
voltage of the voltage boosting converter 21 so as to decrease the
difference .DELTA.pi between the command value Pif* and the
detection value Pi of output electric power by the boosting
converter 21.
[0057] When the command value Pif* of output electric power of the
boosting converter 21 is to be computed, first, as shown in FIG. 2,
the torque command value T1* and the rotation speed N1 of the first
AC motor 13 are input to a first shaft output computation unit 56
to compute a shaft output PD1 of the first AC motor 13. Further,
the torque command value T1* and the rotation speed N1 of the first
AC motor 13 are input to a first output loss computation unit 57 to
compute an output loss PL1 of the first AC motor 13. Thereafter, an
adder 58 adds the output loss PL1 to the shaft output PD1 of the
first AC motor 13 to compute an input power Pi1 to the first AC
motor 13. In this case, when the first AC motor 13 is operating as
a generator, the computation result of input power Pi1 to the first
AC motor 13 assumes a negative value.
[0058] Further, the torque command value T2* and the rotation speed
N2 of the second AC motor 14 are input to a second shaft output
computation unit 59 to operate a shaft output PD2 of the second AC
motor 14. Further, the torque command value T2* and the rotation
speed N2 of the second AC motor 14 are input to a second output
loss computation unit 60 to compute an output loss PL2 of the
second AC motor 14. Thereafter, an adder 61 adds the output loss
PL2 to the shaft output PD2 of the second AC motor 14 to compute an
input power Pi2 to the second AC motor 14. In this case, when the
second AC motor 14 is operating as a generator, the computation
result of input power Pi2 to the second AC motor 14 assumes a
negative value.
[0059] Thereafter, the input power Pi1 to the first AC motor 13 and
the input power Pi2 to the second AC motor are added up together
through an adder 62 to compute a total electric power Pi*. The
total electric power Pi* is input to a second low pass filter 63 so
as to be subjected to the low pass filtering process permitting the
passage of components in a low-frequency region only of the total
electric power Pi*. The total electric power Pif* after being
subjected to the low pass filtering is regarded to be the command
value Pif* for the conversion power. The adder 62 and the second
low pass filter 63 operate as conversion power command value
computation means.
[0060] When the detection value Pi of output electric power of the
voltage boosting converter 21 is to be computed, a detection value
ic of current output from the voltage boosting converter 21
detected by the current sensor 26 is input to a third low pass
filter 64 and is subjected to the low pass filtering process
permitting the components in the low-frequency region only to pass
through in the detection value ic of current output from the
voltage boosting converter 21. A conversion power detection unit 65
multiplies the target value Vs* of the system voltage by the
detection value icf of current output from the voltage boosting
converter 21 after having been subjected to the low pass filtering
in order compute a detection value Pi of the conversion power. The
detection value Vsf of the system voltage may be multiplied by the
detection value icf of the output current to compute the detection
value Pi of the output power.
[0061] Thereafter, a difference .DELTA.Pi between the command value
Pif* and the detection value Pi of output electric power of the
voltage boosting converter 21 is computed by a subtractor 66. The
difference .DELTA.Pi is input to a P-I controller 67 (conversion
power control amount computation means), and a current duty ratio
Dc of a switching element (not shown) in the voltage boosting
converter 21 is computed by P-I control so as to decrease the
difference .DELTA.Pi between the command value Pif* and the
detection value Pi of output electric power of the voltage boosting
converter 21. Then, a voltage boosting drive signal computation
unit 68 computes a voltage boosting drive signals UCU, UCL based on
the current duty ratio Dc, and outputs the computed drive signals
UCU and the UCL to the boosting converter 21.
[0062] Thus, the conversion power control is executed to control
the output electric power of the voltage boosting converter 21 so
as to decrease the difference .DELTA.Pi between the command value
Pif* and the detection value Pi of the output electric power of the
voltage boosting converter 21. Thus, the electric power supplied to
the power line 22 by the voltage boosting converter 21 can be
controlled as desired. In this case, the P-I controller 67, the
voltage boosting drive signal computation unit 68 and the like
operate as conversion power control means.
[0063] As described above, in controlling the second AC motor 14 in
the pulse waveform control method, the input electric power to the
second MG unit 30 is so controlled that the difference .DELTA.Vs
between the target value Vs* and the detection value Vsf of the
system voltage is decreased to execute the system voltage
stabilization control in order to suppress variation in the system
voltage (voltage of the power supply line 22). Therefore, even when
the power balance greatly varies between the two AC motors 13 and
14 due to changes in the operating conditions of the vehicle, the
system voltage can be effectively stabilized. Besides, the voltage
of the power supply line 22 can be highly stabilized without using
the voltage boosting converter 21 of high performance or without
using the smoothing capacitor 24 of a large capacity, satisfying
the requirement of realizing the system in a small size and at a
decreased cost.
[0064] Further, the pulse waveform information (phase command value
.phi.t2, basic duty ratio Dt2) for torque control and the pulse
waveform information (phase correction value .phi.p2, duty ratio
correction value Dp2) for electric power control are computed
independently. Then the final pulse waveform control information
(final phase command value .phi.2, final duty ration Dt) is
computed based on these pulse waveform control information for
torque control and pulse waveform control information for electric
power control. Thus, the torque control of the second AC motor 14
and the input electric power control of the second MG unit 30 are
executed independently from each other; As a result, the torque
control of the second AC motor 14 and the input electric power
control of the MG unit 30 are prevented from interfering each other
and are stabilized well.
[0065] In executing the system voltage stabilization control, the
system voltage is controlled by controlling the input electric
power of the second MG unit 30 while maintaining the torque of the
second AC motor 14 at a substantially constant value (torque
command value T2*). As a result, the system voltage is prevented
from varying without affecting adversely to vehicle operating
conditions.
[0066] The first estimated torque Tt2 is computed based on the
torque control detection current vector it2 of the second AC motor
14, and the second estimated torque T2 is computed based on the
motor detection current vector i2 of the second AC motor 14.
Further, the torque variation zeroing control, which corrects the
phase correction value .phi.p2 of the pulse waveform voltage, is
executed to reduce the difference .DELTA.Tp2 between the first
estimated torque Tt2 and the second estimated torque T2 to zero
substantially. As a result, in the transient condition of
controlling the input electric power of the second MG unit 30, the
current vector i2 of the second AC motor 14 can be changed in line
with the constant torque curve so that the torque of the second AC
motor 14 is restricted from varying. Thus, uncomfortable torque
variation is suppressed.
[0067] The above embodiment may be modified in many ways.
[0068] For example, in the conversion power control, the input
electric power of the voltage boosting converter 21 may be
controlled to reduce a difference between the command value and the
detection value of the input electric power of the converter 21, in
place of controlling the output electric power of the converter 21
to reduce the difference .DELTA.Pi in the input electric power.
[0069] In the system voltage stabilization control, the system
voltage variation may be suppressed by controlling the input
electric power of the first MG unit 29 (first AC motor 13) in place
of controlling the input electric power of the second MG unit
30.
[0070] In addition, in a all-wheel-driven vehicle which has a third
MG unit mounted on a driven wheel, the system voltage may be
stabilized to suppress system voltage variation by controlling the
input electric power of the third MG unit.
[0071] The above embodiments are directed to a hybrid vehicle of
the so-called split type, which splits the motive power of the
engine through the planetary gear mechanism. Not being limited to
the hybrid vehicle of the split type, however, the embodiment may
be hybrid vehicles of other types, such as a parallel type and a
series type. In the above embodiment, further, the vehicle uses the
AC motor and the engine as motive power sources. However, the
vehicle may use the AC motor only as a motive power source. The
vehicle may have only one MG unit comprising an inverter and an AC
motor, or three or more MG units.
* * * * *