U.S. patent application number 10/598133 was filed with the patent office on 2008-01-31 for current direction detection circuit and switching regulator having the same.
This patent application is currently assigned to ROHM COMPANY, LTD.. Invention is credited to Yoshiyuki Hojo.
Application Number | 20080024098 10/598133 |
Document ID | / |
Family ID | 34879253 |
Filed Date | 2008-01-31 |
United States Patent
Application |
20080024098 |
Kind Code |
A1 |
Hojo; Yoshiyuki |
January 31, 2008 |
CURRENT DIRECTION DETECTION CIRCUIT AND SWITCHING REGULATOR HAVING
THE SAME
Abstract
A current direction detection circuit includes a monitoring
transistor having a control terminal and an output terminal
respectively connected with a control terminal and an output
terminal of a ground side output transistor; an impedance element
having one terminal connected with an input terminal of the
monitoring transistor and the other terminal grounded; first and
second constant-current sources; a diode-connected reference
transistor interposed between the first constant-current source and
ground potential; and a sensing transistor interposed between the
second constant-current source and the impedance element and having
a control terminal connected with the control terminal of the
reference transistor. The current direction detection circuit is
small yet capable of minimizing power loss of a switching
regulator.
Inventors: |
Hojo; Yoshiyuki; (Kyoto,
JP) |
Correspondence
Address: |
ROHM CO., LTD.;C/O KEATING & BENNETT, LLP
8180 GREENSBORO DRIVE
SUITE 850
MCLEAN
VA
22102
US
|
Assignee: |
ROHM COMPANY, LTD.
21 Saiin Mizosaki-cho
Ukyo-ku, Kyoto
JP
|
Family ID: |
34879253 |
Appl. No.: |
10/598133 |
Filed: |
February 15, 2005 |
PCT Filed: |
February 15, 2005 |
PCT NO: |
PCT/JP05/02270 |
371 Date: |
April 11, 2007 |
Current U.S.
Class: |
323/282 ;
324/713 |
Current CPC
Class: |
H02M 3/1588 20130101;
H02M 2001/0009 20130101; Y02B 70/10 20130101; H02M 3/156 20130101;
Y02B 70/1466 20130101 |
Class at
Publication: |
323/282 ;
324/713 |
International
Class: |
G05F 1/46 20060101
G05F001/46; G01R 27/16 20060101 G01R027/16 |
Foreign Application Data
Date |
Code |
Application Number |
Feb 19, 2004 |
JP |
2004-042277 |
Claims
1-2. (canceled)
3. A current direction detection circuit for detecting a reverse
flow of current in a ground side output transistor, through which
current flows from a grounded input terminal to an output terminal,
comprising: a monitoring transistor having a control terminal and
an output terminal arranged to be connected, respectively, with a
control terminal and an output terminal of the ground side output
transistor; an impedance element having one terminal connected with
the input terminal of the monitoring transistor and the other
terminal grounded; first and second constant-current sources; a
diode-connected reference transistor arranged between the first
constant-current source and ground potential; and a sensing
transistor arranged between the second constant-current source and
the impedance element, the sensing transistor having a control
terminal connected with a control terminal of the reference
transistor; wherein a voltage between the second constant-current
source and the sensing transistor is output as a control signal to
control the ground side output transistor and monitoring
transistor.
4. A switching regulator comprising: a power source side output
transistor and a ground side output transistor provided in series
between an input power source and ground potential; a smoothing
circuit having an input terminal connected between the power source
side output transistor and the ground side output transistor and an
output terminal connected with a switching regulator output
terminal that outputs a predetermined DC voltage; a regulator
control circuit that performs on/off control of the power source
side output transistor and ground side output transistor so as to
maintain a predetermined DC voltage by inputting as feedback the
voltage of the switching regulator output terminal; the current
direction detection circuit according to claim 3; and a ground side
output transistor control circuit arranged to control the ground
side output transistor so as to maintain the ground side output
transistor turned off once the control signal of the current
direction detection circuit has risen, after being turned on by the
control signal of the regulator control circuit.
Description
BACKGROUND OF THE INVENTION
[0001] 1. Field of the Invention
[0002] The present invention relates to a current direction
detection circuit that, when reverse direction current flows in a
ground side output transistor, is capable of detecting the flow of
current, and relates to a switching regulator including the current
direction detection circuit.
[0003] 2. Description of the Related Art
[0004] A switching regulator is provided with a power source side
output transistor, that defines a main switching element, between a
terminal that inputs power and a terminal that is connected with
the load and outputs a predetermined DC voltage, and maintains a
predetermined DC voltage by turning on/off
(conductive/non-conductive) the power source side output
transistor. Such regulators are of small size and are capable of
achieving high power efficiency and thus are widely used. In recent
years, synchronous rectifying switching regulators have been used
(see, for example, Japanese Patent Application Laid-open No.
2000-92824), in which a ground side output transistor is
additionally provided, defining a synchronous rectifying switching
element. Such synchronous rectifying switching regulators make it
possible to further improve power efficiency.
[0005] FIG. 3 shows the layout of a conventional synchronous
rectifying switching regulator. The switching regulator 101
includes a power source side output transistor 111 defined by a P
type MOS transistor and a ground side output transistor 112 defined
by an N type MOS transistor connected in series between the input
power source V.sub.CC and ground potential; a smoothing circuit 113
whose input terminal is connected to a point between the two
transistors 111, 112 and whose output terminal is connected with
the output terminal OUT, respectively; a regulator control circuit
115 that outputs a control signal A and control signal B that
perform on/off control of the power source side output transistor
111 and ground side output transistor 112 so as to maintain a
predetermined DC voltage in response to feedback input of the
voltage of the output terminal OUT; a current direction detection
circuit 116 that, when reverse direction current flows in the
ground side output transistor 112, detects the reverse direction
current and outputs a control signal F; and a ground side output
transistor control circuit 117 that outputs an output signal C for
controlling the ground side output transistor 112 in accordance
with the control signal B and control signal F. In this case, a
load 114 is connected at the outside to the output terminal OUT.
Also, the smoothing circuit 113 includes a smoothing coil 140
having one terminal connected with the connection point (node D) of
the power source side output transistor 111 and the ground side
output transistor 112 and the other terminal connected with the
output terminal OUT, and a smoothing capacitor 141 having one
terminal connected with the output terminal OUT and the other
terminal grounded. Also, the control signal A and the control
signal B that are output by the regulator control circuit 115 have
substantially the same waveform.
[0006] The current direction detection circuit 116 includes a
comparator 120 that performs a comparison by respectively inputting
the voltage of the node D at its inversion input terminal and
ground potential at its non-inversion input terminal. Also, the
ground side output transistor control circuit 117 includes an AND
circuit 130 that inputs the control signal B of the regulator
control circuit 115 and the control signal F of the current
direction detection circuit 116, and a buffer 131 that delivers an
output with an increased current capability.
[0007] Next, the operation of the switching regulator 101 will be
described with reference to FIG. 4. In FIG. 4, V.sub.B is the
voltage of the control signal B of the regulator control circuit
115, V.sub.C is the voltage of the output signal C of the ground
side output transistor control circuit 117, I.sub.O is the current
flowing in the ground side output transistor 112, and V.sub.D is
the voltage at the node D. It should be noted that FIG. 4 shows the
waveform when the load 114 is light, the case where the load 114 is
large is not shown.
[0008] In the period in which control signal B is low level, the
output signal C is low level, and the ground side output transistor
112 is turned off. The control signal A is also low level, so the
power source side output transistor 111 is turned on. Consequently,
the current I.sub.O flowing in the ground side output transistor
112 is zero, and the voltage V.sub.D at the node D is high
level.
[0009] Since, when the control signal B is high level, the control
signal A is also high level, the power source side output
transistor 111 is turned off. When the voltage V.sub.D at the node
D drops, becoming lower than the ground potential, the control
signal F becomes high level, with the result that the ground side
output transistor 112 is turned on. In this way, first of all,
current I.sub.O in the positive direction flows from ground
potential to the node D. When this happens, the voltage V.sub.D at
the node D drops from ground potential by an amount of the voltage
that is acquired by multiplying this current I.sub.O and the on
resistance of the ground side output transistor 12.
[0010] After this, the current I.sub.O gradually decreases
linearly, and, in response thereto, the negative voltage V.sub.D at
the node D gradually rises in linear fashion. If the load 114 is
large (not shown), the initial current value is large prior to the
commencement of decrease of the current I.sub.O. Therefore, before
the current I.sub.O will become a current in the reverse direction,
the control signal B returns to low level after the lapse of a
period in which the control signal B is high level. In contrast, if
the load 114 is light, the current I.sub.O becomes a current in the
reverse direction before the high level period of the control
signal B has lapsed. This reverse direction current is a current
that flows out towards the ground potential, so it represents a
power loss and the power efficiency of the switching regulator 101
is lowered to that extent. Accordingly, when the current becomes a
reverse direction current, this is detected by the current
direction detection circuit 116, which outputs low level control
signal F. As a result, the voltage V.sub.C of the output signal C
becomes low level and the ground side output transistor 112 is
thereby forcibly turned off, so that the flow of this current in
the reverse direction is minimized.
[0011] Thus, when the load is light, the ground side output
transistor 112 is forcibly turned off when the current I.sub.O
flows in the reverse direction, thereby making it possible to
increase the power efficiency. The inventor of the present
application, as a result of studies directed at achieving further
improvements in power efficiency, discovered that there is a
certain delay (period to in FIG. 4) from detection of the reverse
direction current of the ground side output transistor 112 by the
current direction detection circuit 116, before ground side output
transistor 112 is turned off, and this delay allows a reverse
direction current to flow for a certain period of time, which
therefore results in power loss. Also, since the voltage V.sub.D at
the node D has a wide range of variations from the power source
voltage to below ground potential, the comparator 120 of the
current direction detection circuit 116, which has as its input
voltage a voltage of such a wide range of variations, must be
larger in terms of the size of its circuitry compared with an
ordinary comparator, whose input voltage is a voltage having a
narrow range of variations.
[0012] Also, with the switching regulator 101, as shown in FIG. 4,
there is a risk that a swing, i.e., ringing of the gradually
decaying voltage generated after the forcible turning off of the
ground side output transistor 112 will cause the voltage V.sub.D at
the node D to drop below ground potential, resulting in
instantaneous activation of the current direction detection circuit
116, with consequent wasted power consumption or generation of
noise.
SUMMARY OF THE INVENTION
[0013] In order to overcome the problems described above, preferred
embodiments of the present invention provide a current direction
detection circuit wherein even better suppression of power losses
can be achieved in a switching regulator, for example, and in which
a small sized circuit can be provided. Another preferred embodiment
of the present invention provides a switching regulator in which
current losses can be minimized by such a current direction
detection circuit and wherein there is no possibility of
reactivation of the current direction detection circuit after
detection of a reverse direction current.
[0014] According to a first preferred embodiment of the present
invention, a current direction detection circuit for detecting a
flow of current in the reverse direction in a ground side output
transistor, through which current flows from a grounded input
terminal to the output terminal, includes a monitoring transistor
having a control terminal and an output terminal respectively
connected with a control terminal and an output terminal of the
ground side output transistor; an impedance element having one
terminal connected with the input terminal of the monitoring
transistor and the other terminal grounded; first and second
constant-current sources; a diode-connected reference transistor
interposed between the first constant-current source and ground
potential; and a sensing transistor, interposed between the second
constant-current source and the impedance element, having a control
terminal connected with a control terminal of the reference
transistor, wherein the voltage between the second constant-current
source and the sensing transistor is output as a control signal to
control the ground side output transistor and monitoring
transistor.
[0015] A switching regulator according to another preferred
embodiment of the present invention includes a power source side
output transistor and a ground side output transistor provided in
series between an input power source and ground potential; a
smoothing circuit having an input terminal connected between the
power source side output transistor and the ground side output
transistor and an output terminal connected with a switching
regulator output terminal that outputs a predetermined DC voltage;
a regulator control circuit that performs on/off control of the
power source side output transistor and ground side output
transistor so as to maintain a predetermined DC voltage by
inputting as feedback the voltage of the switching regulator output
terminal; the current direction detection circuit according to
claim 1; and a ground side output transistor control circuit that
controls the ground side output transistor so as to maintain the
ground side output transistor in a continuously turned off state
once the control signal of the current direction detection circuit
has risen, after being turned on by the control signal of the
regulator control circuit.
[0016] In the current direction detection circuit according to the
above-described preferred embodiments of the present invention, due
to the configuration of the monitoring transistor, the impedance
element, the first and second constant-current sources, the
reference transistor, and the sensing transistor, the control
signal is output upon detection of the condition just prior to the
point where the current flowing in the ground side output
transistor starts to flow in the reverse direction. Therefore, it
becomes possible to further minimize the power loss thereof when
used in a switching regulator, for example, and furthermore the
size of the circuitry can be made small. Also, in the switching
regulator according to the above-described preferred embodiments of
the present invention, the current direction detection circuit
cannot be reactivated after detection of the current in the reverse
direction, so wasted power consumption produced by ringing or
generation of noise can be minimized.
[0017] Other features, elements, steps, characteristics and
advantages of the present invention will become more apparent from
the following detailed description of preferred embodiments of the
present invention with reference to the attached drawings.
BRIEF DESCRIPTION OF THE DRAWINGS
[0018] FIG. 1 is a circuit diagram of a current direction detection
circuit according to a preferred embodiment of the present
invention and a switching regulator including the same.
[0019] FIG. 2 is an operating waveform diagram of the switching
regulator in FIG. 1.
[0020] FIG. 3 is a circuit diagram of a switching regulator
according to the background art.
[0021] FIG. 4 is an operating waveform diagram of the switching
regulator in FIG. 3.
DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS
[0022] Preferred embodiments of the present invention are described
below with reference to the drawings. FIG. 1 is a circuit diagram
of a current direction detection circuit and a switching regulator
including the same according to a preferred embodiment of the
present invention. The switching regulator 1 includes a power
source side output transistor 11 defined by a P type MOS transistor
and a ground side output transistor 12 defined by an N type MOS
transistor connected in series between the input power source
V.sub.CC and ground potential; a smoothing circuit 13 having an
input terminal connected between the two transistors 11, 12 and an
output terminal connected to the output terminal (switching
regulator output terminal) OUT; a regulator control circuit 15 that
outputs a control signal A and control signal B that perform on/off
control of the power source side output transistor 11 and ground
side output transistor 12 so as to maintain a predetermined DC
voltage by inputting as feedback the voltage of the output terminal
OUT; a current direction detection circuit 16 that, when reverse
direction current flows in the ground side output transistor 12,
detects reverse direction current and outputs a control signal F;
and a ground side output transistor control circuit 17 that outputs
an output signal C for controlling the ground side output
transistor 12 by means of the control signal B and control signal
F. A load 14 is connected at the outside to the output terminal
OUT. Also, the smoothing circuit 13 includes a smoothing coil 40
having one terminal connected with the connection point (node D) of
the power source side output transistor 11 and the ground side
output transistor 12 and the other terminal connected with the
output terminal OUT, and a smoothing capacitor 41 having one
terminal connected with the output terminal OUT and the other
terminal grounded. Also, the control signal A and the control
signal B outputted by the regulator control circuit 15 have
substantially the same waveform.
[0023] The current direction detection circuit 16 includes a
monitoring transistor 20 defined by an N type MOS transistor having
the gate (control terminal) and drain (output terminal)
respectively connected with the gate (control terminal) and drain
(output terminal) of the ground side output transistor 12; an
impedance element 21 having one terminal connected with the source
(input terminal) of the monitoring transistor 20 and the other
terminal grounded; first and second constant-current sources 22, 23
each defined by a P-type MOS transistor; a reference transistor 24,
interposed between the first constant-current source 22 and ground
potential, that is defined by a diode-connected (i.e., having its
drain and gate mutually connected) N type MOS transistor; and a
sensing transistor 25 defined by an N type MOS transistor,
interposed between the second constant-current source 23 and
impedance element 21, having a gate (control terminal) connected to
the gate (control terminal) of the reference transistor 24. Also,
the current direction detection circuit 16 includes a P-type MOS
transistor 26 defining a current mirror circuit with the first and
second constant-current sources 22, 23 and setting the current
values of these elements, and a constant-current source 27 that
generates the current that flows to the P-type MOS transistor 26.
The current direction detection circuit 16 outputs as a control
signal the voltage between the second constant-current source 23
and sensing transistor 25 (i.e., at the node F) and thereby
controls the ground side output transistor 12 and the monitoring
transistor 20 via the ground side output transistor control circuit
17.
[0024] Since the monitoring transistor 20 passes a current that is
comparatively small in proportion to the current value of the
ground side output transistor 12, it is set to a size of 1/N of the
ground side output transistor 12 (N is a predetermined value). The
impedance element 21 is an element that generates a voltage in
response to the current that flows therein, and for the impedance
element 21 there may be used, for example, a resistor or an N type
MOS transistor whose on-resistance is a comparatively high value.
The first constant-current source 22 and second constant-current
source 23 have the capability of passing equal constant currents
I.sub.REF (for example, about 1 .mu.A ). Also, the size of the
reference transistor 24 is such that the connection point of the
first constant-current source 22 and reference transistor 24 is
high level. Then, in case the sizes of the reference transistor 24
and sensing transistor 25 are equal, if the voltage V.sub.E at the
node E is substantially at least ground potential, the voltage
V.sub.F at the node F (i.e., the voltage of the control signal that
is output by the current direction detection circuit 16) is high
level. In contrast, when the voltage V.sub.E at the node E drops
substantially below the ground potential, the on-resistance of the
sensing transistor 25 falls, with the result that the voltage
V.sub.F at the node F becomes low level.
[0025] More specifically, the case where the voltage at the node E
is at least ground potential includes the case where the monitoring
transistor 20 is off and the case where the monitoring transistor
20 is on, but the voltage V.sub.D at the node D is at least ground
potential. If the monitoring transistor 20 is off, current tries to
flow from the second constant-current source 23 to the impedance
element 21 (for example 1 K.OMEGA.), so the voltage at the node E
rises slightly from ground potential. Also, if the monitoring
transistor 20 is on and the voltage V.sub.D at the node D is at
least ground potential, current flows through the monitoring
transistor 20 and impedance element 21 from the node D, so the
voltage V.sub.E at the node E becomes a value obtained by dividing
the voltage V.sub.D at the node D by the on resistance of the
monitoring transistor 20 and the resistance of the impedance
element 21. In contrast, and more specifically, the case where the
voltage V.sub.E at the node E drops below ground potential
represents the case where the monitoring transistor 20 is on and
the voltage V.sub.D at the node D is a voltage that is lower than
ground potential, i.e., negative voltage. In this case, since the
current flows from ground potential through the impedance element
21 and monitoring transistor 20, the voltage V.sub.E at the node E
is a value obtained by dividing the negative voltage V.sub.D at the
node D by the resistance of the impedance element 21 and the on
resistance of the monitoring transistor 20.
[0026] Even more specifically, even in the case where the
monitoring transistor 20 is on and the node D has a negative
voltage, if this negative voltage value is small, the voltage
V.sub.E at the node E may be ground potential or more. That is, if,
for example, the "on" resistance value of the monitoring transistor
20 and the resistance value of the impedance element 21 are both R,
the voltage V.sub.E at the node E is
V.sub.E=(V.sub.D+I.sub.REF.times.R)/2. As stated above, I.sub.REF
is the constant current value of the second constant-current source
23. Since, when V.sub.D =-I.sub.REF.times.R , V.sub.E is zero, even
if the voltage V.sub.D at the node D is negative if it is smaller
than (I.sub.REF.times.R), the voltage V.sub.E at the node E is at
least ground potential. Thus, the voltage V.sub.D at the node D has
an offset in the negative direction from the ground potential and
is detected by the current direction detection circuit 16. The
value of this offset can be adjusted by means of I.sub.REF or the
resistance value of the impedance element 21. Using this, the fact
that current in the reverse direction is about to flow in the
ground side output transistor 12 can be detected just before this
actually happens. This will be described below.
[0027] Next, the ground side output transistor control circuit 17
will be described. The ground side output transistor control
circuit 17 includes an OR circuit 30 that inputs the inverted
signal of the control signal B of the regulator control circuit 15
and a control signal F of the current direction detection circuit
16; an edge detection circuit 31 that inputs the control signal B
at its set input terminal S, inputs the output of the OR circuit 30
at its reset input terminal R, and outputs the result from the
non-inversion output terminal Q; and a buffer 32 that delivers the
output of the edge detection circuit 31 with increased current
capability. The edge detection circuit 31 outputs a high level from
its non-inversion output terminal Q in response to the rising edge
of the input signal of the set input terminal S, and maintains this
condition, and outputs a low level from its non-inversion output
terminal Q in response to the rising edge of the input signal of
the reset input terminal R, and maintains this condition.
[0028] Next, the operation of the switching regulator 1 will be
described with reference to FIG. 2, focusing on the operation of
the current direction detection circuit 16. In this figure, V.sub.B
is the voltage of the control signal B of the regulator control
circuit 15, V.sub.C is the voltage of the output signal C of the
ground side output transistor control circuit 17, I.sub.O is the
current flowing in the ground side output transistor 12, V.sub.D is
the voltage at the node D, V.sub.E is the voltage at the node E,
and V.sub.F is the voltage of the control signal F of the current
direction detection circuit 16. The height of V.sub.E in this
figure is shown to a larger scale. Also, FIG. 2 shows the waveform
when the load 14 is light. The case where the load 14 is large is
not shown.
[0029] In the period in which the control signal B is low level,
the output signal C is low level and the ground side output
transistor 12 and monitoring transistor 20 are turned off. The
control signal A is also low level and the power source side output
transistor 11 is turned on. Consequently, the current I.sub.O
flowing in the ground side output transistor 12 is zero, and the
voltage V.sub.D at the node D is high level. The monitoring
transistor 20 is off, so, as described above, the voltage V.sub.E
at the node E is raised slightly from the ground potential, causing
the voltage V.sub.F at the node F to become high level.
[0030] When the control signal B becomes high level, the control
signal A also becomes high level, so the power source side output
transistor 11 is turned off. The ground side output transistor
control circuit 17 then outputs a high level on receiving the
rising edge of the control signal B, thereby turning on the ground
side output transistor 12 and monitoring transistor 20. In response
to turning on of the ground side output transistor 12, first of
all, a current I.sub.O in the positive direction flows from ground
potential to the node D. When this happens, the voltage V.sub.D at
the node D is lowered from ground potential by an amount of the
voltage that is acquired by multiplying this current I.sub.O and
the on-resistance of the ground side output transistor 12. The
voltage V.sub.E at the node E is also a negative voltage, and the
voltage V.sub.F at the node F becomes low level.
[0031] After this, the current I.sub.O gradually decreases
linearly, and in response to this the negative voltage V.sub.D at
the node D and the voltage V.sub.E at the node E gradually increase
linearly. If the load 14 is large (not shown), the initial current
value is large prior to the commencement of decrease of the current
I.sub.O. Therefore, before the current I.sub.O will become a
current in the reverse direction, the control signal B returns to
low level after the lapse of the high level period. In this case,
the ground side output transistor control circuit 17 delivers low
level output on receipt of the trailing edge of the input control
signal B, with the result that the ground side output transistor 12
and monitoring transistor 20 are turned off (not shown).
[0032] In contrast, when the load 14 is light, the current I.sub.O
flowing in the ground side output transistor 12 tries to become a
reverse direction current and the voltage V.sub.D at the node D
tries to become positive voltage before the lapse of the high level
period of the control signal B. However, as described above, since
the voltage V.sub.D at the node D has an offset in the negative
direction from ground potential, this situation is detected by the
current direction detection circuit 16. In other words, the current
direction detection circuit 16 detects the condition slightly prior
to the current I.sub.O becoming a current in the reverse direction,
and outputs a high level control signal at the node F. On receipt
of the rising edge of this input control signal F of the current
direction detection circuit 16, the ground side output transistor
control circuit 17 then outputs a low level and thereby forcibly
turns the ground side output transistor 12 off. Specifically, the
ground side output transistor control circuit 17 effects control of
the ground side output transistor 12 such that this output
transistor 12 continues to be turned off once the control signal F
of the current direction detection circuit 16 has risen after being
turned on by the control signal B of the regulator control circuit
15.
[0033] Thus, by detection of this situation, just prior to the flow
of current in the reverse direction in the ground side output
transistor 12, the current direction detection circuit 16
compensates for the circuit delay produced by the current direction
detection circuit 16 and the ground side output transistor control
circuit 17 and thus minimizes power loss, thereby making it
possible to increase the power efficiency. Compared with the
current direction detection circuit 116 of the background art,
whose input voltage is a voltage having a wide range of variations
used in the switching regulator 101, the current direction
detection circuit 16 has a very compact circuit construction and
uses an input voltage having a narrow range of variations. The size
of the current direction detection circuit 16 can therefore be made
small.
[0034] When the ground side output transistor 12 is forcibly turned
off, the voltage V.sub.D at the node D converges with ringing to
the voltage level of the output terminal OUT and is then
stabilized. However, when this happens, the ground side output
transistor control circuit 17 controls the ground side output
transistor 12 such that this ground side output transistor 12
remains turned off once the control signal F of the current
direction detection circuit 16 has risen, so there is no risk of
reactivation of the current direction detection circuit 16 by
ringing, such as could occur in the switching regulator 101 in the
background art.
[0035] It should be noted that, although the current direction
detection circuit according to the preferred embodiments of the
present invention is preferably for use with a switching regulator,
it could also be used in other devices having a ground side output
transistor that outputs current to a coil (such as, for example, a
motor drive device).
[0036] While preferred embodiments of the present invention have
been described above, it is to be understood that variations and
modifications will be apparent to those skilled in the art without
departing the scope and spirit of the present invention. The scope
of the present invention, therefore, is to be determined solely by
the following claims.
* * * * *