U.S. patent application number 11/824856 was filed with the patent office on 2007-11-08 for method for recovering data transmitted over a plurality of channels employing wireless code division multiple access communication.
This patent application is currently assigned to InterDigital Technology Corporation. Invention is credited to John Kowalski, Donald L. Schilling.
Application Number | 20070258412 11/824856 |
Document ID | / |
Family ID | 23069142 |
Filed Date | 2007-11-08 |
United States Patent
Application |
20070258412 |
Kind Code |
A1 |
Schilling; Donald L. ; et
al. |
November 8, 2007 |
Method for recovering data transmitted over a plurality of channels
employing wireless code division multiple access communication
Abstract
A method for recovering data transmitted over a plurality of
channels employing wireless code division multiple access
communication, comprises receiving the plurality of channels as a
received signal, each channel associated with a code. Others from
the plurality of channels from the received signal is subtracted
for each for each of the plurality of channels and a result a
result of that subtracting as data for that channel is despread.
That channel despread signal is respread with a respective channel
code, wherein the respreading channel code is aligned to a timing
of the despread received signal.
Inventors: |
Schilling; Donald L.; (Sands
Point, NY) ; Kowalski; John; (New York, NY) |
Correspondence
Address: |
VOLPE AND KOENIG, P.C.;DEPT. ICC
UNITED PLAZA, SUITE 1600
30 SOUTH 17TH STREET
PHILADELPHIA
PA
19103
US
|
Assignee: |
InterDigital Technology
Corporation
Wilmington
DE
19810
|
Family ID: |
23069142 |
Appl. No.: |
11/824856 |
Filed: |
July 3, 2007 |
Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
|
|
10201797 |
Jul 24, 2002 |
7242675 |
|
|
11824856 |
Jul 3, 2007 |
|
|
|
09851740 |
May 9, 2001 |
6868076 |
|
|
10201797 |
Jul 24, 2002 |
|
|
|
09276019 |
Mar 25, 1999 |
6259688 |
|
|
09851740 |
May 9, 2001 |
|
|
|
08939146 |
Sep 29, 1997 |
6014373 |
|
|
09276019 |
Mar 25, 1999 |
|
|
|
08654994 |
May 29, 1996 |
5719852 |
|
|
08939146 |
Sep 29, 1997 |
|
|
|
08279477 |
Jul 26, 1994 |
5553062 |
|
|
08654994 |
May 29, 1996 |
|
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08051017 |
Apr 22, 1993 |
5363403 |
|
|
08279477 |
Jul 26, 1994 |
|
|
|
Current U.S.
Class: |
370/335 |
Current CPC
Class: |
H04B 1/7093 20130101;
H04B 1/71075 20130101; H04B 1/709 20130101 |
Class at
Publication: |
370/335 |
International
Class: |
H04B 7/216 20060101
H04B007/216 |
Claims
1. A method for recovering data transmitted over a plurality of
channels employing wireless code division multiple access
communication, comprising: a) receiving the plurality of channels
as a received signal, each channel associated with a code; b)
subtracting for each of the plurality of channels others of the
plurality of channels from the received signal and despreading a
result of that subtracting as data for that channel; and c)
respreading that channel despread signal with a respective channel
code; wherein the respreading channel code is aligned to a timing
of the despread received signal.
2. The method of claim 1 wherein step (b) includes, for each
channel: despreading the received signal with the others channel
codes; respreading the despread others channel codes using the
other channels codes; and subtracting from the received signal the
respread other channels.
3. The method of claim 2 wherein the despreading is performed by a
mixer.
4. The method of claim 2 wherein the despreading is performed by a
matched filter.
Description
CROSS REFERENCE TO RELATED APPLICATIONS
[0001] This application is a continuation of application Ser. No.
10/201,797, filed on Jul. 24, 2002, which is a continuation of
application Ser. No. 09/851,740, filed May 9, 2001, now U.S. Pat.
No. 6,868,076, which is a continuation of application Ser. No.
09/276,019, filed Mar. 25, 1999, now U.S. Pat. No. 6,259,688, which
is a continuation of U.S. application Ser. No. 08/939,146, filed
Sep. 29, 1997, now U.S. Pat. No. 6,014,373, which is a continuation
of U.S. application Ser. No. 08/654,994, filed May 29, 1996, now
U.S. Pat. No. 5,719,852, which is a continuation of U.S.
application Ser. No. 08/279,477, filed Jul. 26, 1994, now U.S. Pat.
No. 5,553,062, which is a continuation-in-part of U.S. application
Ser. No. 08/051,017, filed Apr. 22, 1993, now U.S. Pat. No.
5,363,403, all of which are incorporated herein by reference as if
fully set forth.
BACKGROUND
[0002] This invention relates to spread-spectrum communications,
and more particularly to an interference canceller employed by a
remote terminal for reducing interference in a direct sequence,
code division multiple access receiver.
[0003] Direct sequence, code division multiple access,
spread-spectrum communications systems are capacity limited by
interference caused by other simultaneous users. This is compounded
if adaptive power control is not used, or is used but is not
perfect.
[0004] Code division multiple access is interference limited. The
more users transmitting simultaneously, the higher the bit error
rate (BER). Increased capacity requires forward error correction
(FEC) coding, which in turn, increases the data rate and limits
capacity.
SUMMARY
[0005] A general object of the invention is to reduce noise
resulting from N-1 interfering signals in a direct sequence,
spread-spectrum code division multiple access receiver.
[0006] The present invention, as embodied and broadly described
herein, provides a method for recovering data transmitted over a
plurality of channels employing wireless code division multiple
access communication. The method comprises receiving the plurality
of channels as a received signal, each channel associated with a
code. Others from the plurality of channels from the received
signal is subtracted for each for each of the plurality of channels
and a result a result of that subtracting as data for that channel
is despread. That channel despread signal is respread with a
respective channel code, wherein the respreading channel code is
aligned to a timing of the despread received signal.
[0007] Additional objects and advantages of the invention are set
forth in part in the description which follows, and in part are
obvious from the description, or may be learned by practice of the
invention. The objects and advantages of the invention also may be
realized and attained by means of the instrumentalities and
combinations particularly pointed out in the appended claims.
BRIEF DESCRIPTION OF THE DRAWING(S)
[0008] The accompanying drawings, which are incorporated in and
constitute a part of the specification, illustrate preferred
embodiments of the invention, and together with the description
serve to explain the principles of the invention.
[0009] FIG. 1 is a block diagram of the spread-spectrum CDMA
interference canceller using correlators;
[0010] FIG. 2 is a block diagram of the spread-spectrum CDMA
interference canceller for processing multiple channels using
correlators;
[0011] FIG. 3 is a block diagram of the spread-spectrum CDMA
interference canceller using matched filters;
[0012] FIG. 4 is a block diagram of the spread-spectrum CDMA
interference canceller for processing multiple channels using
matched filters;
[0013] FIG. 5 is a block diagram of the spread-spectrum CDMA
interference canceller having multiple iterations for processing
multiple channels;
[0014] FIG. 6 illustrates theoretical performance characteristic
for E.sub.b/.eta.=6 dB;
[0015] FIG. 7 illustrates theoretical performance characteristic
for E.sub.b/.eta.=10 dB;
[0016] FIG. 8 illustrates theoretical performance characteristic
for E.sub.b/.eta.=15 dB;
[0017] FIG. 9 illustrates theoretical performance characteristic
for E.sub.b/.eta.=20 dB;
[0018] FIG. 10 illustrates theoretical performance characteristic
for E.sub.b/.eta.=25 dB;
[0019] FIG. 11 illustrates theoretical performance characteristic
for E.sub.b/.eta.=30 dB;
[0020] FIG. 12 is a block diagram of interference cancellers
connected together;
[0021] FIG. 13 is a block diagram combining the outputs of the
interference cancellers of FIG. 12;
[0022] FIG. 14 illustrates simulation performance characteristics
for asynchronous, PG=100, Equal Powers, E.sub.bN=30 dB;
[0023] FIG. 15 illustrates simulation performance characteristics
for asynchronous, PG=100, Equal Powers, E.sub.bN=30 dB;
[0024] FIG. 16 illustrates simulation performance characteristics
for asynchronous, PG=100, Equal Powers, E.sub.bN=30 dB; and
[0025] FIG. 17 illustrates simulation performance characteristics
for asynchronous, PG=100, Equal Powers, E.sub.bN=30 db.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT(S)
[0026] Reference now is made in detail to the present preferred
embodiments of the invention, examples of which are illustrated in
the accompanying drawings, wherein like reference numerals indicate
like elements throughout the several views.
[0027] In the exemplary arrangement shown in FIG. 1, a
spread-spectrum code division multiple access (CDMA) interference
canceller is provided for reducing interference in a
spread-spectrum CDMA receiver having N channels. The present
invention also works on a spread-spectrum code division multiplexed
(CDMA) system. Accordingly, without loss of generality, the term
spread-spectrum CDMA signal, as used herein, includes
spread-spectrum CDMA signals and spread-spectrum CDM signals. In a
personal communications service, the interference canceller may be
used at a base station or in a remote unit such as a handset.
[0028] FIG. 1 illustrates the interference canceller for the first
channel, defined by the first chip-code signal. The interference
canceller includes a plurality of despreading means, a plurality of
timing means, a plurality of spread-spectrum-processing means,
subtracting means, and first channel-despreading means.
[0029] Using a plurality of chip-code signals, the plurality of
despreading means despreads the received spread-spectrum CDMA
signals as a plurality of despread signals, respectively. In FIG. 1
the plurality of despreading means is shown as first despreading
means, second despreading means, through N.sup.th despreading
means. The first despreading means includes a first correlator,
which is embodied, by way of example, as a first mixer 51, first
chip-code-signal generator 52, and a first integrator 54. The first
integrator 54 alternatively may be a first lowpass filter or a
first bandpass filter. The first mixer 51 is coupled between the
input 41 and the first chip-code-signal generator 52 and the first
integrator 54.
[0030] The second despreading means includes a second correlator,
which is embodied, by way of example, as second mixer 61, second
chip-code-signal generator 62 and second integrator 64. The second
integrator 64 alternatively may be a second lowpass filter or a
second bandpass filter. The second mixer 61, is coupled between the
input 41, the second chip-code-signal generator 62, and the second
integrator 64.
[0031] The N.sup.th despreading means is depicted as an N.sup.th
correlator shown, by way of example, as N.sup.th mixer 71, and
N.sup.th chip-code-signal generator 72, and N.sup.th integrator 74.
The N.sup.th integrator 74 alternatively may be an N.sup.th lowpass
filter or an N.sup.th bandpass filter. The N.sup.th mixer 71 is
coupled between the input 41, the N.sup.th chip-code-signal
generator 72 and the N.sup.th integrator 74.
[0032] As is well known in the art, the first through N.sup.th
despreading means may be embodied as any device which can despread
a channel in a spread-spectrum signal.
[0033] The plurality of timing means may be embodied as a plurality
of delay devices 53, 63, 73. A first delay device 53 has a delay
time T, which is approximately the same as the integration time
T.sub.b of first integrator 54, or time constant of the first
lowpass filter or first bandpass filter. A second delay device 63
has a time delay T, which is approximately the same as the
integration time T.sub.b of second integrator 64, or time constant
of the second lowpass filter or second bandpass filter. Similarly,
the N.sup.th delay device 73 has a time delay T, which is
approximately the same as the integration time T.sub.b of N.sup.th
integrator 74, or time constant of the N.sup.th lowpass filter or
N.sup.th bandpass filter. Typically, the integration times of the
first integrator 54, second integrator 64 through N.sup.th
integrator 74 are the same. If lowpass filters are used, then
typically the time constants of the first lowpass filter, second
lowpass filter through N.sup.th lowpass filter are the same. If
bandpass filters are used, then the time constants of the first
bandpass filter, second bandpass filter through N.sup.th bandpass
filter are the same.
[0034] The plurality of spread-spectrum-processing means
regenerators each of the plurality of despread signals as a
plurality of spread-spectrum signals. The plurality of
spread-spectrum-processing means uses a timed version, i.e. delayed
version, of the plurality of chip-code signals, for spread-spectrum
processing the plurality of despread signals, respectively, with a
chip-code signal corresponding to a respective despread signal. The
plurality of spread-spectrum-processing means is shown, by way of
example, as a first processing mixer 55, a second processing mixer
65, through an N.sup.th processing mixer 75. The first processing
mixer 55 is coupled to the first integrator 54, and through a first
delay device 53 to the first chip-code-signal generator 52. The
second processing mixer 65 is coupled to the second integrator 64,
and through the second delay device 63 to the second
chip-code-signal generator 62. The N.sup.th processing mixer 75 is
coupled to the N.sup.th integrator 74 through the delay device 73
to the N.sup.th chip-code-signal generator 72.
[0035] For reducing interference to a channel using an i.sup.th
chip-code signal of the spread-spectrum CDMA signal, the
subtracting means subtracts, from the spread-spectrum CDMA signal,
each of the N-1 spread-spectrum-processed-despread signals not
corresponding to the i.sup.th channel. The subtracting means
thereby generates a subtracted signal. The subtracting means is
shown as a first subtractor 150. The first subtractor 150 is shown
coupled to the output of the second processing mixer 65, through
the N.sup.th processing mixer 75. Additionally, the first
subtractor 150 is coupled through a main delay device 48 to the
input 41.
[0036] The i.sup.th channel-despreading means despreads the
subtracted signal with the i.sup.th chip-code signal as the
i.sup.th channel. The first channel-despreading means is shown as a
first channel mixer 147. The first channel mixer 147 is coupled to
the first delay device 53, and to the first subtractor 150. The
first channel integrator 146 is coupled to the first channel mixer
147.
[0037] The first chip-code-signal generator 52, the second
chip-code-signal generator 62, through the N.sup.th chip-code
signal generator 72 generate a first chip-code signal, a second
chip-code signal, through an N.sup.th chip-code signal,
respectively. The term "chip-code signal" is used herein to mean
the spreading signal of a spread-spectrum signal, as is well known
in the art. Typically the chip-code signal is generated from a
pseudorandom (PN) sequence. The first chip-code signal, the second
chip code signal, through the N.sup.th chip-code signal might be
generated from a first PN sequence, a second PN sequence, through
an N.sup.th PN sequence, respectively. The first PN sequence is
defined by or generated from a first chip codeword, the second PN
sequence is defined by or generated from a second chip codeword,
through the N.sup.th PN sequence is defined by or generated from an
N.sup.th chip-codeword. Each of the first chip codeword, second
chip codeword through N.sup.th chip codeword is distinct, i.e.
different from one another. In general, a chip codeword can be the
actual sequence of a PN sequence, or used to define settings for
generating the PN sequence. The settings might be the delay taps of
shift registers, for example.
[0038] A first channel of a received spread-spectrum CDMA signal at
input 41 is despread by first mixer 51 as a first despread signal,
using the first chip-code signal generated by first
chip-code-signal generator 52. The first despread signal from the
first mixer 51 is filtered through first integrator 54. First
integrator 54 integrates for a time T.sub.b, the time duration of a
symbol such as a bit. At the same time, the first chip-code signal
is delayed by time T by delay device 53. The delay time T is
approximately equal to the integration time T.sub.b plus system or
component delays. Systems or component delays are usually small,
compared to integration time T.sub.b.
[0039] The delayed version of the first chip-code signal is
processed with the first despread signal from the output of the
first integrator 54 using the first spreading mixer 55. The output
of the first spreading mixer 55 is fed to subtractors other than
first subtractor 150 for processing the second through N.sup.th
channels of the spread-spectrum CDMA signal.
[0040] For reducing interference to the first channel of the
spread-spectrum CDMA signal, the received spread-spectrum CDMA
signal is processed by the second through N.sup.th despreaders as
follows. The second channel of the spread-spectrum CDMA signal is
despread by the second despreading means. At the second mixer 61, a
second chip-code signal, generated by the second chip-code-signal
generator 62, despreads the second channel of the spread-spectrum
CDMA signal. The despread second channel is filtered through second
integrator 64. The output of the second integrator 64 is the second
despread signal. The second despread signal is spread-spectrum
processed by second processing mixer 65 by a delayed version of the
second chip-code signal. The second chip-code signal is delayed
through delay device 63. The delay device 63 delays the second
chip-code signal by time T. The second channel mixer 65
spread-spectrum processes a timed version, i.e. delayed version, of
the second chip-code signal with the filtered version of the second
spread-spectrum channel from second integrator 64. The term
"spread-spectrum process" as used herein includes any method for
generating a spread-spectrum signal by mixing or modulating a
signal with a chip-code signal. Spread-spectrum processing may be
done by product devices, EXCLUSIVE-OR gates, matched filters, or
any other device or circuit as is well known in the art.
[0041] Similarly, the N.sup.th channel of the spread-spectrum CDMA
signal is despread by the N.sup.th despreading means. Accordingly,
the received spread-spectrum CDMA signal has the N.sup.th channel
despread by N.sup.th mixer 61, by mixing the spread-spectrum CDMA
signal with the N.sup.th chip-code signal from N.sup.th
chip-code-signal generator 72. The output of the N.sup.th mixer 71
is filtered by N.sup.th integrator 74. The output of the N.sup.th
integrator 74, which is the N.sup.th despread signal, is a despread
and filtered version of the N.sup.th channel of the spread-spectrum
CDMA signal. The N.sup.th despread signal is spread-spectrum
processed by a delayed version of the N.sup.th chip-code signal.
The N.sup.th chip-code signal is delayed through N.sup.th delay
device 73. The N.sup.th processing mixer 75 spread-spectrum
processes the timed version, i.e. a delayed version, of the
N.sup.th chip-code signal with the N.sup.th despread signal.
[0042] At the first subtractor 150, each of the outputs of the
second processing mixer 65 through the N.sup.th processing mixer 75
is subtracted from a timed version, i.e. a delayed version, of the
spread-spectrum CDMA signal from input 41. The delay of the
spread-spectrum CDMA signal is timed through the first main delay
device 48. Typically, the delay of the first main delay device 48
is time T, which is approximately equal to the integration time of
the first integrator 54 through N.sup.th integrator 74.
[0043] At the output of the first subtractor 150, is generated a
first subtracted signal. The first subtracted signal, for the first
channel of the spread-spectrum CDMA signal, is defined herein to be
the outputs from the second processing mixer 65 through N.sup.th
processing mixer 75, subtracted from the delayed version of the
spread-spectrum CDMA signal. The second subtracted signal through
N.sup.th subtracted signal are similarly defined.
[0044] The delayed version of the first chip-code signal from the
output of first delay device 53 is used to despread the output of
the first subtractor 150. Accordingly, the first subtracted signal
is despread by the first chip-code signal by first channel mixer
147. The output of the first channel mixer 147 is filtered by first
channel integrator 147. This produces an output estimate d.sub.1 of
the first channel of the spread-spectrum CDMA signal.
[0045] As illustratively shown in FIG. 2, a plurality of
subtractors 150, 250, 350, 450 can be coupled appropriately to the
input 41 and to a first spreading mixer 55, second spreading mixer
65, third spreading mixer, through an N.sup.th spreading mixer 75
of FIG. 1. The plurality of subtractors 150, 250, 350, 450 also are
coupled to the main delay device 48 from the input 41. This
arrangement can generate a first subtracted signal from the first
subtractor 150, a second subtracted signal from the second
subtractor 250, a third subtracted signal from the third subtractor
350, through an N.sup.th subtracted signal from an N.sup.th
subtractor 450.
[0046] The outputs of the first subtractor 150, second subtractor
250, third subtractor 350, through the N.sup.th subtractor 450 are
each coupled to a respective first channel mixer 147, second
channel mixer 247, third channel mixer 347, through N.sup.th
channel mixer 447. Each of the channel mixers is coupled to a
delayed version of the first chip-code signal, g.sub.1 (t-T),
second chip-code signal, g.sub.2 (t-T), third chip-code signal,
g.sub.3 (t-T), through N.sup.th chip-code signal, g.sub.N (t-T).
The outputs of each of the respective first channel mixer 147,
second channel mixer 247, third channel mixer 347, through N.sup.th
channel mixer 447 are coupled to a first channel integrator 146,
second channel integrator 246, third channel integrator 346 through
N.sup.th channel integrator 446, respectively. At the output of
each of the channel integrators is produced an estimate of the
respective first channel d.sub.1, second channel d.sub.2, third
channel d.sub.3, through N.sup.th channel d.sub.N.
[0047] Referring to FIG. 1, use of the present invention is
illustrated for the first channel of the spread-spectrum CDMA
signal, with the understanding that the second through N.sup.th
CDMA channels work similarly. A received spread-spectrum CDMA
signal at input 41 is delayed by delay device 48 and fed to the
first subtractor 150. The spread-spectrum CDMA signal has the
second channel through N.sup.th channel despread by second mixer 61
using the second chip-code signal, through the N.sup.th mixer 71
using the N.sup.th chip-code signal. The respective second
chip-code signal through the N.sup.th chip-code signal are
generated by the second chip-code-signal generator 62 through the
N.sup.th chip-code-signal generator 72. The second channel through
N.sup.th channel are despread and filtered through the second
integrator 64 through the N.sup.th integrator 74, respectively. The
despreading removes, partially or totally, the non-despread
channels at the outputs of each of the second integrator 64 through
N.sup.th integrator 74.
[0048] In a preferred embodiment, each of the chip-code signal used
for the first chip-code-signal generator 52, second
chip-code-signal generator 62 through the N.sup.th chip-code-signal
generator 72, are orthogonal to each other. Use of chip-code
signals having orthogonality however, is not required for operation
of the present invention. When using orthogonal chip-code signals,
the despread signals have the respective channel plus noise at the
output of each of the integrators. With orthogonal chip-code
signals, theoretically the mixers remove channels orthogonal to the
despread channel. The respective channel is spread-spectrum
processed by the respective processing mixer.
[0049] At the output of the second processing mixer 65 through the
N.sup.th processing mixer 75 is a respread version of the second
channel through the N.sup.th channel, plus noise components
contained therein. Each of the second channel through N.sup.th
channel is then subtracted from the received spread-spectrum CDMA
signal by the first subtractor 150. The first subtractor 150
produces the first subtracted signal. The first subtracted signal
is despread by a delayed version of the first chip-code signal by
first channel mixer 147, and filtered by first channel filter 146.
Accordingly, prior to despreading the first channel of the
spread-spectrum CDMA signal, the second through N.sup.th channels
plus noise components aligned with these channels are subtracted
from the received spread-spectrum CDMA signal. As illustratively
shown in FIG. 3, an alternative embodiment of the spread-spectrum
CDMA interference canceller includes a plurality of first
despreading means, a plurality of spread-spectrum-processing means,
subtracting means, and second despreading means. In FIG. 3, the
plurality of despreading means is shown as first despreading means,
second despreading means through N.sup.th despreading means. The
first despreading means is embodied as a first matched filter 154.
The first matched filter 154 has an impulse response matched to the
first chip-code signal, which is used to spread-spectrum process
and define the first channel of the spread-spectrum CDMA signal.
The first matched filter 154 is coupled to the input 41.
[0050] The second despreading means is shown as second matched
filter 164. The second matched filter 164 has an impulse response
matched to the second chip-code signal, which is used to
spread-spectrum process and define the second channel of the
spread-spectrum CDMA signal. The second matched filter 164 is
coupled to the input 41.
[0051] The N.sup.th despreading means is shown as an N.sup.th
matched filter 174. The N.sup.th matched filter has an impulse
response matched to the N.sup.th chip-code signal, which is used to
spread-spectrum process and define the N.sup.th channel of the
spread-spectrum CDMA signal. The N.sup.th matched filter is coupled
to the input 41.
[0052] The term matched filter, as used herein, includes any type
of matched filter that can be matched to a chip-code signal. The
matched filter may be a digital matched filter or analog matched
filter. A surface acoustic wave (SAW) device may be used at a radio
frequency (RF) or intermediate frequency (IF). Digital signal
processors and application specific integrated circuits (ASIC)
having matched filters may be used at RF, IF or baseband
frequency.
[0053] In FIG. 3, the plurality of spread-spectrum-processing means
is shown as the first processing mixer 55, the second processing
mixer 65, through the N.sup.th processing mixer 75. The first
processing mixer 55 may be coupled through a first adjustment
device 97 to the first chip-code-signal generator 52. The second
processing mixer 65 may be coupled through the second adjustment
device 98 to the second chip-code-signal generator 62. The N.sup.th
processing mixer 75 may be coupled through the N.sup.th adjustment
device 99 to the N.sup.th chip-code-signal generator 72. The first
adjusting device 97, second adjustment device 98 through N.sup.th
adjustment device 99 are optional, and are used as an adjustment
for aligning the first chip-code signal, second chip-code signal
through N.sup.th chip-code signal with the first despread signal,
second despread signal through N.sup.th despread signal, outputted
from the first matched filter 154, second matched filter 164
through N.sup.th matched filter 174, respectively.
[0054] The subtracting means is shown as the first subtractor 150.
The first subtractor 150 is coupled to the output of the second
processing mixer 65, through the N.sup.th processing mixer 75.
Additionally, the first subtractor 150 is coupled through the main
delay device 48 to the input 41.
[0055] The first channel-despreading means is shown as a first
channel-matched filter 126. The first channel-matched filter 126 is
coupled to the first subtractor 150. The first channel-matched
filter 126 has an impulse response matched to the first chip-code
signal.
[0056] A first channel of a received spread-spectrum CDMA signal,
at input 41, is despread by first matched filter 154. The first
matched filter 154 has an impulse response matched to the first
chip-code signal. The first chip-code signal defines the first
channel of the spread-spectrum CDMA signal, and is used by the
first chip-code-signal generator 52. The first chip-code signal may
be delayed by adjustment time .tau. by adjustment device 97. The
output of the first matched filter 154 is spread-spectrum processed
by the first processing mixer 55 with the first chip-code signal.
The output of the first processing mixer 55 is fed to subtractors
other than the first subtractor 150 for processing the second
channel through the N.sup.th channel of the spread-spectrum CDMA
signals.
[0057] For reducing interference to the first spread-spectrum
channel, the received spread-spectrum CDMA signal is processed by
the second despreading means through N.sup.th despreading means as
follows. The second matched filter 164 has an impulse response
matched to the second chip-code signal. The second chip-code signal
defines the second channel of the spread-spectrum CDMA signal, and
is used by the second chip-code-signal generator 62. The second
matched filter 164 despreads the second channel of the
spread-spectrum CDMA signal. The output of the second matched
filter 164 is the second despread signal. The second despread
signal triggers second chip-code-signal generator 62. The second
despread signal also is spread-spectrum processed by second
processing mixer 65 by a timed version of the second chip-code
signal. The timing of the second chip-code signal triggers the
second despread signal from the second matched filter 164.
[0058] Similarly, the N.sup.th channel of the spread-spectrum CDMA
signal is despread by the N.sup.th despreading means. Accordingly,
the received spread-spectrum CDMA signal has the N.sup.th channel
despread by N.sup.th matched filter 174. The output of the N.sup.th
matched filter 174 is the N.sup.th despread signal, i.e. a despread
and filtered version of the N.sup.th channel of the spread-spectrum
CDMA signal. The N.sup.th despread signal is spread-spectrum
processed by a timed version of the N.sup.th chip-code signal. The
timing of the N.sup.th chip-code signal is triggered by the
N.sup.th despread signal from the N.sup.th matched filter 174. The
N.sup.th processing mixer 75 spread-spectrum processes the timed
version of the N.sup.th chip-code signal with the N.sup.th despread
signal.
[0059] At the first subtractor 150, each of the outputs of the
second processing mixer 65 through the N.sup.th processing mixer 75
are subtracted from a delayed version of the spread-spectrum CDMA
signal from input 41. The delay of the spread-spectrum CDMA signal
is timed through delay device 48. The time of delay device 48 is
set to align the second through N.sup.th
spread-spectrum-processed-despread signals for subtraction from the
spread-spectrum CDMA signal. This generates at the output of the
first subtractor 150, a first subtracted signal. The subtracted
signal is despread by the first channel-matched filter 126. This
produces an output estimate d.sub.1 of the first channel of the
spread-spectrum CDMA signal.
[0060] As illustrated in FIG. 4, a plurality of subtractors 150,
250, 350, 450 can be coupled appropriately to the output from a
first processing mixer, second processing mixer, third processing
mixer, through an N.sup.th processing mixer, and to a main delay
device form the input. A first subtracted signal is outputted from
the first subtractor 150, a second subtracted signal is outputted
from the second subtractor 250, a third subtracted signal is
outputted from the third subtractor 350, through an N.sup.th
subtractor signal is outputted from the N.sup.th subtractor
450.
[0061] The output of the first subtractor 150, second subtractor
250, third subtractor 350, through the N.sup.th subtractor 450 are
each coupled to a respective first channel-matched filter 126,
second channel-matched filter 226, third channel-matched filter
326, through N.sup.th channel-matched filter 426. The first
channel-matched filter 126, second channel-matched filter 226,
third channel-matched filter 326 through N.sup.th channel-matched
filter 426 have an impulse response matched to the first chip-code
signal, second chip-code signal, third chip-code signal, through
N.sup.th chip-code signal, defining the first channel, second
channel, third channel through N.sup.th channel, respectively, of
the spread-spectrum CDMA signal. At each of the outputs of the
respective first channel-matched filter 126, second channel-matched
filter 226, third channel-matched filter 326, through N.sup.th
channel-matched filter 426, is produced an estimate of the
respective first channel d.sub.1, second channel d.sub.2, third
channel d.sub.3, through N.sup.th channel d.sub.N.
[0062] In use, the present invention is illustrated for the first
channel of the spread-spectrum CDMA signal, with the understanding
that the second channel through N.sup.th channel work similarly. A
received spread-spectrum CDMA signal at input 41 is delayed by
delay device 48 and fed to subtractor 150. The same spread-spectrum
CDMA signal has the second through N.sup.th channel despread by the
second matched filter 164 through the N.sup.th matched filter 174.
This despreading removes the other CDMA channels from the
respective despread channel. In a preferred embodiment, each of the
chip-code signals used for the first channel, second channel,
through the N.sup.th channel, is orthogonal to the other chip-code
signals. At the output of the first matched filter 154, second
matched filter 164 through N.sup.th matched filter 174, are the
first despread signal, second despread signal through N.sup.th
despread signal, plus noise.
[0063] The respective channel is spread-spectrum processed by the
processing mixers. Accordingly, at the output of the second
processing mixer 65 through the N.sup.th processing mixer 75 is a
spread version of the second despread signal through the N.sup.th
despread signal, plus noise components contained therein. Each of
the spread-spectrum-processed-despread signals, is then subtracted
from the received spread-spectrum CDMA signal by the first
subtractor 150. This produces the first subtracted signal.
[0064] The first subtracted signal is despread by first
channel-matched filter 126. Accordingly, prior to despreading the
first channel of the spread-spectrum CDMA signal, the second
channel through N.sup.th channel plus noise components aligned with
these channels, are subtracted from the received spread-spectrum
CDMA signal.
[0065] As is well known in the art, correlators and matched filters
may be interchanged to accomplish the same function. FIGS. 1 and 3
show alternate embodiments using correlators or matched filters.
The arrangements may be varied. For example, the plurality of
despreading means may be embodied as a plurality of matched
filters, while the channel despreading means may be embodied as a
correlator. Alternatively, the plurality of despreading means may
be a combination of matched filters and correlators. Also, the
spread-spectrum-processing means may be embodied as a matched
filter or SAW, or as EXCLUSIVE-OR gates or other devices for mixing
a despread signal with a chip-code signal. As is well known in the
art, any spread-spectrum despreader or demodulator may despread the
spread-spectrum CDMA signal. The particular circuits shown in FIGS.
1-4 illustrate the invention by way of example.
[0066] The concepts taught in FIGS. 1-4 may be repeated, as shown
in FIG. 5. FIG. 5 illustrates a first plurality of interference
cancellers 511, 512, 513, a second plurality of interference
cancellers 521, 522, 523, through an N.sup.th plurality of
interference cancellers 531, 532, 533. Each plurality of
interference cancellers includes appropriate elements as already
disclosed, and referring to FIGS. 1-4, the input is delayed through
a delay device in each interference canceller.
[0067] The received spread-spectrum CDMA signals has interference
canceled initially by the first plurality of interference
cancellers 511, 512, 513, thereby producing a first set of
estimates, i.e. a first estimate d.sub.11, a second estimate
d.sub.12, through an N.sup.th estimate d.sub.1N, of the first
channel, second channel through the N.sup.th channel, of the
spread-spectrum CDMA signal. The first set of estimates can have
interference canceled by the second plurality of interference
cancellers 521, 522, 523. The first set of estimates d.sub.11,
d.sub.12, . . . , d.sub.1N, of the first channel, second channel
through N.sup.th channel, are input to the second plurality of
interference cancellers, interference canceller 521, interference
canceller 522 through N.sup.th interference canceller 523 of the
second plurality of interference cancellers. The second plurality
of interference cancellers thereby produce a second set of
estimates, i.e. d.sub.21, d.sub.22, . . . , d.sub.2N, of the first
channel, second channel, through N.sup.th channel. Similarly, the
second set estimates can pass through a third plurality of
interference cancellers, and ultimately through an M.sup.th set of
interference cancellers 531, 532, 533, respectively.
[0068] The present invention also includes a method for reducing
interference in a spread-spectrum CDMA receiver having N chip-code
channels. Each of the N channels is identified by a distinct
chip-code signal. The method comprises the steps of despreading,
using a plurality of chip-code signals, the spread-spectrum CDMA
signal as a plurality of despread signals, respectively. Using a
timed version of the plurality of chip-code signals, the plurality
of despread signals are spread-spectrum processed with a chip-code
signal corresponding to a respective despread signal. Each of the
N-1 spread spectrum-processed-despread signals, is subtracted from
the spread-spectrum CDMA signal, with the N-1
spread-spectrum-processed-despread signals not including a
spread-spectrum-processed signal of the i.sup.th despread signal,
thereby generating a subtracted signal. The subtracted signal is
despread to generate the i.sup.th channel.
[0069] The probability of error P.sub.e for direct sequence,
spread-spectrum CDMA system is: P e = 1 2 .times. erfc .function. (
.alpha. .times. .times. SNR ) .times. 1 2 ##EQU1## where erfc is
complementary error function, SNR is signal-to-noise ratio, and
1.ltoreq..alpha..ltoreq.2. The value of cL depends on how a
particular interference canceller system is designed.
[0070] The SNR after interference cancellation and method is given
by: SNR = ( PG / N ) R + 1 1 + ( PG / N ) R + 1 .times. 1 E b /
.eta. .times. 1 - ( N / PG ) R + 1 1 - N / PG ##EQU2## where N is
the number of channels, PG is the processing gain, R is the number
of repetitions of the interference canceller, E.sub.b is energy per
information bit and .eta. is noise power spectral density.
[0071] FIG. 6 illustrates theoretical performance characteristic,
of the interference canceller and method for when E.sub.b/.eta.=6
dB. The performance characteristic is illustrated for SNR out of
the interference canceller, versus PG/N. The lowest curve, for R=0,
is the performance without the interference canceller. The curves,
for R=1 and R=2, illustrates improved performance for using one and
two iterations of the interference canceller as shown in FIG. 5. As
PG/N.fwdarw.1, there is insufficient SNR to operate. If PG>N,
then the output SNR from the interference canceller approaches
E.sub.b/.eta.. Further, if (N/PG).sup.R+1<<1, then
SNR.fwdarw.(E.sub.b/.eta.)(1-N/PG).
[0072] FIG. 7 illustrates the performance characteristic for when
E.sub.b/.eta.=10 dB.
[0073] FIG. 7 illustrates that three iterations of the interference
canceller can yield a 4 dB improvement with PG/N=2.
[0074] FIG. 8 illustrates the performance characteristic for when
E.sub.b/.eta.=15 dB. With this bit energy to noise ratio, two
iterations of the interference canceller can yield 6 dB improvement
for PG/N=2.
[0075] FIG. 9 illustrates the performance characteristic for when
E.sub.b/.eta.=20 dB. With this bit energy to noise ratio, two
iterations of the interference canceller can yield 6 dB improvement
for PG/N=2. Similarly, FIGS. 10 and 11 show that one iteration of
the interference canceller can yield more than 10 dB improvement
for PG/N=2.
[0076] The present invention may be extended to a plurality of
interference cancellers. As shown in FIG. 12, a received
spread-spectrum signal, R(t), is despread and detected by CDMA/DS
detector 611. Each of the channels is represented as outputs
O.sub.01, O.sub.02, O.sub.03, . . . , O.sub.0m. Thus, each output
is a despread, spread-spectrum channel from a received
spread-spectrum signal, R(t).
[0077] Each of the outputs of the CDMA/DS detector 611 is passed
through a plurality of interference cancellers 612, 613, . . . ,
614, which are serially connected. Each of the spread-spectrum
channels passes through the interference canceling processes as
discussed previously. The input to each interference canceller is
attained by sampling and holding the output of the previous stage
once per bit time. For channel i, the first interference canceller
samples the output of the CDMA/DS detector at time t=T+.tau..sub.i.
This value is held constant as the input until t=2T+.tau..sub.i at
which point the next bit value is sample. Thus, the input waveforms
to the interference canceller are estimates, d
.sub.i(t-.tau..sub.i), of the original data waveform
(d.sub.i(t-.tau..sub.i), and the outputs are second estimates, d
.sub.i(t-.tau..sub.i). The M spread-spectrum channel outputs
O.sub.0i, i=1, 2, . . . , M, are passed through interference
canceller 612 to produce a new corresponding set of channel outputs
O.sub.1i, i=1, 2, . . . , M.
[0078] As shown in FIG. 13, the outputs of a particular
spread-spectrum channel, which are at the output of each of the
interference cancellers, may be combined. Accordingly, combiner 615
can combine the output of the first channel which is from CDMA/DS
detector 611, and the output O.sub.11 from the first interference
canceller 612, and the output O.sub.21 from the second interference
canceller 613, through the output O.sub.N1 from the N.sup.th
interference canceller 614. Each output to be combined is of the
corresponding bit. Therefore "s" bit time delays is inserted for
each O.sub.s1. The combined outputs are then passed through the
decision device 616. This can be done for each spread spectrum
channel, and therefore designate the outputs of each of the
combiners 615, 617, 619 as averaged outputs O.sub.1 for channel
one, averaged output O.sub.2 for channel two, and averaged output
O.sub.M for channel M. Each of the averaged outputs are
sequentially passed through decision device 616, decision device
618, and decision device 620. Preferably, the averaged outputs have
multiplying factor c.sub.j which may vary according to a particular
design. In a preferred embodiment, c.sub.j=1/2.sup.j. This allows
the outputs of the various interference cancellers to be combined
in a particular manner.
[0079] FIGS. 14-17 illustrate simulation performance
characteristics for the arrangement of FIGS. 12 and 13. FIGS. 14-17
are for asynchronous channel (relative time delays are uniformly
distributed between 0 and bit time, T), processing gain of 100, all
users have equal powers, and thermal signal to noise ratio
(E.sub.bN of 30 dB). Length 8191 Gold codes are used for the PN
sequences.
[0080] In FIG. 14, performance characteristic of each of the output
stages of FIG. 12 is shown. Thus, S0 represents the BER performance
at the output of CDMA/DS detector 611, S1 represents the BER
performance at the output of interference canceller 612, S2
represents the BER performance at the output of interference
canceller 613, etc. No combining of the outputs of the interference
cancellers are used in determining the performance characteristic
shown in FIG. 14. Instead, the performance characteristic is for
repetitively using interference cancellers. As a guideline, in each
of the subsequent figures the output for each characteristic of
CDMA/DS detector 611 is shown in each figure.
[0081] FIG. 15 shows the performance characteristic when the output
of subsequent interference cancellers are combined. This is shown
for a particular channel. Thus, curve S0 is the output of the
CDMA/DS detector 611. Curve S1 represents the BER performance of
the average of the outputs of CDMA/DS detector 611 and interference
canceller 612. Here C.sub.0=C.sub.1=1/2C.sub.j=0,j not equal to
zero, one. Curve S2 represents the BER performance of the average
output of interference canceller 613 and interference canceller
612. Curve S2 is determined using the combiner shown in FIG. 13.
Here, C.sub.1 and C.sub.2 are set equal to 1/2 and all other
C.sub.j set to zero. Similarly, curve S3 is the performance of the
output of a second and third interference canceller averaged
together. Thus, curve S3 is the performance characteristic of the
average between outputs of a second and third interference
canceller. Curve S4 is the performance characteristic of the
average output of a third and fourth interference canceller. Only
two interference cancellers are taken at a time for determining a
performance characteristic of an average output of those to
particular interference cancellers.
[0082] FIG. 16 shows the regular outputs for the CDMA/DS detector
611, and a first and second interference canceller 612, 613.
Additionally, the average output of the CDMA/DS detector 611 and
the first interference canceller 612 is shown as S1 AVG. The BER
performance of the average of the outputs of the first interference
canceller 612 and the second interference canceller 613 is shown as
the average output S2 AVG.
[0083] FIG. 17 shows performance characteristic correspondence for
those of FIG. 16, but in terms of signal to-noise ratio in decibels
(dB).
[0084] It will be apparent to those skilled in the art that various
modifications can be made to the spread-spectrum CDMA interference
canceller and method of the instant invention without departing
from the scope or spirit of the invention, and it is intended that
the present invention cover modifications and variations of the
spread-spectrum CDMA interference canceller and method provided
they come within the scope of the appended claims and their
equivalents.
* * * * *