U.S. patent application number 10/177575 was filed with the patent office on 2002-12-26 for volt-second balanced pfcpwm power converter.
This patent application is currently assigned to Champion Microelectronic Corp.. Invention is credited to Hwang, Jeffrey H..
Application Number | 20020196006 10/177575 |
Document ID | / |
Family ID | 23159323 |
Filed Date | 2002-12-26 |
United States Patent
Application |
20020196006 |
Kind Code |
A1 |
Hwang, Jeffrey H. |
December 26, 2002 |
Volt-second balanced PFCPWM power converter
Abstract
A volt-second balanced, power factor correction (PFC),
pulse-width modulation (PWM) two-stage power converter. A first PFC
stage receives an AC input signal and forms a regulated
intermediate output voltage. A second stage receives the
intermediate output voltage and forms a regulated DC output
voltage. A level of the intermediate output voltage is monitored
and used to adjust the duty cycle of a main power switch in the PWM
stage. By adjusting the PWM duty cycle based on the level of the
intermediate output voltage, rather than the DC output voltage, the
PWM converter is volt-second balanced. Further, when a controller
for the power converter is implemented as an integrated circuit, a
pin is not required for monitoring the regulated DC output.
Accordingly, the number of pins is minimized.
Inventors: |
Hwang, Jeffrey H.;
(Saratoga, CA) |
Correspondence
Address: |
Derek J. Westberg
Stevens & Westberg LLP
Suite 201
99 North First St.
San Jose
CA
95113
US
|
Assignee: |
Champion Microelectronic
Corp.
San Jose
CA
|
Family ID: |
23159323 |
Appl. No.: |
10/177575 |
Filed: |
June 21, 2002 |
Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
|
|
60300492 |
Jun 21, 2001 |
|
|
|
Current U.S.
Class: |
323/288 |
Current CPC
Class: |
H02M 1/092 20130101;
H02M 1/32 20130101; Y02B 70/10 20130101; H02M 1/007 20210501; H02M
3/33523 20130101; Y02P 80/10 20151101; H02M 1/0845 20130101; H02M
1/36 20130101; H02M 1/4225 20130101; Y10S 323/908 20130101; Y10S
323/901 20130101 |
Class at
Publication: |
323/288 |
International
Class: |
G05F 001/40 |
Claims
What is claimed is:
1. A two stage power converter comprising: a power factor
correction stage for forming an intermediate voltage; and a pulse
width modulation stage for receiving the intermediate voltage and
for forming a DC output voltage wherein a duty cycle of the pulse
width modulation stage is adjusted in response to a level of the
intermediate voltage.
2. The power converter according to claim 1, wherein a periodic
ramp signal formed for controlling timing of switching in the power
factor correction stage is compared to a signal representative of
the intermediate voltage for controlling a switch of the pulse
width modulation stage.
3. The power converter according to claim 1, wherein the power
factor correction stage comprises: a first switch for modulating a
first input current drawn from an alternating-current (AC) source;
and a power factor correction controller for controlling the first
switch so as to maintain the first input current substantially in
phase with an input voltage of the source and for forming the
intermediate output voltage across a first energy storage
element.
4. The power converter according to claim 3, wherein the power
factor correction controller performs average current mode
control.
5. The power converter according to claim 3, wherein the power
factor correction controller performs input current shaping.
6. The power converter according to claim 1, wherein the pulse
width modulation stage comprises: means for forming an error signal
that is representative of the intermediate output voltage and a
desired level for the intermediate output voltage; and means for
comparing the error signal to a periodic ramp signal wherein an
output of said means for comparing controls the duty cycle of the
pulse width modulation stage.
7. The power converter according to claim 6, wherein switching in
the pulse width modulation stage is synchronized with switching in
the power factor correction stage.
8. The power converter according to claim 7, wherein the periodic
ramp signal is synchronized with switching the power factor
correction stage.
9. The power converter according to claim 1, wherein the pulse
width modulation stage comprises an active clamping circuit.
10. The power converter according to claim 1, wherein the pulse
width modulation stage is substantially volt-second balanced when
the duty-cycle is less than 66.6 percent.
11. The power converter according to claim 1, wherein the pulse
width modulation stage is substantially volt-second balanced for
when the duty-cycle is fifty percent.
12. The power converter according to claim 1, further comprising a
controller for controlling switching the power factor correction
stage and in the pulse width modulation stage the controller being
implemented as an integrated circuit and lacking a pin for
monitoring the DC output voltage.
13. A controller for a two stage power converter comprising: a
power factor correction stage controller for controlling switching
in a power factor correction stage of the power converter for
forming an intermediate voltage; and a pulse width modulation stage
controller for monitoring the intermediate voltage and for
adjusting a duty cycle of the pulse width modulation stage in
response to a level of the intermediate voltage.
14. The controller according to claim 13, comprising means for
comparing a periodic ramp signal formed for controlling timing of
switching in the power factor correction stage to a signal
representative of the intermediate voltage for controlling
switching in the pulse width modulation stage.
15. The controller according to claim 13, wherein the power factor
correction stage controller controls a first switch so as to
maintain the first input current substantially in phase with an
input voltage of the source and for forming the intermediate output
voltage across a first energy storage element.
16. The controller according to claim 15, wherein the power factor
correction controller performs average current mode control.
17. The controller according to claim 15, wherein the power factor
correction controller performs input current shaping .
18. The controller according to claim 13, wherein the pulse width
modulation stage comprises: means for forming an error signal that
is representative of the intermediate output voltage and a desired
level for the intermediate output voltage; and means for comparing
the error signal to a periodic ramp signal wherein an output of
said means for comparing controls the duty cycle of the pulse width
modulation stage.
19. The controller according to claim 18, wherein switching in the
pulse width modulation stage is synchronized with switching in the
power factor correction stage.
20. The power converter according to claim 13, wherein the
controller is implemented as an integrated circuit and lacking a
pin for monitoring the DC output voltage.
21. A method for performing power conversion comprising: modulating
a first input current drawn from an alternating-current (AC) source
with a first switch for maintaining the first input current
substantially in phase with an input voltage of the source and for
forming an intermediate output voltage across a first energy
storage element; and modulating a second input current from the
first energy storage element for forming a DC output voltage across
a second energy storage element, wherein a duty cycle for
modulating the second input current is based on a level of the
intermediate output voltage.
22. The method according to claim 21, further comprising: forming a
first error signal that is representative of a difference between
the intermediate output voltage and a desired level for the
intermediate output voltage; and comparing the first error signal
to a periodic ramp signal, wherein a result of said comparing
controls the duty cycle for modulating the second input
current.
23. The method according to claim 22, further comprising sensing a
level of the first input current and the level of the intermediate
output voltage for controlling a duty cycle for modulating the
first input current.
24. The method according to claim 23, further comprising sensing a
level of the input voltage for controlling the duty cycle of the
first input current.
25. The method according to claim 23, further comprising: forming a
second error signal that is representative of a difference between
the intermediate output voltage and a desired level for the
intermediate output voltage; integrating the second error signal
thereby forming a signal that is representative of an integration
of the second error signal; and comparing the signal that is
representative of an integration of the second error signal to a
signal that is representative of the input current, wherein a
result of said comparing controls the duty cycle for modulating the
first input current.
26. The method according to claim 22, wherein said periodic ramp
signal is synchronized with operation of the first switch.
Description
[0001] This application claims the benefit of U.S. Provisional
Application Serial No. 60/300,492, filed Jun. 21, 2001.
FIELD OF THE INVENTION
[0002] The invention relates to switching power converters. More
particularly, the invention relates to PFC-PWM two-stage power
converters.
BACKGROUND OF THE INVENTION
[0003] A conventional PFC-PWM two-stage power converter includes a
first PFC stage and a second PWM stage. An intermediate voltage
formed by the PFC stage is monitored and switching in the PFC is
adjusted in a feedback loop in response to the monitored
intermediate voltage. A DC output voltage of the PWM stage is
monitored and switching in the PWM stage is adjusted in a feedback
loop in response to this monitored DC output voltage. Thus, a
controller for the converter monitors both the intermediate voltage
and the DC output voltage.
[0004] It is desired to provide an improved PFC-PWM two-stage power
converter. It is to these ends that the present invention is
directed.
SUMMARY OF THE INVENTION
[0005] The invention is a volt-second balanced, power factor
correction (PFC), pulse-width modulation (PWM) two-stage power
converter. A first PFC stage receives an AC input signal and forms
a regulated intermediate output voltage. A second stage receives
the intermediate output voltage and forms a regulated DC output
voltage. A level of the intermediate output voltage is monitored
and used to adjust the duty cycle of a main power switch in the PWM
stage. By adjusting the PWM duty cycle based on the level of the
intermediate output voltage, rather than the DC output voltage, the
PWM converter is volt-second balanced. Further, when a controller
for the power converter is implemented as an integrated circuit, a
pin is not required for monitoring the regulated DC output.
Accordingly, the number of pins is minimized.
BRIEF DESCRIPTION OF THE DRAWINGS
[0006] FIG. 1 illustrates a schematic diagram of a PWM-PFC
two-stage power converter in accordance with the present
invention.
[0007] FIG. 2 illustrates a schematic diagram of a controller for
the power converter of FIG. 1 in accordance with an aspect of the
present invention;
[0008] FIG. 3 illustrates a schematic diagram of an alternate
embodiment of a controller for the power converter of FIG. 1 in
accordance with an aspect of the present invention; and
[0009] FIG. 4 illustrates a schematic diagram of an alternate
embodiment of a PWM stage of a power converter in accordance with
an aspect of the present invention.
DETAILED DESCRIPTION OF A PREFERRED EMBODIMENT
[0010] FIG. 1 illustrates a schematic diagram of a PWM-PFC
two-stage power converter 100 in accordance with the present
invention. A power supply 102, such an AC power source, may provide
a signal VAC that is coupled across input terminals of a bridge
rectifier 104. A first output terminal of the rectifier 104 may be
coupled to a first terminal of an inductor L1. A second terminal of
the inductor L1 may be coupled to an anode of a rectifying diode D1
and to a first terminal of a switch SW1 (e.g., a MOSFET). A cathode
of the diode D1 may be coupled to a first terminal of a capacitor
C1.
[0011] A second output terminal of the rectifier 104 may be coupled
to a first terminal of a current-sensing resistor Rsense. A second
terminal of the current-sensing resistor Rsense, a second terminal
of the switch SW1 and a second terminal of the capacitor C1 may be
coupled to a ground node. Collectively, the inductor L1, switch
SW1, diode D1, and capacitor C1 form a power factor correction
(PFC) stage of the power converter 100.
[0012] When the switch SW1 is closed, current from the rectifier
104 charges the inductor L1 with energy. When the switch SW1 is
opened, energy stored in the inductor L1 is discharged into the
capacitor C1. An output voltage Vo is formed by the PFC stage
across the capacitor C1. A controller 110, such as an integrated
circuit controller, may control the switch SW1 to regulate an
output voltage formed at the first terminal of a capacitor C1. The
controller 110 may include a conventional PFC controller 112.
[0013] A resistive divider including resistors R1 and R2 may be
coupled across the capacitor C1. A feedback voltage VFB that is
representative of the voltage Vo may be coupled to the PFC
controller 112. In addition, the current-sensing resistor Rsense
may be coupled to the PFC controller 112. Also, a first terminal of
an input voltage sensing resistor Rac may be coupled to the first
output terminal of the rectifier 104. A second terminal of resistor
Rac may be coupled to the PFC controller 112.
[0014] To form a switch control signal VSW1, the PFC controller 112
may receive a signal Isense formed at the first terminal of the
sensing resistor Rsense that is representative of an input current
Iin drawn from the source 102 and the signal VFB that is
representative of the output voltage Vo. The PFC controller 112 may
also receive a signal IAC that is representative of a rectified
input voltage Vin formed by the rectifier 104. The switch control
signal VSW1 may be coupled to control the switch SW1 to maintain
the input current substantially in phase with the input voltage VAC
in addition to regulating the output voltage Vo. A periodic ramp
signal RTCT may be generated by the controller 112, such as by an
oscillator (128 in FIG. 2 and 144 in FIG. 3) of the controller 112,
and may be used to control the switching frequency of the switch
SW1.
[0015] The intermediate output voltage Vo of the PFC stage serves
as an input source for pulse-width modulation (PWM) stage of the
converter 100. More particularly, the first terminal of the
capacitor C1 may be coupled to a first terminal (designated with a
"dot" according to the "dot" convention for designating winding
polarity) of a first winding of a transformer T1 and to a first
terminal of a second winding of the transformer T1. The second
winding may be inductively coupled to the first winding. A second
terminal of the first winding may be coupled to a first terminal of
a switch SW2 (e.g., a MOSFET). A second terminal (designated with a
"dot") of the second winding may be coupled to a cathode of a diode
D2. A second terminal of the switch SW2 and an anode of the diode
D2 may be coupled to the ground node.
[0016] A third winding of the transformer T1 may be inductively
coupled to the second winding. A first terminal of the third
winding may be coupled to an anode of a diode D3. A cathode of the
diode D3 may be coupled to a cathode of a diode D4 and to a first
terminal of an inductor L2. A second terminal of the inductor L2
may be coupled to first terminal of a capacitor C2. A second
terminal of the third winding may be coupled to an anode of the
diode D4 and to a second terminal of the capacitor C2. A regulated
output voltage VDC may be formed across the capacitor C2 by the PWM
stage.
[0017] The feedback signal VFB may be coupled to a non-inverting
input of an amplifier 114. An inverting input of the amplifier 114
may be coupled to an output of the amplifier 114 and to a first
terminal of a resistor R4. A second terminal of the resistor R4 may
be coupled to a first terminal of a resistor R3 and to an inverting
input of an amplifier 116. A reference voltage Vref1 (e.g., 2.5
volts) may be coupled to a non-inverting input of the amplifier
116. A second terminal of the resistor R3 may be coupled to an
output of the amplifier 116 and to a first input terminal of a
comparator 118. The periodic ramp signal RTCT may be coupled to a
second input terminal of the comparator 118. An output of the
comparator 118 forms a switch control signal VSW2. The switch
control signal VSW2 controls the switch SW2 to form the output
voltage VDC.
[0018] More particularly, when the switch SW1 is closed, the
transformer T1 is charged with energy. When the switch is opened,
the energy is discharged into the capacitor C2 through the inductor
L2. The diode D2 rectifies current in the second winding of the
transformer T1, while the diodes D3 and D4 rectify current in the
third winding of the transformer T1. The transformer T1 is part of
an active clamping circuit. It will be apparent, however, that
another topology may be used for the PFC stage.
[0019] A duty cycle of the switch SW2 controls the level of the
output voltage VDC. When the intermediate output voltage Vo is at a
desired level (e.g., 380 volts), then the duty cycle of the switch
SW2 is preferably approximately 50%. This steady-state duty-cycle
can be adjusted by selecting component values, such as inductance
values and winding ratios for the transformer T1, based on expected
power consumption by a load (not shown) that receives the output
voltage VDC.
[0020] When the intermediate voltage Vo rises under transient
conditions, so does the feedback voltage VFB. In response, the duty
cycle for the switch SW2 is decreased. Conversely, when the
intermediate voltage Vo falls, so does the feedback voltage VFB. In
response, the duty cycle for the switch SW2 is increased.
Accordingly, the output voltage VDC of the PWM stage is regulated
(i.e. maintained substantially constant) by the controller 110
monitoring the voltage at the input of the PWM stage (i.e. the
intermediate voltage Vo) rather than the output voltage VDC.
[0021] FIG. 2 illustrates a schematic diagram of an exemplary
controller 112 for the PFC stage of the power converter of FIG. 1
in accordance with an aspect of the present invention. The
controller 112 uses average current-mode control to adjust the
switching duty cycle of the switch SW1. The output voltage sensing
signal VFB may be coupled to a first input of an amplifier 120. A
second input of the amplifier 120 may be coupled to receive a
reference voltage VREF2. An output of the amplifier 120 forms an
error signal which is representative of a difference between the
intermediate output voltage Vo and a desired level for the
intermediate output voltage Vo. The error signal may be coupled to
a first input of a multiplier 122. The input voltage sensing signal
IAC may be coupled to a second input of the multiplier 122.
[0022] An output of the multiplier 122 may be coupled to a first
input terminal of an amplifier 124. The input current sensing
signal ISENSE may be coupled to a second input of the amplifier 124
via a resistor R5. An output of the error amplifier 124 may be
coupled to a first input terminal of a modulating comparator 126.
An oscillator 128 may form a clock signal VCLK and a linear
periodic ramp signal VRAMP that is synchronized to the clock signal
VCLK. The ramp signal VRAMP may be coupled to a second input
terminal of the modulating comparator 126. The ramp output of the
oscillator 128 may be formed, for example, by charging a capacitor
(not shown) with a constant current. An output of the modulating
comparator 126 may be coupled as an input R of a flip-flop 130. The
clock output VCLK of the oscillator 128 may be coupled as an input
S of the flip-flop 130. An output Q of the flip-flop 130 may form
the switch control signal VSW1.
[0023] The signal output from the amplifier 124 modulates up and
down. When compared to the linear ramp signal from the oscillator
128, this adjusts the switching duty cycle of the PFC stage of the
power converter 100 so as to regulate the intermediate output
voltage Vo. More particularly, the amplifier 124 adjusts the
switching duty cycle under closed loop control to maintain a
voltage differential across its inputs to nearly zero volts. This
forces the input current Iin to follow the waveform of the
rectified sine wave of the input voltage Vin. The current control
loop and the power delivery circuitry must have at least enough
bandwidth to follow this waveform. It will be apparent that
configuration of the controller 112 is exemplary and that
modifications may be made.
[0024] FIG. 3 illustrates a schematic diagram of an alternate
embodiment of a controller 112' for the power converter 100 of FIG.
1 in accordance with an aspect of the invention. The controller
112' uses input current shaping to adjust the duty cycle of the
switch SW1. The current sensing signal ISENSE is coupled to a first
terminal of a resistor R6. A second terminal of the resistor R6 may
be coupled to the first input of an amplifier 132 and to a first
terminal of a resistor R7. A second terminal of the resistor R7 may
be coupled to the output of the amplifier 132, while a second input
of the amplifier 132 may be coupled to a ground node. A signal VA
formed at the output of the amplifier 132 is representative of the
input current Iin. The signal VA may be coupled to a first input of
a comparator 134.
[0025] The voltage sensing signal VFB may be coupled to a first
input terminal of an amplifier 136. A second input terminal of the
amplifier 136 may be coupled to receive a reference voltage VREF4.
An output of the amplifier 136 forms an error signal VEAO which is
representative of a difference between the output voltage Vo and a
desired level for the output voltage Vo.
[0026] A ramp generator 138 receives the error signal VEAO as an
input and integrates the signal VEAO. Thus, the slope of a periodic
ramp signal formed by the ramp generator 138 depends on the
then-current level of the error signal VEAO. The signal from the
ramp generator 138 is then applied to a squaring element 140. An
output of the squaring element 140 is applied to the second input
terminal of the comparator 134.
[0027] An output of the comparator 134 may be coupled to a set
input S of a flip-flop or latch 142. An oscillator 144 may form a
clock signal VCLK, which is coupled to a reset input of the
flip-flop 142. In addition, the oscillator 144 may form a periodic
linear ramp signal RTCT RAMP for use by the PWM stage. A Q output
of the flip-flop 142 may form the switch control signal VSW1 which
controls the duty cycle of the switch SW1 so as to regulate the
intermediate output voltage Vo formed by the PFC stage.
[0028] The signal VSW1 may be reset to a logical low voltage level
upon a leading edge of each pulse in the clock signal VCLK. When
the signal VC exceeds the signal VA, the output of the comparator
134 may set the flip-flop 142 such that the switch control signal
VSW1 returns to a logical high voltage level. Thus, the duty cycle
of the switch SW1 is controlled with negative feedback to maintain
the input current En in phase with the input voltage Vin and to
regulate the output voltage Vo. It will be apparent that leading or
trailing edge modulation techniques may be utilized and that other
types of modulation may be used, such as frequency modulation.
Unlike the average current-mode controller illustrated in FIG. 2,
the input voltage sensing signal IAC is not required. Accordingly,
the resistor Rac may be omitted from FIG. 1.
[0029] Other switching power supplies that perform power factor
correction are described in: U.S. Pat. No. 5,804,950, entitled,
"Input Current Modulation for Power Factor Correction;" U.S. Pat.
No. 5,742,151, entitled, "Input Current Shaping Technique and Low
Pin Count for PFC-PWM Boost Converter;" U.S. Pat. No. 5,798,635,
entitled, "One Pin Error Amplifier and Switched Soft Start for an
Eight Pin PFC-PWM Combination Integrated Circuit Converter
Controller;" and co-pending U.S. patent application Ser. No.
______, filed May 31, 2002, and entitled, "Power Factor Correction
with Carrier Control and Input Voltage Sensing" the contents of all
of which are hereby incorporated by reference.
[0030] Advantages of the invention are that the PWM converter is
volt-second balanced. This is because the PWM duty cycle is
adjusted based on the level of the intermediate output voltage Vo,
rather than the output voltage VDC.
[0031] In one embodiment, the windings ratio between the first
winding (in series with the switch SW2) and second winding (in
series with the diode D2) of the transformer T1 (FIG. 1) may be:
2:1. In other words, the first winding has twice as many windings
as the second winding. The voltage Vo may have, for example, a
regulated level of 380 volts. Thus, when the switch SW2 is closed,
380 volts is applied across the first winding of the transformer.
Due to the windings ratio, 190 volts is induced across the second
winding (and the voltage across the diode D2 is, thus, 570 volts).
In addition, when the switch SW2 is closed, a volt-second product
for the first winding is equal to the duration of the switch being
closed (D) times the voltage Vo. Where the duty cycle (D) is 50%,
this yields a volt-second product of 50% times 380 volts or 190
volt-seconds. This represents a level of magnetic flux in the first
winding induced during the charging phase. If allowed to build over
multiple switching cycles, this could lead to saturation of the
transformer T1.
[0032] When the switch SW2 is opened, the voltage Vo is applied
across the second winding. As a result, a voltage of 760 volts is
induced across the first winding. Thus, when the switch SW2 is
open, a volt-second value for the first winding is equal to the
duration of the switch being opened (1-D) times the voltage Vo.
Where the duty cycle is 50%, the volt-second product for the
discharge phase is 50% times 760 volts or 380 volt-seconds.
Therefore, because the volt-second product during discharging is at
least as great as the volt-second product during charging the power
converter can be said to be volt-second balanced.
[0033] The maximum duty-cycle (D) given the above winding ratio is
2/3 or 66.6%. Thus, for charging, the volt-second product is 2/3
times 380 volts or 253 volt-seconds. And, for discharging, the
volt-second product is 1/3 times 760 volts or 253 volt-seconds.
Thus, the duty-cycle for the switch SW2 is preferably maintained
below 66.6% (e.g., 50%).
[0034] Thus, by controlling the duty-cycle of the switch SW2 based
on the voltage Vo, the duty-cycle is maintained such that the
transformer T1 is volt-second balanced. This is true despite
changes in the PWM output voltage VDC or changes in the
intermediate output voltage Vo. It will be apparent that other
parameters may be selected, while maintaining this volt-second
balance in accordance with the present invention. For example, a
different windings ratio may be selected for the transformer
T1.
[0035] Further, when the controller 110 for the power converter 100
is implemented as an integrated circuit, a pin is not required for
monitoring the regulated output VDC. Accordingly, the number of
pins is minimized. Further, the periodic ramp signal generated by
the PFC controller 112 may be used as a PWM ramp for the PWM stage.
This also reduces the need for an additional pin.
[0036] FIG. 4 illustrates a schematic diagram of an alternate
embodiment of PWM stage of a power converter in accordance with an
aspect of the present invention. The output voltage Vo of the PFC
stage may be applied to a first terminal of a capacitor C7, to a
first terminal of a resistor R27, to a first terminal of a
capacitor C20 to a cathode of a diode D8 and to a first terminal
(designated with a "dot") of a first primary winding of a
transformer T2. A second terminal of the capacitor C7 may be
coupled to a ground node. A second terminal of the resistor R27 and
a second terminal of the capacitor C20 may be coupled to a cathode
of a diode D13. An anode of the diode D13 may be coupled to a
second terminal of the first primary winding of the transformer T2,
to a first terminal of a capacitor C15 and to a drain of a
transistor Q3.
[0037] An anode of the diode D8 may be coupled to a second terminal
of the capacitor C15 and to first terminal of a second primary
winding of the transformer T2. A drain of the transistor switch Q3
may be coupled to a first terminal of a resistor R31 and to a
cathode of a Zener diode ZD1. A second terminal (designated with a
"dot") of the second primary winding of the transformer T2, a
second terminal of the resistor R31 and an anode of the diode ZD1
may be coupled to the ground node.
[0038] The PWM switch control signal VSW1 may be coupled to base
terminals of transistors Q6 and Q7. A supply voltage VCC may be
coupled to a first terminal of a capacitor C34 and to a collector
of the transistor Q6. An emitter of the transistor Q6 may be
coupled to a first terminal of a resistor R28 and to a collector of
the transistor Q7. A second terminal of the resistor 28 may be
coupled to a gate of the transistor Q3 and to a first terminal of a
resistor R29. A second terminal of the capacitor C34, a second
terminal of the resistor R29 and an emitter of the transistor Q7
may be coupled to a ground node.
[0039] Thus, the transistor switch Q3 operates in accordance with
the switch control signal VSW1. When the switch Q3 is closed,
current is induced in the first and second primary windings of the
transformer T2 which charges the primary windings with energy. When
the switch Q3 is open, energy from the primary windings is
discharged to first and second secondary windings of the
transformer T2. Also during each switching cycle, the resistor R29,
the diode D13 and capacitors C20, C15 function as a snubber to
limit induced voltages at the primary windings of the transformer
T2. As a result, the volt-second product applied to each primary
winding of the transformer T2 tends to remain balanced for each
phase of the switching cycle of the switch Q3. The arrangement of
FIG. 4 operates similarly to that of FIG. 1 in that the PWM
converter is substantially volt-second balanced. In other words the
volt-second product during the discharging phase is at least as
great as the volt-second product during the charging phase.
[0040] A first terminal (designated with a "dot") of the second
secondary winding of the transformer T2 may be coupled to a first
terminal of a capacitor C14 and to an anode of a diode D9A. A
second terminal of the capacitor C14 may be coupled to a first
terminal of a resistor R34. A second terminal of the resistor R34
may be coupled to a cathode of the diode D9A, to a cathode of a
diode D9B, to a first terminal of an inductor L4 and to a first
terminal of a resistor R35. A second terminal of the resistor R35
may be coupled to a first terminal of a capacitor C22. A second
terminal of the first secondary winding of the transformer T2, an
anode of the diode D9B and a second terminal of the capacitor C22
may be coupled to a ground node.
[0041] A second terminal of the inductor L4 may be coupled to a
first terminal of a capacitor C17 and to a first terminal of an
inductor L5. A second terminal of the inductor L5 may be coupled to
a first terminal of a capacitor C18 and to a first terminal of a
capacitor C19. A second terminal of the capacitors C17, C18 and C19
may be coupled to a ground node. The output voltage VDC of the PWM
stage may be formed across the capacitors C18 and C19.
[0042] A first terminal (designated with a "dot") of the second
secondary winding of the transformer T2 may be coupled to an anode
of a diode D16. A cathode of the diode D16 may be coupled to a
first terminal of a resistor R32A. A second terminal of the
resistor R32A may be coupled to a first terminal of a capacitor
C31, to a first terminal of a resistor R32 and to a first terminal
of a resistor R33. A second terminal of the second secondary
winding of the transformer T2 and a second terminal of the
capacitor C31 may be coupled to a ground node. Second terminals of
the resistors R32 and R33 may be coupled together. The supply
voltage VDC may be formed at a second terminals of the resistors
R32 and R33.
[0043] Thus, while the foregoing has been with reference to
particular embodiments of the invention, it will be appreciated by
those skilled in the art that changes in these embodiments may be
made without departing from the principles and spirit of the
invention, the scope of which is defined by the appended
claims.
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