U.S. patent application number 09/681273 was filed with the patent office on 2002-01-03 for infrared inductive light switch using triac trigger-control and early-charging-peak current limiter with adjustable power consumption.
Invention is credited to Li, Jian, Song, Qun, Xie, Fang.
Application Number | 20020000758 09/681273 |
Document ID | / |
Family ID | 4586205 |
Filed Date | 2002-01-03 |
United States Patent
Application |
20020000758 |
Kind Code |
A1 |
Song, Qun ; et al. |
January 3, 2002 |
Infrared inductive light switch using triac trigger-control and
early-charging-peak current limiter with adjustable power
consumption
Abstract
An electronic switch can replace a standard mechanical light
switch for 110-240 volt alternating-current (A.C.) devices. A triac
switches the A.C. current to an A.C. device such as a light. A
rectifier bridge generates a direct-current (D.C.) voltage that is
applied to a special current limiter. The special current limiter
generates a large current peak at low voltages, but limits current
at high voltages. The large current peak from the special current
limiter charges a capacitor when voltage is low at the beginning of
each A.C. half-cycle, before the triac turns on. The capacitor has
enough charge to supply D.C. current to an Infrared detector and
trigger control logic for the rest of the A.C. half-cycle. When the
detector detects a person nearby, it signals the trigger control
logic. The D.C. voltage from the rectifier bridge is filtered to
generate a sync pulse to the trigger control logic when adds a
phase delay to the sync pulse which triggers the triac.
Inventors: |
Song, Qun; (ShangHai,
CN) ; Li, Jian; (ShangHai, CN) ; Xie,
Fang; (ShangHai, CN) |
Correspondence
Address: |
STUART T AUVINEN
429 26TH AVENUE
SANTA CRUZ
CA
95062-5319
US
|
Family ID: |
4586205 |
Appl. No.: |
09/681273 |
Filed: |
March 12, 2001 |
Current U.S.
Class: |
307/116 |
Current CPC
Class: |
H05B 39/08 20130101;
Y02B 20/40 20130101; H05B 47/13 20200101; H05B 47/165 20200101 |
Class at
Publication: |
307/116 |
International
Class: |
H02B 001/24 |
Foreign Application Data
Date |
Code |
Application Number |
Jun 6, 2000 |
CN |
00116805.3 |
Claims
1. An electronic switch comprising: alternating-current (A.C.)
terminals for receiving alternating current for powering an A.C.
device; a rectifier, coupled to the A.C. terminals, for generating
a rectified D.C. voltage; a triggered current switch, coupled to at
least one of the A.C. terminals, for switching the alternating
current to the A.C. device; a coupler for coupling a trigger pulse
to the triggered current switch, the trigger pulse causing the
triggered current switch to switch the alternating current; a
current limiter, receiving the rectified D.C. voltage from the
rectifier, for generating a charging-current pulse for low voltages
of the rectified D.C. voltage, but limiting current at high
voltages above the low voltages; a charge store, receiving the
charging-current pulse from the current limiter, for storing
charge, the charge store outputting charge to an internal D.C.
supply when the current limiter limits current at the high
voltages; and D.C. logic, powered by the internal D.C. supply from
the charge store, the D.C. logic generating the trigger pulse
coupled to the triggered current switch, whereby the D.C. logic is
powered by the charge store that is charged by the charging-current
pulse for low voltages.
2. The electronic switch of claim 1 wherein the D.C. logic further
comprises: a detector, powered by the internal D.C. supply, for
generating a detect signal when the electronic switch is to switch
the alternating current to the A.C. device; trigger control logic,
powered by the internal D.C. supply, receiving the detect signal
from the detector and generating the trigger pulse.
3. The electronic switch of claim 2 wherein the trigger pulse is
synchronized to an A.C. cycle of the alternating current.
4. The electronic switch of claim 3 further comprising: a
synchronizing network, receiving the rectified D.C. voltage, for
generating a sync pulse to the trigger control logic, the sync
pulse being synchronized to the A.C. cycle of the alternating
current; the trigger control logic receiving the sync pulse from
the synchronizing network, the trigger control logic generating the
trigger pulse in response to the sync pulse when the detect signal
is activated by the detector.
5. The electronic switch of claim 4 wherein the trigger pulse has a
phase delay from the sync pulse, the phase delay determining a
conducting angle, the conducting angle being a portion of the A.C.
cycle wherein the A.C. device is powered, wherein larger phase
delays reduce overall power delivered to the A.C. device by
reducing the conducting angle.
6. The electronic switch of claim 5 wherein the conducting angle is
between 5.degree. and 175.degree., wherein each A.C. cycle contains
two half-cycles having 180.degree. each; wherein the A.C. terminals
receive an alternating voltage of 110 to 240 volts root-mean-square
(rms).
7. The electronic switch of claim 5 wherein the phase delay is
variable to reducing power to the A.C. device.
8. The electronic switch of claim 5 wherein the detector detects
infrared light, sound, motion, proximity, vibration, radio signals,
or presence of a person nearby.
9. The electronic switch of claim 5 wherein the current limiter
generates the charging-current pulse before the trigger pulse
activates the triggered current switch, the charging-current pulse
being terminated when the triggered current switch switches the
alternating current to the A.C. device; wherein when the detect
signal is not generated by the detector and the triggered current
switch is not triggered, the current limiter ends the
charging-current pulse in response to the rectified D.C. voltage
reaching a predetermined voltage.
10. The electronic switch of claim 9 wherein the current limiter
comprises: a first transistor, conducting a first current when the
rectified D.C. voltage is below the predetermined voltage, a first
resistor, limiting the first current from the first transistor; a
second transistor, conducting a second current when the rectified
D.C. voltage is above the predetermined voltage, a second resistor,
limiting the second current from the second transistor; wherein the
first resistor has a lower effective resistance than the second
resistor, the first current being a larger current than the second
current; wherein the charging-current pulse is generated by the
first current through the first transistor, while the second
current is limited by the second resistor.
11. The electronic switch of claim 10 wherein the second current is
less than a maximum first current at a peak of the charging-current
pulse for all rectified D.C. voltages above the predetermined
voltage.
12. The electronic switch of claim 11 wherein the current limiter
further comprises: a Zener diode, for conducting current to
activate the second transistor when the rectified D.C. voltage is
above the predetermined voltage, the Zener diode not conducting
sufficient current to activate the second transistor when the
rectified D.C. voltage is below the predetermined voltage, whereby
the Zener diode sets the predetermined voltage.
13. The electronic switch of claim 12 wherein the current limiter
comprises: a first path from the rectified D.C. voltage to the
charge store, the first path comprising the first transistor and
the first resistor in series; a second path from the rectified D.C.
voltage to the charge store, the second path comprising the second
transistor and the second resistor in series; wherein a voltage
generated in the second path controls activation of the first
transistor; a third path from the rectified D.C. voltage to the
charge store, the third path comprising the Zener diode and at
least one resistor in series; wherein a voltage generated in the
third path controls activation of the second transistor.
14. The electronic switch of claim 10 wherein the first and second
transistors are bipolar transistors activated by a base current
that flows when an activating voltage occurs or
metal-oxide-semiconductor (MOS) transistors activated by a gate
voltage.
15. The electronic switch of claim 9 wherein when the detect signal
is not generated by the detector and the triggered current switch
is not triggered, a second charging-current pulse is generated by
the current limiter when the rectified D.C. voltage falls back down
to the predetermined voltage after having risen above the
predetermined voltage, whereby two charging-current pulses are
generated when the detect signal is not generated.
16. The electronic switch of claim 1 5 wherein the A.C. cycle
comprises two half-cycles; wherein the charging-current pulse is
generated at a beginning of each of the two half-cycles for every
A.C. cycle, whereby the charge store is recharged by the
charging-current pulse at least twice for every A.C. cycle.
17. The electronic switch of claim 16 wherein the rectifier is a
single diode half-wave rectifier or a four-diode full-wave
rectifier; wherein the coupler is an opto-electronic coupler, a
capacitor, a transformer, or a direct-wired connection; wherein the
triggered current switch is a triac, a thyristor, or a
silicon-controlled rectifier; wherein the charge store is a shunt
capacitor and a shunt diode to a ground; wherein the synchronizing
network is a resistor or a resistor in series with a capacitor.
18. A switch comprising: terminals for receiving an
alternating-current (A.C.) voltage, the A.C. voltage being a power
source for the switch; rectifier means, receiving the A.C. voltage,
for generating a direct current (D.C.) voltage, the D.C. voltage
varying in cycle pulses synchronized to A.C. cycles of the A.C.
voltage, the cycle pulses including an initial region when the D.C.
voltage is less than a critical voltage, a middle region wherein
the D.C. voltage is above the critical voltage, and a final region
wherein the D.C. voltage is again below the critical voltage;
current-switch means, coupled to the terminals, for switching the
alternating-current voltage to selectively power an A.C. device in
response to a trigger signal; limiter means, receiving the D.C.
voltage from the rectifier means, for generating a high-current
peak during the initial region, but for limiting current to below
the high-current peak during the middle region; charge store means,
coupled to receive the high-current peak from the limiter means,
for storing charge and generating an internal D.C. supply voltage;
and D.C. means, powered by the internal D.C. supply voltage from
the charge store means, for generating the trigger signal to the
current-switch means, the trigger signal causing the current-switch
means to power the A.C. device, whereby the internal D.C. supply
voltage is generated from the A.C. voltage by charging the charge
store means during the initial region of the cycle pulses.
19. The switch of claim 18 wherein the D.C. means is only powered
by the charge store means, the switch not receiving any external
D.C. power.
20. The switch of claim 18 further comprising: sync means, coupled
to the D.C. voltage from the rectifier means, for generating sync
pulses to the D.C. means at a start of every cycle pulse; the D.C.
means comprising detect means for detecting when the A.C. device is
to be powered and trigger means, responsive to the detect means,
for generating the trigger signal at a start of each cycle pulse
when the detect means detects that the A.C. device be powered, the
trigger signal being generated after a phase delay relative to the
start of every cycle pulse, wherein when the detect means detects
that the A.C. device be powered, the A.C. device is powered for a
powered portion of every cycle pulse, but not powered for a start
portion of every cycle pulse before the powered portion, the start
portion being a portion including the phase delay; whereby the A.C.
device is pulsed on for the powered portion of the A.C. cycles but
off for the start portions.
21. An alternating-current (A.C.) switch comprising: A.C. terminals
for receiving an A.C. voltage having an A.C. cycle; a triac,
coupled between the A.C. terminals, for connecting the A.C.
terminals together to power an A.C. device in response to a trigger
input; a rectifier bridge, coupled across the A.C. terminals,
having a ground output and a rectified D.C. node with a rectified
voltage; a special current limiter, coupled to the rectified D.C.
node, having a first path that conducts a large peak current to an
internal D.C. supply when the rectified voltage is below a critical
voltage, and a second path that conducts a small current to the
internal D.C. supply when the rectified voltage is above the
critical voltage, the small current being less than the large peak
current; a shunt capacitor, coupled across the internal D.C. supply
and the ground, for storing charge from the large peak current; a
shunt diode, coupled across the internal D.C. supply and the
ground, for limiting a maximum voltage of the internal D.C. supply;
a detector, coupled between the internal D.C. supply and the
ground, for generating a detect signal indicating that the A.C.
device be powered; a sync signal, having sync pulses generated in
synchronization to the A.C. cycle; trigger control logic, coupled
between the internal D.C. supply and the ground, receiving the
detect signal and the sync signal, for generating a first pulse
when the detect signal is activated and a sync pulse is received;
and a coupler for coupling the first pulse to the trigger input of
the triac, whereby the triac is triggered on by the first pulse
generated by the trigger control logic powered by the shunt
capacitor charged by the special current limiter.
22. The A.C. switch of claim 21 wherein the special current limiter
comprises: the first path comprising a first transistor and a first
resistor in series that generate the large peak current; the second
path comprising a second resistor and a second transistor in series
that generate the small current and a first control voltage that
disables the first transistor when the second transistor is
enabled; a third path comprising at least one resistor and a Zener
diode that begins conducting when the critical voltage is reached,
the third path generating a second control voltage that causes the
second transistor to be enabled when the Zener diode begins
conducting.
23. The A.C. switch of claim 22 wherein the special current limiter
further comprises: a first interlocked transistor in series with at
least one resistor, for generating a third control voltage, coupled
to the second transistor, the third control voltage enabling the
second transistor; a second interlocked transistor, of an opposite
polarity type as the first interlocked transistor, coupled to
conduct current around the Zener diode when the first interlocked
transistor is enabled; wherein the first interlocked transistor is
controlled by the second control voltage, the first interlocked
transistor beginning to conduct when the Zener diode conducts as
the critical voltage is reached, but the first interlocked
transistor continuing to conduct after the Zener diode stops
conducting as the rectified voltage falls, whereby the interlocked
transistors prevent the first transistor from being re-enabled
after the Zener diode turns off.
24. The A.C. switch of claim 23 wherein the sync signal is
generated from the rectified voltage by a resistor and a capacitor;
wherein the coupler is an opto-electronic coupler, a capacitor, a
transformer, or a direct-wired connection; wherein the detector
detects infrared light, sound, motion, proximity, vibration, radio
signals, or presence of a person nearby.
Description
CROSS REFERENCE TO RELATED APPLICATIONS
[0001] This application claims priority to foreign application No.:
00116805.3 (China, P.R.) which has a filing Date of Jun. 6,
2001.
BACKGROUND OF INVENTION
[0002] This invention relates to electronic switches, and more
particularly to inductive light switches.
[0003] Mechanical light switches are commonly used in the home and
at the office. Such switches are often mounted in the wall near a
doorway, allowing a person to flip the switch to turn on the room
lights. Such mechanical switches may also control other electrical
appliances that are plugged into wall plugs or receptacles that are
controlled by the switch.
[0004] More recently, more advanced electronic switches have been
developed to replace such mechanical switches. The electronic
switch may include a motion sensor or infrared sensor to detect
when a person is moving in a room. Thus the room lights appear to
turn on automatically when a person enters a room. A timer may also
be used to turn off the lights after a period of time without
motion, such as in an office after 6 PM.
[0005] Such electronic switches can be used in a variety of
applications, not just for light switches. Switches designed for
switching standard 110-240 volt alternating-current (A.C.) lines
are desirable due to the widespread use of such standard power
lines inside buildings.
BRIEF DESCRIPTION OF DRAWINGS
[0006] FIG. 1 is a schematic of an optically-isolated A.C. power
switch using a current limiter to charge a shunt regulator that
powers low-voltage D.C. components.
[0007] FIG. 2A is a schematic highlighting the special current
limiter that limits current for high voltages.
[0008] FIG. 2B shows current waveforms for the special current
limiter.
[0009] FIGS. 3A-D are waveforms highlighting operation of the
trigger control logic.
[0010] FIGS. 4A-B are waveforms showing current and voltage
characteristics of the special current limiter.
[0011] FIGS. 5A-C are waveforms highlighting charging currents when
the triac turns on due to detection.
[0012] FIGS. 6A-B are I-V curves for the special current limiter
when larger and smaller resistance values are used for the
high-voltage resistors.
[0013] FIG. 7 is an alternate embodiment using a transformer for
A.C. isolation.
[0014] FIG. 8 is still another embodiment using a single diode
rectifier.
[0015] FIG. 9 is an embodiment using a low-power special current
limiter.
DETAILED DESCRIPTION
[0016] The present invention relates to an improvement in
electronic switches. The following description is presented to
enable one of ordinary skill in the art to make and use the
invention as provided in the context of a particular application
and its requirements. Various modifications to the preferred
embodiment will be apparent to those with skill in the art, and the
general principles defined herein may be applied to other
embodiments. Therefore, the present invention is not intended to be
limited to the particular embodiments shown and described, but is
to be accorded the widest scope consistent with the principles and
novel features herein disclosed.
[0017] FIG. 1 is a schematic of an optically-isolated A.C. power
switch using a current limiter to charge a shunt regulator that
powers low-voltage D.C. components. Standard A.C. power lines of
110-240 volts root-mean-square (rms) are coupled across terminals
AC1 and AC2. Load resistor 22 can be a light bulb in a light
controlled by the switch, or another electrical device such as a
radio, TV, or computer plugged into a power plug or receptacle. The
exact amount of load resistance produced by the light or electrical
device varies with the device. The switch connects terminals AC1
and AC3 when the switch is closed (activated or on), but
disconnects AC1 and AC3 when the switch is open (disconnected or
off). Terminals AC1 and AC3 could be connected to the black and
white wires on a standard home electrical cable in the U.S. that
carry the A.C. current.
[0018] The electrical device represented by load resistor 22 is
turned on when the switch triggers triac 20, switching on current
between terminals AC1 and AC3. Once triggered, triac 20 remains on
until the direction of the A.C. current reverses. The voltage
difference across A.C. terminals AC1 and AC3 drops to near zero
when triac 20 turns on.
[0019] A triggering current is generated by opto-electronic coupler
50 when current flowing through the light-emitting diode (LED)
input side of the opto-electronic coupler generates light that is
captured by the thyristor output side of opto-electronic coupler
50. The generated light activates the thyristor, causing current to
flow through. This current flows from terminal AC1 through limiting
resistor 32 and the thyristor side of opto-electronic coupler 50 to
the trigger terminal of triac 20, turning it on.
[0020] Opto-electronic coupler 50 isolates the higher-voltage A.C.
signals from the lower-voltage D.C. components in the switch. These
D.C. components could be damaged by the unfiltered A.C. signals.
However, coupling using light prevents various kinds of electrical
coupling into the D.C. components.
[0021] The A.C. power signal is converted into D.C. power using a
rectifier bridge of diodes 12, 14, 16, 18. When AC1 is a positive
voltage and AC3 is a negative voltage, current in the bridge flows
from AC1 through diode 14 to node V1, while current from ground
flows through diode 16 to AC3. During the other half of the A.C.
wave, AC1 is a negative voltage and AC3 is a positive voltage. Then
current in the bridge flows from AC3 through diode 18 to node V1,
while current from ground flows through diode 12 to AC1. Thus the
A.C. current from terminals AC1 and AC3 is converted to a D.C.
voltage on node V1 between diodes 14, 18, relative to the D.C.
ground between diodes 12, 16.
[0022] The voltage on node V1 varies with time, the maximum peak at
about the same peak voltage as the A.C. voltage amplitude, 155 to
338 volts. This is still a much higher voltage than the acceptable
voltage by many D.C. components such as integrated circuits, many
of which operate at 5 volts.
[0023] A special current limiter is formed by transistors 24, 26
and resistors 28, 30, 34, 36 and Zener diode 40. This special
current limiter provides a high current when the voltage on node V1
is low, but a low current when the voltage on node V1 is high. This
allows a high current to flow from node V1 to node V2 during the
parts of the A.C. cycle when the instant voltage is low, but little
current flows to node V2 during high instant voltage portions of
the A.C. cycle.
[0024] Shunt capacitor 48 is a charge store that is charged by the
high current through the special current limiter during the
low-voltage regions of the A.C. cycle, near the crossover
(0-voltage) part of the A.C. cycle or sine wave. During the peaks
and troughs of the A.C. cycle, when the absolute voltage is large,
the special current limiter provides little current to shunt
capacitor 48. Instead, shunt capacitor 48 provides charge or
current to D.C. components such as detector 60 and trigger control
logic 62. Shunt capacitor 48 provides enough charge over the
remainder of the A.C. cycle to power these D.C. components. Thus
shunt capacitor 48 acts as a D.C. power source, driving the
power-supply VD inputs to detector 60 and trigger control logic 62.
Shunt capacitor 48 has a sufficiently large capacitance value to
power the D.C. components by compensating for charge drawn by the
D.C. components from node V2.
[0025] Shunt Zener diode 42 acts to regulate the voltage on node
V2. When the voltage on node V2 rises above the reverse-breakdown
or trigger voltage of the Zener diode, reverse conduction occurs,
shunting current to the D.C. ground. Once the voltage on node V2
falls back below the trigger voltage, shunt Zener diode 42 turns
off again. Together, shunt capacitor 48 and shunt Zener diode 42
act as a shunt regulator, regulating the internal D.C. power-supply
voltage VD on node V2.
[0026] Resistor 38 and capacitor 44 form a synchronizing or
synchronous-signal-sampling network, sampling the rectified
waveform on node V1. A sync signal is generated each time the
voltage on node V1 falls back to zero, which occurs twice for each
A.C. cycle, at the crossovers. This sync signal is input to the
sync input of trigger control logic 62.
[0027] When infrared detector 60 senses a person nearby, it
activates its detect-signal output OUT, which is the IN input to
trigger control logic 62. Trigger control logic 62 then outputs a
delayed pulse after the sync pulse is received when the IN input is
activated by the detector 60 sensing a person nearby. The pulses
output by trigger control logic 62 activate the LED in
opto-electronic coupler 50, activating the thyristor side, which
generates the trigger current to triac 20, turning on the A.C.
switch.
[0028] Since the sync pulses are generated by resistor 38 and
capacitor 44 for each A.C. half-cycle, opto-electronic coupler 50
is pulsed on at the start of each half-cycle when detector 60
detects a person nearby. Thus pulsing re-triggers triac 20, turning
it on again for each of the two half-cycles for each A.C.
period.
[0029] Special Current Limiter Produces High Current for Low
Voltages
[0030] FIG. 2A is a schematic highlighting the special current
limiter that limits current for high voltages. There are three
primary paths through the special current limiter: a high-current
path through transistor 24 and resistor 28, a low-current current
path through resistor 30 and transistor 26, and a control path
through Zener diode 40 and resistors 34, 36. The paths are
connected together by activating voltages that control transistors
24, 26. These activating voltages are typically applied to the
bases of bipolar transistors, but can also be applied to the gates
of MOS transistors.
[0031] Zener diode 40 has a breakdown voltage VZ that is usually
chosen to be a suitable value. When the rectified voltage V1 is
low, VA is below VZ, then Zener diode 40 is off and only leakage
current flows. The lack of current flow through Zener diode 40
prevents current flow through resistor 34, causing no base-emitter
current to flow through transistor 26. Transistor 26 is off, in the
cut-off region of operation with little or no collector-to emitter
current flow. Thus most or all of the current through resistor 30
is diverted into the base of transistor 24, causing the
base-emitter junction to become forward biased. This turns on
transistor 24, allowing a large collector current to flow.
Transistor 24 then typically operates in the saturated region. This
collector current and the smaller base current flow from the
emitter of transistor 24 through resistor 28.
[0032] Thus for voltages VA across the special current limiter that
are below VZ, current IA through the special current limiter flows
mostly through transistor 24 and resistor 28. This current begins
to flow at a VA of about 0.6 volt, when the base-emitter junction
of transistor 24 is turned on.
[0033] Once the voltage VA across the special current limiter
exceeds VZ, Zener diode 40 turns on, and current flows from node V1
through Zener diode 40 and resistor 34. Some of this current flows
through resistor 36 and the rest of the current flows into the base
of transistor 26. Once the voltage across resistor 36 reaches the
junction turn-on voltage of about 0.6 volt, the base current into
transistor 26 turns it on. The base current through transistor 26
increases until transistor 26 becomes saturated.
[0034] Once transistor 26 turns on, the current through resistor 30
is sent through the collector of transistor 26, reducing the
current through the base of transistor 24. The voltage drop across
resistor 28 reduces the base-emitter voltage of transistor 24
relative to that of transistor 26. Eventually transistor 24 turns
off, while transistor 26 remains on. Most of the IA current then
flows through resistor 30 and transistor 26, rather than through
transistor 24 and resistor 28.
[0035] The values of resistors 30, 34 are typically much larger
than the resistance of resistor 28. This causes the current flow
through transistor 24 to be much larger than the current through
transistor 26. Since transistor 24 is on for lower voltages below
VZ, while transistor 26 is on for higher voltages above VZ, the
total current IA is large for voltages below VZ, but small for high
voltages.
[0036] FIG. 2B shows current waveforms for the special current
limiter. The total current IA through the special current limiter
initially rises as the current flows through transistor 24. Since
this current is limited by resistor 28, the slope of the curve from
about the origin to near point 100 is the resistance of resistor 28
and rises sharply due to the relatively low resistance of resistor
28.
[0037] As the Zener breakdown voltage VZ is reached at point 100,
Zener diode 40 turns on, sending current into the base of
transistor 26. Transistor 26 turns on, depriving transistor 24 of
its base current. Transistor 24 shuts off. Now the current flows
mostly through resistors 30, 34, which have relatively large
resistances. The relatively larger resistance of resistors 30, 34
compared to resistor 28 causes a lower current to flow through the
special current limiter. Thus the current drops rapidly near
voltage VZ from point 100, when transistor 24 and resistor 28
generate most of current IA, to point 102, when transistor 26 and
resistors 30, 34 conduct most of the IA current.
[0038] From point 102 to point 104, the current is limited by
resistors 30, 34, which have a high resistance. The slope of the
curve from about the point 102 to 104 is the equivalent resistance
of resistors 30, 34 and transistor 26. The high equivalent
resistance causes the current curve to rise quite gradually to
point 104. Of course, the actual slopes will vary with the
resistance values the designer chooses.
[0039] Since the transistors require a voltage of about 0.6 volt to
turn on the base-emitter junctions, the current may be limited to
leakage currents when VA is below half a volt. Thus the curve may
actually not pass through the origin as shown, and the current
curve may not be linear near the origin. An idealized curve is
shown.
[0040] Leakage resistor 36 is used to eliminate leakage current
from Zener diode 40 before it breaks down at voltage VZ. The
resistance value of leakage resistor 36 is chosen so that the I-R
voltage drop across leakage resistor 36 for the expected leakage
current through Zener diode 40 is less than 0.6 volt. This keeps
the base-emitter junction of transistor 26 from inadvertently
turning on due to Zener leakage below breakdown voltage VZ.
[0041] Thus the special current limiter uses active
components--transistors--to generate large currents at low
voltages, but small currents at high voltages. This is the opposite
behavior of simple resistor-based current limiters. The special
current limiter provides a high current at low voltages to charge
the shunt capacitor, but limits current at high voltage to prevent
damage to D.C. components. Thus the special current limiter,
together with the Zener and capacitor shunts, is ideal for
generating an internal D.C. voltage supply.
[0042] FIGS. 3A-D are waveforms highlighting operation of the
trigger control logic.
[0043] Trigger control logic 62 of FIG. 1 has two inputs: an IN
input from infrared detector 60 and a SYNC input. Trigger control
logic 62 generates a trigger output OUT2 that causes re-triggering
of triac 20. Trigger control logic 62 also has a ground input and a
power (VD) input from the internal power supply (node V2).
[0044] FIG. 3A shows the rectified voltage waveform at node V1,
after the diode bridge rectifier but before the special current
limiter. A sync signal SYNC is generated by resistor 38 and
capacitor 44 that form the synchronous signal sampling network. The
rectified waveform on node V1 (FIG. 3A) is filtered to generate the
SYNC input of FIG. 3B. A sync signal is generated each time the
voltage on node V1 falls back to zero, which occurs twice for each
A.C. cycle, at the crossovers. This sync signal is input to the
sync input of trigger control logic 62. The actual waveform may be
less ideal and more rounded in shape, depending on the actual R and
C values chosen for resistor 38 and capacitor 44. The sync signal
and waveforms at node V1 falls sharply from high to low level when
OUT2 is active.
[0045] FIG. 3C shows the IN input from the infrared detector. At
about the middle of the time period shown in FIG. 3C, a person
walks into the detection range or area of infrared detector 60.
Infrared detector 60 drives its output high to indicate the
detected presence of a person in the area.
[0046] When trigger control logic 62 receives the high IN signal
from infrared detector 60, it pulses its output OUT2 as shown in
FIG. 3D. These pulses are optically coupled to the power triac's
trigger input. Since the pulses occur slightly after the
zero-voltage points of the A.C. waveform, the pulses re-trigger and
re-enable the triac after the triac turns off at zero A.C. volts.
This re-triggering occurs when detection occurs, but not when
detection is not signaled by infrared detector 60.
[0047] Trigger control logic 62 can be implemented with logic
gates. Additional buffers can be added to generate the desired
delay Td, or an R-C delay can be added to achieve the desired
Td.
[0048] Of course, many other alternatives are possible, such as
inverting signals at various points. Low-going pulses can be used,
such as an active-low rather than an active-high input from the
detector. Pulses could be output from the detector at a variety of
frequencies rather than a stable level. The level could vary in
voltage somewhat, such as due to a less-than-ideal internal D.C.
voltage VD.
[0049] Thus a re-triggering signal is generated for the triac at a
frequency of double the A.C. frequency when detection occurs. No
trigger pulses are generated when no detection occurs. These
trigger pulses cause the triac to remain on for much of the A.C.
cycle, allowing current to flow through the device represented by
load resistor 22 of FIG. 1.
[0050] Phase Delay Affects A.C. Power Switched
[0051] The phase delay Td of the OUT2 re-triggering signal has
profound implications for the overall operation of the switch. The
phase delay is typically set to between 5.degree. (degrees) and
175.degree., where 180.degree. is the width of the A.C. pulse in
FIG. 3A, or half of the A.C. cycle or period. This phase delay
determines the conductive angle of the triac, or the percentage or
fraction of the A.C. cycle that triac 20 is turned on. This
conductive angle is the amount of time that A.C. current is
switched on to the device being switched by the switch circuit.
Keeping the conductive angle large and the phase delay Td small
maximized the A.C. current and power delivered to the device being
switched.
[0052] For example, when the phase delay Td is 5.degree., then the
conductive angle is 175.degree., and the triac remains on for
175/180 of the A.C. cycle. Less power is delivered when the phase
delay is increased to 30.degree., since the conductive angle is
reduced to 150.degree.. Then the triac remains on for only 150/180
of the cycle. Power could be reduced further when the phase delay
is increased to 120.degree., since the conductive angle is then cut
to 60.degree., with the triac delivering power only for 60/180, or
one-third of the cycle.
[0053] The power being delivered can be reduced by increasing the
delay Td. A programmable or user-variable delay could be introduced
by the trigger control logic. The user could rotate a dial, and the
dial position could be translated to a programmable value by any
one of a variety of circuits. The programmable value could then be
fed to trigger control logic 62, and the delay Td adjusted
according to the new programmable value. The new Td then would
produce a different conductive angle, and a different power is
delivered by the triac. For example, a light could be dimmed by
increasing Td in such a manner.
[0054] Phase Delay May Affect D.C. Voltage
[0055] The phase delay does have a practical lower limit. When the
phase delay is too small, the internal D.C. supply voltage at node
V2 can drop or become unstable. When the triac is turned on,
current is drawn away from the rectifier diode bridge and the
special current limiter, maybe preventing the full charging of
shunt capacitor 48. The unstable or insufficient internal D.C.
voltage VD may then cause infrared detector 60 and trigger control
logic 62 to operate improperly. However, phase delays as low as
5.degree. are possible.
[0056] FIGS. 4A-B are waveforms showing current and voltage
characteristics of the special current limiter. In FIG. 4A, the V1
voltage input to the special current limiter is shown. For 110-240
volt A.C., the peak voltages after the diode bridge, at node V1,
are about 155-338 volts. Shunt Zener diode 42 on node V2 has a
small breakdown voltage, such as 3 to 5 volts, which is much
smaller than the peak voltage on node V1. Thus the current through
the special current limiter is determined mostly by its own I-V
characteristics.
[0057] The I-V curve shown in FIG. 2B is replicated for each peak
and mirrored for the quarter-cycles that the voltage V1 is
decreasing. Thus FIG. 4B shows many peaks when the voltage V1 is
less that the VZ breakdown voltage of Zener diode 40 in the special
current limiter. When the voltage V1 in FIG. 4A rises above VZ,
current I1 is limited, producing the slightly-sloped regions
between current peaks that coincide with the voltage peaks.
[0058] The shunt capacitor 48 is charged during the current peaks
of FIG. 4B, when the voltage V1 is below VZ. One current peak
occurs as V1 is rising from zero, and another current peak occurs
as V1 falls back to zero, for a total of two charging-current peaks
per half-cycle, or four current peaks for each A.C. cycle.
[0059] The maximum voltage V2 on shunt capacitor 48 is limited to
3-5 volts by shunt diode 42. During the remainder of the cycle,
when the special current limiter reduces the current, shunt
capacitor 48 delivers charge to the infrared detector and trigger
control logic's power-supply input (VD). As long as the capacitance
value of shunt capacitor 48 is sufficiently large, enough current
is delivered during each half-cycle to power the infrared detector
and trigger control logic.
[0060] Capacitor Charging Stopped When Triac Turns On --FIG. 5
[0061] The current waveform of FIG. 4B applies when no person is
detected, and triac 20 is off. When detection occurs and triac 20
turns on, the diode rectifier is robbed of current by triac 20, and
the voltage on node V1 falls to ground. FIGS. 5A-C are waveforms
highlighting charging currents when the triac turns on due to
detection.
[0062] FIG. 5A is a waveform showing that the rectified voltage V1
is cut off when the triac is turned on. When no person is detected,
the triac remains off, and node V1 has the rectified voltage
waveform shown by the dotted lines. However, when the triac is
enabled by the OUT2 trigger pulses of FIG. 5C from the trigger
control logic, the voltage across the diode rectifier bridge falls
below the junction turn-on voltage of about 0.7 volt required for
diodes 12, 14, 16, 18 to conduct current. Thus the diode bridge
turns off when triac 20 turns on. The result is that the rectified
voltage on node V1 falls to ground after the trigger pulses on OUT2
turn on the triac for each half-cycle. Voltage V1 pulses high for
just a short period at the beginning of each half-cycle.
[0063] However, the special current limiter is designed to deliver
high current for low voltages. The low voltages on node V1 occur at
the beginning of the half-cycle. Thus charging-current peaks still
occur before the triac is enabled, as shown in FIG. 5B. For very
short phase delays, these current peaks may be cut short, limiting
the charging current to shunt capacitor 48. However, a phase delay
of as little as 5.degree. should produce a sufficiently large
current peak to charge shunt capacitor 48 with enough charge to
supply the detector and trigger control logic for the remainder of
the half-cycle. As long as the voltage on node V1 reaches breakdown
voltage VZ before the triac turns on, the full charging-current
peak is generated. Even without a full charging-current peak, shunt
capacitor 48 may be sufficiently charged for proper operation.
[0064] Note that FIG. 5B has only one charging-current peak for
each half cycle, while FIG. 4B has two charging-current peaks per
half-cycle. When detection occurs and the triac turns on, the triac
remains on until the A.C. voltage reaches zero. Thus current peak
that occurs in FIG. 4B for low voltages as V1 falls does not occur
in FIG. 5B because the triac is still on.
[0065] The special current limiter produces an initial burst of
charge at the beginning of each A.C. half-cycle. This initial
current burst quickly charges the shunt capacitor before the triac
steals the current from the diode bridge. Thus the internal D.C.
supply is powered from the initial part of each half-cycle,
corresponding to the phase delay, while the device switched by the
triac is powered by the remainder of the half-cycle, corresponding
to the conducting angle.
[0066] Power Adjustable by Resistors in Special Current
Limiter--FIG. 6
[0067] The power consumed by the switch circuit is determined to
some extent by the special current limiter. The values of resistors
30, 34 determine the current through the special current limiter
for high voltages, above VZ. Since the shunt capacitor is
sufficiently charged by low voltages, the current delivered during
high voltage periods is basically wasted. Power consumption of the
switch can be reduced by using higher resistance values for
resistors 30, 34 in the special current limiter.
[0068] FIG. 6A is an I-V curve for the special current limiter when
larger resistance values are used for the high-voltage resistors.
The initial peak 100 provides most of the charging current for the
shunt capacitor. Once voltage VZ is reached, current drops to
trough 102. Then current is determined primarily by resistors 30,
34. The slope of the I-V curve from trough 102 to point 104 is
determined by the resistances of resistors 30, 34.
[0069] In FIG. 6B, lower resistance values are used for resistors
30, 34. These lower resistances allow more current to flow through
the special current limiter for high voltages. The higher trough
102 and point 104 result from the higher currents. This current is
wasted current, since the shunt capacitor was already charged by
initial peak 100. Thus the curve in FIG. 6A is better than the
curve in FIG. 6B since less current is wasted.
[0070] Transformer Isolation-- FIG. 7
[0071] FIG. 7 is an alternative embodiment using a transformer for
A.C. isolation.
[0072] The switch circuit in FIG. 7 operates in much the same way
as described for the circuit of FIG. 1. Rather than use
opto-electronic coupler 50, transformer 54 provides isolation
between the A.C. and D.C. sections. Trigger control logic 62
generates a pulse output as described before, and this output OUT2
is applied to one set of windings of transformer 54. The pulse on
OUT2 is inductively coupled to the second set of windings of
transformer 54, generating a pulse that is applied to the trigger
input of triac 20. Limiting resistor 32 is also deleted. Note that
limiting resistor 32 could also be deleted from FIG. 1 if a
sufficient internal resistance in opto-electronic coupler 50 is
provided.
[0073] Although transformer 54 does not provide as much isolation
as opto-electronic coupler 50, a sufficient amount of isolation is
obtained for some applications.
[0074] Another alternative shown in FIG. 7 is that capacitor 44
from the synchronous signal sampling network is also deleted.
Resistor 38 couples the rectified waveform to the SYNC input of
trigger control logic 62. Although the shape of the SYNC waveform
is less ideal without capacitor 44, the SYNC waveform may still
operate properly, depending on the characteristics of trigger
control logic 62. This alternative may also be applied to other
embodiments.
[0075] FIG. 8 is still another embodiment using a single diode
rectifier. The four-diode bridge of diodes 12, 14, 16, 18 of FIG. 1
is replaced with single diode 56, which acts as a diode rectifier.
Terminal AC1 acts as the D.C. ground. Since only one diode is used,
only half-wave rectification is obtained at node V1. This reduces
the number of low-voltage charging-current peaks to two per A.C.
cycle.
[0076] The SYNC input uses resistor 38 without a capacitor as the
synchronous signal sampling network. The SYNC signal is generated
only once per A.C. cycle since resistor 38 takes its input from AC3
rather than a fully-rectified bridge. To compensate, trigger
control logic 62 can trigger on both the rising and falling edges
of the SYNC pulse.
[0077] The pulsed output OUT2 from trigger control logic 62 is
directly coupled to the trigger input of triac 58, with no
isolation, a direct-wired connection.
[0078] Low-Power Special Current Limiter--FIG. 9
[0079] FIG. 9 is an embodiment using a low-power special current
limiter. This embodiment is shown using opto-electronic coupler 50
and a full-wave rectifier bridge of diodes 12, 14, 16, 18, but the
alternative transformer or direct coupling could be substituted, as
could the single-diode half-wave rectifier.
[0080] The special current limiter delivers a larger
charging-current peak at low voltages, charging shunt capacitor 48,
which then supplies charge during the rest of the A.C. cycle when
the special current limiter reduces current at higher voltages.
Thus shunt capacitor 48 acts as a D.C. supply to detector 60' and
trigger control logic 62. Shunt Zener diode 42 prevents the
internal D.C. supply voltage VD from rising too high, preventing
damage to detector 60' and trigger control logic 62.
[0081] A more complex but lower power special current limiter is
shown. It uses two additional transistors 70, 78, which reduce the
power consumption when triac 20 is off.
[0082] For low voltages below VZ, current flows through transistor
24, which receives a current into its base from resistor 30.
Transistor 26 is shut off, since it does not receive any
significant base current, as such current is blocked by transistor
70. Transistor 70 is also shut off, since Zener diode 40 has not
yet broken down. Only a small leakage current flows through Zener
diode 40. This leakage current flows through resistors 34, 36.
However, the resistance value of resistor 36 is low enough that an
I-R drop of less than 0.6 volt is produced for the leakage current
from Zener diode 40. Thus the base-emitter junction of transistor
70 is not turned on by the leakage current. Since transistor 70 is
off, transistor 78 is also shut off, since no significant current
flows through resistors 76, 74. Thus transistor 78 is deprived of
base-emitter current.
[0083] Note that in this embodiment transistor 78 is a PNP
transistor, with the emitter at node V1, while transistors 70, 24,
26 are NPN transistors. NPN transistors 70, 24, 26 turn on when the
base is about 0.6 volt above the emitter junction, when standard
bipolar transistors are used. However, PNP transistor 78 turns on
when the opposite polarity bias is applied --when the base junction
is about 0.6 volt below its emitter. More exotic kinds of
transistors can be substituted that have turn-on voltages other
than 0.6 volt.
[0084] As the voltage on node V1 rises above VZ, and the voltage
across Zener diode 40 rises above its breakdown voltage, Zener
diode 40 breaks down and begins reverse conduction. A large current
flows through Zener diode 40 and resistors 34, 36. Some of this
current flows into the base of transistor 70, turning on its
base-emitter junction. A collector current begins to flow, from
resistors 76, 74, through transistor 70 to resistor 72. While the
collector current is normally larger than the base current by a
factor of perhaps 100, transistor 70 quickly becomes saturated,
limiting the collector current. Other transistors 26, 78 may
likewise operate mostly in the saturated region.
[0085] As transistor 70 turns on, current flows through resistor
72, creating an I-R voltage drop across it. The base-emitter
junction of transistor 26 turns on, and base current flows through
transistor 26, turning on its collector current from resistor 30.
This collector current robs current from transistor 24, and
transistor 24 turns off.
[0086] Since resistor 28 is designed to have a lower resistance
than the equivalent resistance through resistors 30, 72, 74, 76,
34, 36, the current delivered by the special current limiter drops
as V1 rises above VZ. Thus the initial current peak ends as VZ is
reached. Also, if detector 60' signals detection, causing trigger
control logic 62 to turn on triac 20, bridge diodes 12, 14, 16, 18
then turn off, and voltage V1 falls, ending the current pulse. Of
course, triac 20 does not turn on until after the SYNC pulse is
received by trigger control logic 62, and after phase delay Td has
elapsed. The phase delay is usually designed so that a sufficiently
long charging peak has already occurred before triac 20 is turned
on.
[0087] In the simpler special current limiter of FIG. 1, when
detection occurs and voltage V1 drops back to zero, transistor 24
can not turn on again as Zener diode 40 turns off as V1 falls back
below VZ. When no detection occurs, a second current peak occurs
for each half-cycle V1 pulse as V1 falls back to zero. When
transistor 24 turns on again, a larger current again flows. This
larger current is undesirable as it consumes power.
[0088] In the lower-power special current limiter of FIG. 9,
transistors 70, 78 act as a thyristor, being interlocked to each
other as back-to-back PNP and NPN transistors. Once transistor 70
turns on, current flowing through resistor 76 develops an I-R
voltage drop of at least 0.6 volt across it. Thus the base of
transistor 78 is 0.6 volt below its emitter, and the emitter-base
junction of this PNP transistor turns on. Current can then flow
through the collector of transistor 78.
[0089] When voltage V1 drops below VZ, Zener diode 40 turns off.
However, transistor 78 is still on, and it conducts current around
Zener diode 40, continuing to supply current through resistor 34
into the base of transistor 70. Since transistor 70 remains on,
base current still flows through resistor 74 and transistor 78,
keeping transistor 78 on. Thus both interlocked transistors 70, 78
remain on, despite Zener diode 40 turning off. Since transistor 70
remains on, transistor 26 also remains on, keeping transistor 24
off.
[0090] Keeping transistor 24 off ensures that the large current
through low-resistance resistor 28 does not occur, unlike the
simpler special current limiter of FIG. 1. Thus the second charging
peak is avoided as voltage V1 falls back to ground, either due to
detection or due to the end of the VI half-cycle pulse. Once V1
nears ground, interlocked transistors 70, 78 turn off, and the low
power special current limiter is reset for the next half-wave of
V1.
[0091] With the elimination of the second charging-current peak for
falling V1 voltages, power consumption through the low power
special current limiter is reduced. Since shunt capacitor 48 is
already sufficiently charged by the initial charging peak, shunt
Zener diode 42 normally sinks this extra current to ground, saving
power compared with the simpler special current limiter of FIG. 1.
Thus power consumption is reduced.
[0092] Interlocked transistors 70, 78 could be replaced with a
triac, silicon-controlled-rectifier (SCR), thyristor, or other kind
of triggering device. Some of the resistor may also be
replaced.
[0093] In this embodiment shown in FIG. 9, detector 60' can be any
detector, such as the previously-described infrared detector, or a
motion detector, sound detector, vibration detector, pressure,
temperature, radio signal, or smoke detector, or other kinds of
detectors. Such alternative detectors can be used in the other
embodiments as well. Many types of commercially-available detectors
may be used. Often additional inputs or outputs are available for
these detectors, and some of these additional inputs or outputs may
be ignored or connected to fixed voltages or terminated with
resistors. Additional interface logic may be needed for some
alternative detectors, and trigger control logic 62 can be modified
to interface with different signal specifications and timings.
ALTERNATE EMBODIMENTS
[0094] Several other embodiments are contemplated by the inventors.
For example other special current limiters can be substituted.
Other kinds of transistors can be used, such as Darlington
transistors, Gallium-Arsenide transistors, or complementary
metal-oxide-semiconductor (CMOS) transistors, VMOS transistors, or
VDMOS transistors. Some MOS transistors are particularly
contemplated, since they can easily be integrated with other
components, such as the trigger control logic.
[0095] Rather than using the Zener diode to detect voltage VZ, a
resistor chain could be used as a voltage divider, producing a test
voltage. Once the test voltage rises above a threshold, a trigger
could be activated that switched from a high-current-delivering
mode to a low-current mode. A mux could be used. A zero-current
mode could be used rather than a low-current mode. Many other
circuit arrangements and networks can be used, and passive
components such as resistors and capacitors can be added or removed
from the circuit. Additional triacs or triggered current switches
can be used to cut off A.C. current at more than one terminal, or
in multiple loops, and for multiple A.C. devices. Rather than
switching all of the current to the A.C. device, the current may be
reduced by the switch such as for dimming lights. A non-triggered
current switch could be used in place of the triac. The trigger
pulse could trigger a flip-flop of latch, which then drives a stead
signal to control the non-triggered current switch.
[0096] The Infrared detector can be replaced by other kinds of
detectors, such as motion detectors, microwave detectors, light
detectors of other frequencies than infrared, sound, vibration,
proximity, or other detectors. The triac could be replaced with a
silicon-controlled-rectifie- r (SCR), thyristor, or other kind of
triggering device, and the bridge diodes could themselves be
replaced by other kinds of rectifiers. Many types of coupling of
the triac trigger can be used, such as other kinds of
opto-electronic or optical couplers, inductive couplers such as
coils and transformers, capacitive couplers, or even direct
coupling.
[0097] The conductive angle has been described in an idealized form
where the phase delay is 180 minus the conductive angle. Other
delays may cause the actual conductive time or angle to decrease
from the ideal. For example, the triac, opto-coupler, or device
being switched may require time to turn on and off. It is
understood that these various parasitic delays are secondary
effects and in a first-order analysis the switch operation can be
described by ignoring such secondary effects. The breakdown voltage
VZ is also somewhat idealized, since the predetermined voltage
across the special current limiter also includes voltage drops
through resistors and a transistor in series with the Zener diode
that is breaking down.
[0098] The abstract of the disclosure is provided to comply with
the rules requiring an abstract which will allow a searcher to
quickly ascertain the subject matter of the technical disclosure of
any patent issued from this disclosure. It is submitted with the
understanding that it will not be used to interpret or limit the
scope or meaning of the claims. 37 C.F.R. .sctn. 1.72(b). Any
advantages and benefits described may not apply to all embodiments
of the invention. When the word "means" is recited in a claim
element, Applicant intends for the claim element to fall under 35
USC .sctn. 112, paragraph 6. Often a label of one or more words
precedes the word "means". The word or words proceeding the word
"means" is a label intended to ease referencing of claims elements
and is not intended to convey a structural limitation. Such
means-plus-function claims are intended to cover not only the
structures described herein for performing the function and their
structural equivalents, but also equivalent structures. For
example, although a nail and a screw have different structures,
they are equivalent structures since they both perform the function
of fastening. Claims that do not use the word means are not
intended to fall under 35 USC .sctn. 112, paragraph 6. Signals are
typically electronic signals, but may be optical signals such as
can be carried over a fiber optic line. Low and high voltages may
be absolute values of voltages, depending on what is considered to
be the ground voltage reference.
[0099] The foregoing description of the embodiments of the
invention has been presented for the purposes of illustration and
description. It is not intended to be exhaustive or to limit the
invention to the precise form disclosed. Many modifications and
variations are possible in light of the above teaching. It is
intended that the scope of the invention be limited not by this
detailed description, but rather by the claims appended hereto.
* * * * *