U.S. patent number 9,755,323 [Application Number 14/872,444] was granted by the patent office on 2017-09-05 for antenna apparatus.
This patent grant is currently assigned to FUJITSU LIMITED. The grantee listed for this patent is FUJITSU LIMITED. Invention is credited to Kazumi Kasai, Zhengyi Li, Yoji Ohashi.
United States Patent |
9,755,323 |
Li , et al. |
September 5, 2017 |
Antenna apparatus
Abstract
An antenna apparatus includes N (2=<N) transmitting antennas
configured to transmit RF signals having Orbital Angular Momentum
(OAM) of designated modes, and N receiving antennas configured to
make N pairs with the N transmitting antennas, respectively, and to
receive the RF signals having OAM of the designated modes
transmitted from the corresponding N transmitting antennas within
the N pairs.
Inventors: |
Li; Zhengyi (Shinagawa,
JP), Ohashi; Yoji (Fucyu, JP), Kasai;
Kazumi (Shibuya, JP) |
Applicant: |
Name |
City |
State |
Country |
Type |
FUJITSU LIMITED |
Kawasaki-shi, Kanagawa |
N/A |
JP |
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Assignee: |
FUJITSU LIMITED (Kawasaki,
JP)
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Family
ID: |
52021787 |
Appl.
No.: |
14/872,444 |
Filed: |
October 1, 2015 |
Prior Publication Data
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Document
Identifier |
Publication Date |
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US 20160028163 A1 |
Jan 28, 2016 |
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Related U.S. Patent Documents
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Application
Number |
Filing Date |
Patent Number |
Issue Date |
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PCT/JP2013/066115 |
Jun 11, 2013 |
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Current U.S.
Class: |
1/1 |
Current CPC
Class: |
H01Q
21/00 (20130101); H01Q 19/17 (20130101); H01Q
21/29 (20130101); H01Q 15/166 (20130101); H01Q
25/007 (20130101); H01Q 21/28 (20130101); H01Q
15/167 (20130101); H04L 47/82 (20130101) |
Current International
Class: |
H01Q
21/00 (20060101); H01Q 21/28 (20060101); H01Q
19/17 (20060101); H01Q 15/16 (20060101); H01Q
25/00 (20060101); H01Q 21/29 (20060101); H04L
12/911 (20130101) |
Field of
Search: |
;343/702,700MS,836,893 |
References Cited
[Referenced By]
U.S. Patent Documents
Foreign Patent Documents
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2004-517549 |
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Jun 2004 |
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JP |
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2009-033747 |
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Feb 2009 |
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JP |
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02/054626 |
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Jul 2002 |
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WO |
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2005069443 |
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Jul 2005 |
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WO |
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2008059985 |
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May 2008 |
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WO |
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2009017230 |
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Feb 2009 |
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WO |
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2010026233 |
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Mar 2010 |
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WO |
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Other References
Colin Sheldon et al., "A 60GHz Line-of-Sight 2.times.2 MIMO Link
Operating at 1 .2Gbps", Antennas and Propagation Society
International Symposium, AP-S 2008. IEEE, Jul. 5, 2008, pp. 1-4 (4
pages). cited by applicant .
Tzvika Naveh, "Mobile Backhaul: Fiber vs. Microwave", Case Study
Analyzing Various Backhaul Technology Strategies, Oct. 2009, pp.
1-11 (11 pages). cited by applicant .
Jian Wang et al., "Terabit free-space data transmission employing
orbital angular momentum multiplexing", Nature Photonics, vol. 6,
Jul. 2012, pp. 488-496 (9 pages). cited by applicant .
International Search Report and Written Opinion of the
International Searching Authority (Form PCT/ISA/210, Form
PCT/ISA/237), mailed in connection with PCT/JP2013/066115 and
mailed Sep. 10, 2013 (7 pages). cited by applicant.
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Primary Examiner: Han; Jessica
Assistant Examiner: Tran; Hai
Attorney, Agent or Firm: Fujitsu Patent Center
Parent Case Text
CROSS-REFERENCE TO RELATED APPLICATION
This application is a continuation application of International
Application PCT/JP2013/066115 filed on Jun. 11, 2013 and designated
the U.S., the entire contents of which are incorporated herein by
reference.
Claims
What is claimed is:
1. An antenna apparatus comprising: N (2=<N) transmitting
antennas configured to transmit RF signals having Orbital Angular
Momentum (OAM) of designated modes; and N receiving antennas
configured to make N pairs with the N transmitting antennas,
respectively, and to receive the RF signals having OAM of the
designated modes transmitted from the corresponding N transmitting
antennas within the N pairs, wherein the transmitting antennas
include output parts that output the RF signals and first
transmitting filters that realize spiral shapes of one cycle of the
RF signals by giving delays to the RF signals output from the
output parts, and wherein the receiving antennas include second
filters that realize inverted spiral shapes of one cycle of the RF
signals and receiving parts that receive the RF signals transmitted
through the second filters.
2. The antenna apparatus as claimed in claim 1, wherein, the N
pairs of the N transmitting antennas and the N receiving antennas
include two pairs of the transmitting and the receiving antennas
that have interference with each other.
3. The antenna apparatus as claimed in claim 1, wherein, the N
pairs of the N transmitting antennas and the N receiving antennas
include two pairs of the transmitting and the receiving antennas,
one pair not having interference with the other pair, the other
pair having interference with the one pair.
4. The antenna apparatus as claimed in claim 1, wherein, the N
pairs of the N transmitting antennas and the N receiving antennas
include two pairs of the transmitting and the receiving antennas
that do not have interference with each other.
5. The antenna apparatus as claimed in claim 1, wherein the N
receiving antennas have optical axes, the optical axes being
matched with optical axes of the corresponding N transmitting
antennas within the N pairs.
6. The antenna apparatus as claimed in claim 1, wherein the
transmitting antennas and the receiving antennas are parabola
antennas having spiral reflection surfaces corresponding to one
cycle the RF signals having OAM of the designated modes.
7. The antenna apparatus as claimed in claim 1, wherein the
designated modes are types of modes that multiply delays occurred
in one cycle by I, and I is even number.
8. An antenna apparatus comprising: N (2=<N) transmitting
antennas configured to transmit RF signals having Orbital Angular
Momentum (OAM) of designated modes; and N receiving antennas
configured to make N pairs with the N transmitting antennas,
respectively, and to receive the RF signals having OAM of the
designated modes transmitted from the corresponding N transmitting
antennas within the N pairs, wherein the transmitting antennas
include output parts that output the RF signals, first transmitting
filters that transmit the RF signals output from the output parts,
and first parabola reflectors that reflect the RF signals
transmitted through the first transmitting filters, and total
delays of delays given by the first transmitting filters to the RF
signals and delays given by the first parabola reflectors realize
mode conversion of the RF signals output from the output parts to
the RF signals having OAM of the designated modes, and wherein the
receiving antennas include second parabola reflectors that reflect
the RF signals having OAM of the designated modes transmitted from
the transmitting antennas, second transmitting filters that give
delays to the RF signals output from the second parabola
reflectors, and receiving parts that receives the RF signals
transmitted through the second transmitting filters, and total
delays of delays given by the second parabola reflectors to the RF
signals and delays given by the second transmitting filters to the
RF signals realize reverse mode conversion of the RF signals input
to second parabola reflectors to planar wave RF signals.
9. The antenna apparatus as claimed in claim 8, wherein, the N
pairs of the N transmitting antennas and the N receiving antennas
include two pairs of the transmitting and the receiving antennas
that have interference with each other.
10. The antenna apparatus as claimed in claim 8, wherein, the N
pairs of the N transmitting antennas and the N receiving antennas
include two pairs of the transmitting and the receiving antennas,
one pair not having interference with the other pair, the other
pair having interference with the one pair.
11. The antenna apparatus as claimed in claim 8, wherein, the N
pairs of the N transmitting antennas and the N receiving antennas
include two pairs of the transmitting and the receiving antennas
that do not have interference with each other.
12. The antenna apparatus as claimed in claim 8, wherein the N
receiving antennas have optical axes, the optical axes being
matched with optical axes of the corresponding N transmitting
antennas within the N pairs.
13. The antenna apparatus as claimed in claim 8, wherein the
transmitting antennas and the receiving antennas are parabola
antennas having spiral reflection surfaces corresponding to one
cycle the RF signals having OAM of the designated modes.
14. The antenna apparatus as claimed in claim 8, wherein the
designated modes are types of modes that multiply delays occurred
in one cycle by I, and I is even number.
15. A signal transmitting system comprising: transmitting antennas
configured to have axes as Orbital Angular Momentum (OAM) axes and
to transmit signals having OAMs, respectively, the OAMs having
distributions of phase delays, respectively, the distributions
being obtained by multiplying an angle by proportionality factors,
respectively, the proportionality factors being integer numbers,
respectively, different to each other, the angle being obtained
around the OAM axes; and receiving antennas configured to have axes
as OAM axes and to receive the respective signals, wherein the OAM
axes of the transmitting antennas and the OAM axes of the receiving
antennas are in line with the same lines, respectively, wherein the
transmitting antennas and the receiving antennas are arranged in
pairs, respectively, the OAM axes included in the pairs are
arranged on different lines, respectively, and the signals having
OAM are transmitted within the same frequency band at the same time
period, wherein the transmitting antennas include output parts that
output the RF signals, first transmitting filters that transmit the
RF signals output from the output parts, and first parabola
reflectors that reflect the RF signals transmitted through the
first transmitting filters, and total delays of delays given by the
first transmitting filters to the RF signals and delays given by
the first parabola reflectors realize mode conversion of the RF
signals output from the output parts to the RF signals having OAM
of the designated modes, and wherein the receiving antennas include
second parabola reflectors that reflect the RF signals having OAM
of the designated modes transmitted from the transmitting antennas,
second transmitting filters that give delays to the RF signals
output from the second parabola reflectors, and receiving parts
that receives the RF signals transmitted through the second
transmitting filters, and total delays of delays given by the
second parabola reflectors to the RF signals and delays given by
the second transmitting filters to the RF signals realize reverse
mode conversion of the RF signals input to second parabola
reflectors to planar wave RF signals.
16. The signal transmitting system as claimed in claim 15, wherein
the transmitting antennas and the receiving antennas have
combinations of the proportionality factors of the same sign,
respectively, and thereby constitute OAM systems.
17. The signal transmitting system as claimed in claim 16, an
absolute value of the proportionality factor of a certain pair is
less than twice as that of the other pair.
18. The signal transmitting system as claimed in claim 16, the
proportionality factor has an even value.
19. The signal transmitting system as claimed in claim 15, the
transmitting antennas and the receiving antennas of the pairs have
the same OAM, respectively.
Description
FIELD
The present invention is related to an antenna apparatus.
BACKGROUND
Microwave backhaul has been extensively used to connect base
stations to the corresponding base station controllers for several
years (for example, Non Patent Document 1).
However, currently, wireless networks are evolving from supporting
voice-only to supporting both voice and high-speed data services.
Thus, there will be an increasing need for bandwidth capacity at
base stations and microwave backhaul.
Line-of-sight (LoS) MIMO can be considered as a candidate solution
for high capacity microwave backhaul (for example, Non Patent
Document 2). In these systems, due to the lack of multipath
scattering, the antenna separation depends on communication
distance to achieve space multiplexing.
For example, in a LoS MIMO system as illustrated in FIG. 1, 2*2
(two-by-two) form communication is performed by using transmitting
antennas Tx1 and Tx2 and receiving antennas Rx1 and Rx2. Distance d
between the transmitting antennas Tx1 and Tx2 which is necessary
for separating the transmitting antennas Tx1 and Tx2 depends on
communication distance L, as represented by formula (1). d= {square
root over (.lamda.L/2)} (1)
Here, .lamda. represents wavelength. In a case where the
communication distance L is 400 m and communication frequency is
2.4 GHz, the distance d becomes about 5 m. In a case where the
communication distance L is 400 m and communication frequency is 60
GHz, the distance d becomes about 1 m. Therefore, the antenna
separation (the distance d) is relatively large and usually not
available for compact devices. Furthermore, if the antenna
separation shrinks, the channel capacity degrades drastically.
Recently, the study of orbital angular momentum (OAM) is very hot
in high capacity optical communication (for example, Non Patent
Document 3). OAM, similar to polarization (Spin Angular Momentum
(SAM)), is also a fundamental property of electromagnetic
waves.
As illustrated in FIG. 2, an electromagnetic wave having OAM has a
spiral wavefront, and represents a linear phase delay with
azimuthal angle OAM mode 1 (1=.+-.1, .+-.2, . . . ) represents that
there is a phase delay of 21.pi. during one cycle (physical one
cycle). The phase delay is represented in an electric angle.
In the configuration of optical communication as illustrated in
FIG. 3, OAM signals are superposed with respect to a single optical
axis by using optical combiners (for example, Non Patent Document
3).
Since electromagnetic waves having different OAM modes are
orthogonal to each other, high capacity is achieved due to multiple
orthogonal channels.
However, it is difficult for a Radio Frequency (RF) signal to
superpose OAM channels with respect to a single optical axis. Thus,
it is difficult to multiplex the RF signal.
Non-Patent Document 1: Mobile Backhaul: Fiber vs. Microwave, Case
Study Analyzing Various Backhaul Technology Strategies, Tzvika
Naveh. [Searched on Jan. 29, 2013] Internet
(http://www.ceragon.com/files/ceragon_mobile_backhau_fiber_microwave_whit-
e_paper.pdf)
Non-Patent Document 2: C. Sheldon, E. Torkildson, M. Seo, C. P.
Yue, U. Madhow, and M. Rodwell, "A 60 GHz line-of-sight 2.times.2
MIMO link operating at 1.2 Gbps," in Proc. IEEE Antennas Propag.
Soc. Int. Symp. (AP-S 2008), July 2008.
Non-Patent Document 3: J. Wang, J.-Y. Yang, I. M. Fazal, N. Ahmed,
Y. Yan, H. Huang, Y. Ren, Y. Yue, S. Dolinar, M. Tur, and A. E.
Willner, "Terabit free-space data transmission employing orbital
angular momentum multiplexing," Nature Photonics, vol. 6, pp.
488-496, July 2012.
SUMMARY
An antenna apparatus according to an embodiment of the present
invention includes N (2=<N) transmitting antennas configured to
transmit RF signals having Orbital Angular Momentum (OAM) of
designated modes, and N receiving antennas configured to make N
pairs with the N transmitting antennas, respectively, and to
receive the RF signals having OAM of the designated modes
transmitted from the corresponding N transmitting antennas within
the N pairs.
The object and advantages of the invention will be realized and
attained by means of the elements and combinations particularly
pointed out in the appended claims. It is to be understood that
both the foregoing general description and the following detailed
description are exemplary and explanatory and are not restrictive
of the invention as claimed.
BRIEF DESCRIPTION OF DRAWINGS
FIG. 1 illustrates a Los MIMO system,
FIG. 2 illustrates a wavefront of an electromagnetic wave having
OAM,
FIG. 3 illustrates a configuration of optical communication in
which OAM signals are superposed with respect to a single optical
axis by using optical combiners,
FIG. 4 illustrates an arrangement of transmitting antennas and
receiving antennas included in an antenna apparatus according to an
embodiment,
FIG. 5 illustrates an arrangement of the transmitting antennas and
the receiving antennas included in the antenna apparatus according
to the embodiment,
FIG. 6 is a diagram illustrating wavefronts of RF signals having
OAM according to the single mode,
FIG. 7 is a diagram illustrating wavefronts of RF signals having
OAM according to the multiple mode,
FIG. 8 is a diagram illustrating positional relationship between
two neighboring receiving antennas included in the antenna
apparatus of the present embodiment in plan view,
FIG. 9 is a diagram illustrating a simulation result of channel
capacity of the antenna apparatus according to the present
embodiment,
FIG. 10 is a diagram illustrating the relationship between value
.beta. which satisfies the equation d=.beta.(.lamda.L/2).sup.1/2
and the channel capacity in a condition where SNR is fixed to 20
dB,
FIG. 11 is a diagram illustrating the antenna apparatus according
to the present embodiment,
FIG. 12 is a diagram illustrating the antenna apparatus according
to a variation of the present embodiment,
FIG. 13 is a diagram illustrating an antenna apparatus according to
one variation of the present embodiment, and
FIG. 14 is a diagram illustrating an antenna apparatus according to
another variation of the present embodiment.
DESCRIPTION OF EMBODIMENT
In the following, embodiments to which an antenna apparatus of the
present invention is applied will be described.
Embodiment
FIGS. 4 and 5 illustrate an arrangement of transmitting antennas
and receiving antennas included in an antenna apparatus 100
according to the present embodiment.
The antenna apparatus 100 includes transmitting antennas Tx1, Tx2,
Tx3, . . . TxN and receiving antennas Rx1, Rx2, Rx3, . . . RxN.
Herein, N represents an integer number greater than or equal to
two. In the embodiment as illustrated in FIGS. 4 and 5, a case
where N is greater than or equal to five will be described.
As illustrated in FIG. 4, the transmitting antennas Tx1, Tx2, Tx3,
. . . TxN and the receiving antennas Rx1, Rx2, Rx3, . . . RxN may
be arranged in a linear fashion, respectively. The transmitting
antennas Tx1, Tx2, Tx3, . . . TxN and the receiving antennas Rx1,
Rx2, Rx3, . . . RxN are arranged in a manner that optical axes of
the transmitting antennas Tx1, Tx2, Tx3, . . . TxN and optical axes
of the receiving antennas Rx1, Rx2, Rx3, . . . RxN correspond to
each other, respectively.
The transmitting antennas Tx1, Tx2, Tx3, . . . TxN communicate with
the receiving antennas Rx1, Rx2, Rx3, . . . RxN, respectively.
Accordingly, the transmitting antenna Tx1 communicates with the
receiving antenna Rx1. Similarly, the transmitting antenna Tx2
communicates with the receiving antenna Rx2. The transmitting
antenna Tx3 communicates with the receiving antenna Rx3. Moreover,
the transmitting antenna TxN communicates with the receiving
antenna RxN.
As a result, it is possible to perform communications in N channels
between the transmitting antennas Tx1, Tx2, Tx3, . . . TxN and the
receiving antennas Rx1, Rx2, Rx3, . . . RxN.
In the antenna apparatus 100 according to the present embodiment,
each of the transmitting antennas Tx1, Tx2, Tx3, . . . TxN performs
mode conversion in which RF signal without OAM mode is converted
into an RF signal having orbital angular momentum (OAM) of
designated mode and transmits the RF signal having OAM of the
designated mode. Each of the receiving antennas Rx1, Rx2, Rx3, . .
. RxN performs reverse conversion in which the RF signal having OAM
of the designated mode is reversely converted into the RF signal
without OAM mode.
The RF signal having OAM propagates in a spiral manner along an
optical axis of the transmitting antenna Tx while shifting a phase
of the RF signal having OAM. The optical axis extends in a
propagation direction of the RF signal having OAM. Accordingly, the
RF signal having OAM has a spiral shaped wavefront (a helicoid
wavefront) having a central axis corresponding to the optical
axis.
Herein, mode 1 (1=.+-.1, .+-.2, . . . ) of the RF signal having OAM
indicates that a phase delay of 21.pi. is included in a physical
one cycle (360 degrees). Mode 1 indicates that a phase delay of
2.pi. is included in the physical one cycle (360 degrees).
Accordingly, the RF signal having OAM of mode 1 (1=1) has a
wavefront of which the phase shifts 2.pi. while the RF signal
having OAM of mode 1 (1=1) propagates in a spiral manner in the
physical one cycle (360 degrees). The RF signal having OAM of mode
2 (1=2) has a wavefront of which the phase shifts 4.pi.
(2.pi..times.2) while the RF signal having OAM of mode 2 (1=2)
propagates in a spiral manner in the physical one cycle (360
degrees). Accordingly, the RF signal having OAM of mode 1 has a
wavefront of which the phase shifts 21.pi. while the RF signal
having OAM of mode 1 propagates in a spiral manner in the physical
one cycle (360 degrees).
Herein, a value 1 of mode 1 takes a positive value when the RF
signal having OAM of mode 1 propagates along the optical axis in a
spiral manner of the counterclockwise direction, and takes a
negative value when the RF signal having OAM of mode 1 propagates
along the optical axis in a spiral manner of the clockwise
direction.
Since the antenna apparatus 100 uses the RF signal having OAM, it
is necessary to arrange the receiving antennas Rx1.about.RxN in
positions where the receiving antennas Rx1.about.RxN can receive
the RF signals having OAM from the transmitting antennas
Tx1.about.TxN, respectively.
The RF signal having OAM propagates in a spiral manner along the
optical axis which extends along the propagation direction while
shifting the phase. Accordingly, the RF signal having OAM
propagates in a spiral manner along the optical axis. The phase of
the RF signal having OAM is determined by an azimuthal angle of the
spiral shaped wavefront.
Accordingly, in order to receive the whole cycles of the RF signals
having OAM in N channels, it is necessary to bring the optical axes
of the receiving antennas Rx1.about.Rx in line with the optical
axes of the transmitting antennas Tx1.about.TxN, respectively.
The transmitting antennas Tx1.about.TxN that transmit the RF
signals having OAM and the receiving antennas Rx1.about.RxN that
receive the RF signals having OAM have designated configurations
that can realize the mode conversion and the reverse conversion,
respectively.
However, details of the configurations of the transmitting antennas
Tx1.about.TxN and the receiving antennas Rx1.about.RxN will be
described later. In FIGS. 4 and 5, positional relationships between
the transmitting antennas Tx1.about.TxN and the receiving antennas
Rx1.about.RxN will be described.
Thus, the transmitting antennas Tx1, Tx2, Tx3, . . . TxN and the
receiving antennas Rx1, Rx2, Rx3, . . . RxN may be arranged in a
linear fashion as long as the optical axes of the transmitting
antennas Tx1, Tx2, Tx3, . . . TxN and the optical axes of the
receiving antennas Rx1, Rx2, Rx3, . . . RxN correspond to each
other, respectively, as illustrated in FIG. 4.
Otherwise, the transmitting antennas Tx1, Tx2, Tx3, . . . TxN and
the receiving antennas Rx1, Rx2, Rx3, . . . RxN may be arranged in
a random fashion as long as the optical axes of the transmitting
antennas Tx1, Tx2, Tx3, . . . TxN and the optical axes of the
receiving antennas Rx1, Rx2, Rx3, . . . RxN correspond to each
other, respectively, as illustrated in FIG. 5.
In FIGS. 4 and 5, the transmitting antenna Tx1 and the receiving
antenna Rx1 perform communication which uses the RF signal having
OAM of mode 1, and the transmitting antenna Tx2 and the receiving
antenna Rx2 perform communication which uses the RF signal having
OAM of mode 2.
In FIGS. 4 and 5, the transmitting antenna Tx3 and the receiving
antenna Rx3 perform communication which uses the RF signal having
OAM of mode 3, and the transmitting antenna TxN and the receiving
antenna RxN perform communication which uses the RF signal having
OAM of mode N.
However, an assignment of mode 1 as illustrated in FIGS. 4 and 5 is
illustrative only. Each pair of the transmitting antennas
Tx1.about.TxN and the receiving antennas Rx1.about.RxN communicates
with each other by using the RF signal having OAM of the same mode.
Each pair of the transmitting antennas Tx1.about.TxN and the
receiving antennas Rx1.about.RxN is not able to communicate with
each other by using the RF signals having OAM of different
modes.
Accordingly, all of the pairs of the transmitting antennas
Tx1.about.TxN and the receiving antennas Rx1.about.RxN may
communicate by using the RF signals having OAM of the same
mode.
Next, a single mode and a multiple mode will be described with
reference to FIGS. 6 and 7.
FIG. 6 is a diagram illustrating wavefronts of RF signals having
OAM according to the single mode. FIG. 7 is a diagram illustrating
wavefronts of RF signals having OAM according to the multiple mode.
In FIGS. 6 and 7, the transmitting antennas Tx1 and Tx2 and the
receiving antennas Rx1 and Rx2 perform communications in two
channels.
In the single mode, the RF signals having OAM used in plural of
channels have the same (single) mode 1. In the multiple mode, the
RF signals having OAM used in plural of channels have plural modes,
i.e. more than two modes. Since the communications in two channels
are illustrated in FIGS. 6 and 7, the RF signals having OAM of the
same mode 1 are illustrated in FIG. 6.
The RF signals having OAM of the same mode 1, as illustrated in
FIG. 6, propagate along optical axes A1 and A2 in a spiral manner,
respectively.
In FIG. 7, the RF signals having OAM of two different modes are
illustrated. The RF signals having OAM of the different modes, as
illustrated in FIG. 7, propagate along optical axes A1 and A2 in a
spiral manner, respectively.
In FIGS. 6 and 7, the wavefronts of the RF signals having OAM are
illustrated schematically.
Next, low interference of the two channels that are realized by the
two neighboring receiving antennas will be described with reference
to FIG. 8. Herein, receiving antennas Rx1 and Rx2 are used as an
example of the two neighboring receiving antennas.
FIG. 8 is a diagram illustrating positional relationship between
the two neighboring receiving antennas included in the antenna
apparatus 100 of the present embodiment in plan view.
In FIG. 8, center points O1 and O2 and outlines C1 and C2 of the
receiving antennas Rx1 and Rx2 as viewed from the propagating
direction of RF signals having OAM are illustrated. In reality, the
receiving antennas Rx1 and Rx2 are arranged adjacently to each
other as illustrated in FIG. 7 and perform communications in the
single mode or the multiple mode in the two channel.
The outlines C1 and C2 of the receiving antennas Rx1 and Rx2 are
shaped in circles that have the center points O1 and O2 and radii
R, respectively. Distance between the center points O1 and O2 is d.
Since the receiving antennas Rx1 and Rx2 are separated from each
other, the distance d is greater than 2R, i.e., 2R<=d.
The optical axes of the receiving antennas Rx1 and Rx2 pass through
the center points O1 and O2 and extend in the directions vertical
to the circles represented by the outlines C1 and C2,
respectively.
The transmitting antennas Tx1 and Tx2 corresponding to the
receiving antennas Rx1 and Rx2 are arranged on the opposite side to
the receiving antennas Rx1 and Rx2, as illustrated in FIG. 7, and
have the same configurations as those of the receiving antennas Rx1
and Rx2, respectively. The optical axes of the transmitting
antennas Tx1 and Tx2 are identical to the optical axes of the
receiving antennas Rx1 and Rx2, respectively.
Accordingly, the transmitting antenna Tx1 and the receiving antenna
Rx1 have the same configurations with each other and face each
other in a state where the optical axes thereof are identical to
each other. Similarly, the transmitting antenna Tx2 and the
receiving antenna Rx2 have the same configurations with each other
and face each other in a state where the optical axes thereof are
identical to each other.
Thus, distance between the center point of the transmitting antenna
Tx1 and the center point of the transmitting antenna Tx2 is d.
The transmitting antenna Tx1 and the receiving antenna Rx1 use the
RF signal having OAM of mode m to communicate with each other. The
transmitting antenna Tx2 and the receiving antenna Rx2 use the RF
signal having OAM of mode n to communicate with each other. Integer
numbers m and n are arbitrary number and may be the same number or
different numbers.
Herein, in order to explain the low interference between the
receiving antennas Rx1 and Rx2, reception of the RF signals having
OAM transmitted from the transmitting antennas Tx1 and Tx2 at a
point P which is located on a surface of the receiving antenna Rx2
will be described.
A distance between the point P and the center point O2 of the
receiving antenna Rx2 is r (r<R). Line segment O1O2 and line
segment O2P intersect at the center point O2 at angle .theta.. Line
segment O1P and the line segment O1O2 intersect at the center point
O1 at angle .alpha..
Since the optical axes of the receiving antennas Rx1 and Rx2 that
constitute the two channels are different from each other as
illustrated in FIG. 8, an electric field E at the point P
transmitted from the transmitting antenna Tx1 is represented by a
following formula (2). E=E.sub.0e.sup.jma (2)
Herein, E.sub.0 represents an amplitude of the electric field
E.
Power Pim,n of the RF signal having OAM which is transmitted from
the transmitting antenna Tx1 and is received by the receiving
antenna Rx2 is represented by a following formula (3). The power
Pim,n represents power of an interference which occurs at the
receiving antenna Rx2 in a case where the receiving antenna Rx2
receives the RF signal having OAM from the transmitting antenna
Tx1.
.varies..times..intg..times..intg..pi..pi..times..times..times..times..ti-
mes..times..alpha..times..times..times..theta..times..times..times..times.-
.theta..times..times..times..times. ##EQU00001##
Herein, Z represents an impedance of the RF signal having OAM in a
free space.
The angle .alpha. which is made by the intersection of the line
segment O1P and the line segment O1O2 is represented by a following
formula (4).
.alpha..function..times..times..times..times..theta..times..times..times.-
.times..theta. ##EQU00002##
Similar to the formula (3), power Psn of the RF signal having OAM
which is transmitted from the transmitting antenna Tx2 and is
received by the receiving antenna Rx2 is represented by a following
formula (5).
.varies..times..intg..times..intg..pi..pi..times..times..times..times..ti-
mes..times..theta..times..times..times..times..times..theta..times..times.-
.times..times..theta..times..times..times..times..times..times..times..tim-
es..pi..times. ##EQU00003##
Accordingly, it is possible to derive a following formula (6) by
calculating a ratio of the power Pim,n to the power Psn based on
formulae (3) and (5).
.pi..times..times..intg..times..intg..pi..pi..times..times..times..times.-
.times..alpha..times..times..times..times..times..theta..times..times..tim-
es..times..theta..times..times..times..times..times.
##EQU00004##
An integral term I|r included in the formula (6) is represented by
a following formula (7).
I|.sub.r=.intg..sub.-.pi..sup..pi.e.sup.jm.alpha.e.sup.-jn.theta.d.theta.
(7)
Herein, a calculation result of the formula (7) becomes zero if m
and n satisfy the condition given by (8). If m>0n>0, m is
even number and n>=m/2+1 If m<0n<0, -m is even number and
-n>=-m/2+1 (8)
Therefore, a calculation result of the formula (6) becomes zero.
Accordingly, the ratio of the power Pim,n to the power Psn becomes
zero, and thereby the interference from Tx1-Rx1 to Tx2-Rx2 is
suppressed. Meanwhile, the interference from Tx2-Rx2 to Tx1-Rx1
also needs suppressing. Then, m and n should satisfy the condition
given by (9). If m>0 n>0, n is even number and m>=n/2+1 If
m<0 n<0, -n is even number and -m>=-n/2+1 (9)
Herein, if m and n satisfy both (8) and (9), the two channels are
orthogonal.
Since the OAM mode represents the spiral wavefront rotates 1
periods in one cycle, in which 1 is an integer, when (8) and (9)
are both satisfied, the spiral wavefronts of the two transmitting
antennas rotate in the same direction, and the spiral wavefront of
each transmitting antenna rotate less than twice as fast as the
other antenna, and the spiral wavefront of each transmitting
antenna rotates 1 periods in one cycle, in which 1 is even
number.
In fact, as in FIGS. 4 and 5, in an N-channel system, the best
condition is that any two channels are orthogonal. it means that
the spiral wavefronts of all the transmitting antennas rotate in
the same direction, and the spiral wavefront of each transmitting
antenna rotate less than twice as fast as the other antenna, and
the spiral wavefront of each transmitting antenna rotates 1 periods
in one cycle, in which 1 is even number. {2}, {-2}, {4, 6}, {-4,
-6} are some examples of such orthogonal channel groups.
For {2}, 2 is first even number, and 2 is obviously less than
double of 2. {2} means OAM mode 2 is applied in all the N
channels.
For {4, 6}, 4 and 6 are both even number, and 6 is less than double
of 4. {4, 6} means OAM mode 4 is applied in all the N channels, or
OAM mode 6 is applied in all the N channels, or OAM mode 4 is
applied in some channels and OAM mode 6 is applied in other
channels.
For {-2} and {-4, -6}, the system setup is similar and the only
difference is the rotation direction.
Besides orthogonal channels, channels with low interference can
also be used. For two channels (mode m and mode n), the condition
of low interference is given by (10). If m>0 n>0, m>=n/2,
and n>=m/2 If m<0 n<0, -m>=-n/2, and -n>=m/2
(10)
It means that the spiral wavefronts of the two transmitting
antennas rotate in the same direction, and the spiral wavefront of
each transmitting antenna rotate no more than twice as fast as the
other antenna. It is clear that orthogonal channels satisfied this
condition.
Therefore, as in FIGS. 4 and 5, in an N-channel system it is
expected that any two channels are of low interference. It means
that the spiral wavefronts of all the transmitting antennas rotate
in the same direction, and the spiral wavefront of each
transmitting antenna rotate no more than twice as fast as the other
antenna. {1, 2}, {-1, -2}, {2, 3, 4}, {-2, -3, -4} are some
examples of such channel groups with low interference.
For {1, 2}, 2 is no more than double of 1. {1, 2} means OAM mode 1
is applied in all the N channels, or OAM mode 2 is applied in all
the N channels, or OAM mode 1 is applied in some channels and OAM
mode 2 is applied in other channels
For {2, 3, 4}, 4 is no more than double of 2. {2, 3, 4} means OAM
mode 2 is applied in all the N channels, or OAM mode 3 is applied
in all the N channels, or OAM mode 4 is applied in all the N
channels, or OAM mode 2 is applied in some channels and OAM mode 3
is applied in other channels, or OAM mode 2 is applied in some
channels and OAM mode 4 is applied in other channels, or OAM mode 3
is applied in some channels and OAM mode 4 is applied in other
channels, or OAM mode 2 is applied in some channels and OAM mode 3
is applied in some channels and OAM mode 4 is applied in other
channels.
For {-1, -2} and {-2, -3, -4}, the system setup is similar and the
only difference is the rotation direction.
In terms of formula (6), if m>0 and n<0 or m<0 and n>0,
the interference is relatively larger. Therefore, as in FIGS. 4 and
5, in an N-channel system, at least, the spiral wavefronts of all
the transmitting antennas should rotate in the same direction.
Next, a channel capacity of the antenna apparatus 100 according to
the present embodiment will be described with reference to FIG.
9.
FIG. 9 is a diagram illustrating a simulation result of the channel
capacity of the antenna apparatus 100 according to the present
embodiment.
In FIG. 9, in addition to a channel capacity (2*2OAM) of the
transmitting antennas Tx1 and Tx2 and the receiving antennas Rx1
and Rx2 of the antenna apparatus 100 according to the present
embodiment, a channel capacity (SISO) of a transmitting antenna and
a receiving antenna that constitute a SISO (Single Input Single
Output) is illustrated. Further, for a comparison purpose, three
channel capacities (2*2LosMIMO(d=(.lamda.L/2).sup.1/2),
2*2LosMIMO(d=(1/2*(.lamda.L/2).sup.1/2) and
2*2LosMIMO(d=(1/4*(.lamda.L/2).sup.1/2)) are illustrated in FIG. 9.
The three channel capacities (2*2LosMIMO(d=(.lamda.L/2).sup.1/2),
2*2LosMIMO(d=(1/2*(.lamda.L/2).sup.1/2) and
2*2LosMIMO(d=(1/4*(.lamda.L/2).sup.1/2)) are obtained by three
LosMIMOs including two transmitting antennas and two receiving
antennas that form two channels, respectively. The three LosMIMOs
have different center-to-center distances d (see FIG. 8) between
the two transmitting antennas and the two receiving antennas.
The channel capacity (2*2LosMIMO(d=(.lamda.L/2).sup.1/2)) is
obtained by the LOsMIMO having the distance
d(=(*.lamda.L/2).sup.1/2). The channel capacity
(2*2LosMIMO(d=(1/2*(.lamda.L/2).sup.1/2)) is obtained by the
LOsMIMO having the distance d (=1/2*(.lamda.L/2).sup.1/2). The
channel capacity (2*2LosMIMO(d=(1/4*(.lamda.L/2).sup.1/2)) is
obtained by the LOsMIMO having the distance d
(=1/4*(.lamda.L/2).sup.1/2).
Herein, L represents length between the transmitting antenna Tx1
and the receiving antenna Rx1. The length L is equal to that of
transmitting antenna Tx2 and the receiving antenna Rx2.
In FIG. 9, the horizontal axis represents a Signal to Noise Ratio
(SNR), and the vertical axis represents the channel capacity
(bps/Hz).
As illustrated in FIG. 9, the channel capacity of the
2*2LosMIMO(d=(.lamda.L/2).sup.1/2 is slightly greater than the
channel capacity (2*2OAM) obtained by the transmitting antennas Tx1
and Tx2 and the receiving antennas Rx1 and Rx2 of the antenna
apparatus 100, and is the highest of all the channel
capacities.
However, the channel capacity of the
2*2LosMIMO(d=(.lamda.L/2).sup.1/2 is obtained in a case where the
LosMIMO has the longest distance d among three LosMIMOs.
The simulation result shows that the channel capacities of the
LosMIMOs degrade with decreasing of the distance d. The shorter the
distance d becomes, the lower the separation of the neighboring
antennas becomes.
The channel capacity (2*2OAM) is obtained in a condition where the
distance d is much shorter than the distance d
(=1/4*(.lamda.L/2).sup.1/2), because the distance d of the antenna
apparatus 100 is close to 2R (see FIG. 8). Compared to the channel
capacities of the LosMIMOs that degrade with decreasing of the
center-to-center distance d, the channel capacity (2*2OAM) shows
very high value in spite of the short center-to-center distance d
of the antenna apparatus 100.
The SISO shows the lowest channel capacity as illustrated in FIG.
9. Although the channel capacity of the SISO increases with
increasing of the SNR, the channel capacity of the SISO is lower
than the channel capacity (2*2OAM) of the transmitting antennas Tx1
and Tx2 and the receiving antennas Rx1 and Rx2 of the antenna
apparatus and the three channel capacities of the three
LosMIMOs.
Next, with reference to FIG. 10, a relationship between value
.beta. which satisfies an equation d=.beta.(.lamda.L/2).sup.1/2 and
the channel capacity will be described in a condition where the SNR
is fixed to 20 dB.
FIG. 10 is a diagram illustrating the relationship between the
value .beta. which satisfies the equation
d=.beta.(.lamda.L/2).sup.1/2 and the channel capacity in a
condition where the SNR is fixed to 20 dB.
In FIG. 10, the channel capacity (2*2OAM) of the transmitting
antennas Tx1 and Tx2 and the receiving antennas Rx1 and Rx2 of the
antenna apparatus 100 according to the present embodiment and the
channel capacity (2*2LosMIMO) of the two neighboring transmitting
antennas and the two neighboring receiving antennas that form the
LosMIMO are illustrated.
Since the horizontal axis of the FIG. 10 represents the value
.beta. which satisfies the equation d=.beta.(.lamda.L/2).sup.1/2,
the center-to-center distance decreases with decreasing of the
value .beta.. Accordingly, the neighboring two antennas separate
with increasing of the value .beta..
The center-to-center distance d becomes shorter with decreasing of
the value .beta.. Accordingly, the neighboring two antennas come
closer with decreasing of the value .beta..
As illustrated in FIG. 10, the channel capacity (2*2OAM) of the
transmitting antennas Tx1 and Tx2 and the receiving antennas Rx1
and Rx2 of the antenna apparatus 100 is constant regardless of the
value .beta.. This result is derived from a feature that the high
channel capacity is obtained regardless of the center-to-center
distance d.
The channel capacity (2*2LosMIMO) of the two neighboring
transmitting antennas and the two neighboring receiving antennas
that form the two channel LosMIMO decreases with decreasing of the
value .beta..
This shows that the channel capacity degrades drastically as the
center-to-center distance d becomes shorter.
According to the present embodiment, it is possible to obtain the
high channel capacity (2*2OAM) regardless of the center-to-center
distance d between the transmitting antennas Tx1 and Tx2 and the
receiving antennas Rx1 and Rx2.
Further, the shorter the center-to-center distance d becomes, the
greater the advantage of the channel capacity (2*2OAM) of the
antenna apparatus 100 becomes compared to the channel capacity
(2*2LosMIMO).
Thus, the antenna apparatus 100 of the present embodiment becomes
more advantageous in a situation where the separation of the
neighboring antennas is relatively low than in a situation where
the separation of the neighboring antennas is relatively high.
Accordingly, the antenna apparatus 100 of the present embodiment is
suitable for downsizing.
Next, configurations of the transmitting antennas Tx1 and Tx2 and
the receiving antennas Rx1 and Rx2 of the antenna apparatus 100
will be described with reference to FIGS. 11 to 14.
Hereinafter, in a case where the transmitting antennas Tx1 and Tx2
are not distinguished, the transmitting antenna of the present
embodiment is referred to as a transmitting antenna Tx. Similarly,
in a case where the receiving antennas Rx1 and Rx2 are not
distinguished, the receiving antenna of the present embodiment is
referred to as a receiving antenna Rx.
Since the transmitting antenna Tx and the receiving antenna Rx have
the same configuration, the transmitting antenna Tx can be used as
the receiving antenna Rx, and the receiving antenna Rx can be used
as the transmitting antenna Tx.
Accordingly, in a case where the transmitting antenna Tx and the
receiving antenna Rx are not distinguished, the antenna of the
present embodiment is referred to as an antenna 10 or 20.
FIG. 11 is a diagram illustrating the antenna apparatus 100
according to the present embodiment. In FIG. 11, (A1) and (A2)
illustrate the antenna 10 which transmits and receives the RF
signal having OAM of mode 1, and (B1) and (B2) illustrate the
antenna 20 which transmits and receives the RF signal having OAM of
mode 2.
In FIG. 11, as illustrated in (A1), (A2), (B1) and (B2), XYZ
coordinates system as an orthogonal coordinates is defined. The Z
axis is parallel to the optical axes of the antennas 10 and 20.
As illustrated in (A1) and (A2) of FIG. 11, antenna 10 used for
mode 1 includes a radiator 11 (see (A2)) and an antenna reflector
12. The antenna 10 is a type of a deformed parabola antenna. In
(A1) of FIG. 11, the radiator 11 is omitted.
The radiator 11 performs transmit and receive of the RF signal. The
radiator 11 is fixed to the antenna reflector 12 by stays or the
like that are not illustrated. The radiator 11 transmits the RF
signal to the antenna reflector 12 in the negative Z axis
direction. The radiator 11 receives the RF signal which propagates
in the positive Z axis direction after being reflected by the
antenna reflector 12.
The antenna reflector 12 has a parabolic concaved cross section
truncated by a plane including the Z axis and is shaped in a circle
in plan view (see (A1) of FIG. 11). The optical axis of the antenna
reflector 12 passes through the center O and extends parallel to
the Z axis.
The antenna reflector 12 includes a slit 12A. The slit 12A is
formed in the antenna reflector 12 so that the slit 12 extends from
the center O to the periphery in the positive Z direction. A gap,
with half wavelength (.lamda./2) of a communication frequency in
the center O, is formed between one side 12B and the other side 12C
of the slit 12A in the Z axis direction. The gap is used to
generate one wavelength of path difference.
In the antenna reflector 12 described above, the gap is uniformly
and linearly distributed from the one side 12B to the other side
12C in the counterclockwise direction around the center O in a 360
degree arc as viewed from the positive Z direction. This means that
a phase of the surface of the reflector 12 progresses .lamda./2
(.pi.) in a 360 degree arc from the one side 12B to the other side
12C in the counterclockwise direction around the center O as viewed
from the positive Z direction.
Accordingly, if the RF signal without OAM mode is transmitted from
the radiator 11 to the antenna reflector 12 in the negative Z
direction, the RF signal without OAM mode radiated from the
radiator 11 is mode-converted into the RF signal having OAM of mode
1 by the antenna reflector 12, and then the RF signal having OAM of
mode 1 propagates in a spiral manner in the positive Z
direction.
The RF signal having OAM of mode 1 which is reflected and
mode-converted by the antenna reflector 12 propagates in a spiral
manner around the central axis Herein, the central axis of the RF
signal having OAM of mode 1 is equal to the optical axis which
passes through the center O and is parallel to the Z axis. The RF
signal having OAM of mode 1 which is mode-converted by the antenna
reflector 12 has the same mode as the antenna 10.
On the contrary, if the RF signal having OAM mode 1 propagates in a
spiral manner to the antenna reflector 12 in a state where the
central axis of the RF signal having OAM mode 1 corresponds to the
optical axis which passes through the center O and is parallel to
the Z axis, the RF signal having OAM mode 1 is reversely converted
into the planar wave by the antenna reflector 12 and the planar
wave RF signal is received by the radiator 11.
The antenna 10 is a type of a parabola antenna which has a spiral
reflection surface corresponding to one cycle of the spiral
wavefront of the RF signal having OAM of mode 1.
As illustrated in (B1) and (B2) of FIG. 11, antenna 20 used for
mode 2 includes a radiator 21 (see (B2)) and an antenna reflector
22. The antenna 20 is a type of a deformed parabola antenna. In
(B1) of FIG. 11, the radiator 21 is omitted.
The radiator 21 performs transmit and receive of the RF signal. The
radiator 21 is fixed to the antenna reflector 22 by stays or the
like that are not illustrated. The radiator 21 transmits the RF
signal to the antenna reflector 22 in the negative Z axis
direction. The radiator 21 receives the RF signal which propagates
in the positive Z axis direction after being reflected by the
antenna reflector 22. The radiator 21 is similar to the radiator
11.
The antenna reflector 22 has a parabolic concaved cross section
truncated by a plane including Z axis and is shaped in a circle in
plan view (see (B1) of FIG. 11). The optical axis of the antenna
reflector 22 passes through the center O and extends parallel to
the Z axis.
The antenna reflector 22 includes a boundary portion 22A. The
boundary portion 22A divides the antenna reflector 22 into a
reflection part 221 and a reflection part 222 along the XZ plane
which passes the center O. The reflection part 221 is located in
the positive Y axis side, and the reflection part 222 is located in
the negative Y axis side. The antenna reflector 22 is divided into
the two reflection parts 221 and 222 by the boundary portion
22A.
The reflection parts 221 and 222 are obtained by dividing one
parabola antenna into two parts along a line which passes through
the center point of the parabola antenna.
The reflection parts 221 and 222 have a positional relation in
which the reflection parts 221 and 222 are slightly rotated along
the Y axis in the opposite directions with each other.
A gap, with half wavelength (.lamda./2) of a communication
frequency in the center O is formed between one side 22B1 and the
other side 22C1 of the boundary portion 22A in the Z axis
direction. The gap is used to generate one wavelength of path
difference.
Similarly, a gap with half wavelength (.lamda./2) of a
communication frequency in the center O is formed between one side
22B2 and the other side 22C2 of the boundary portion 22A in the Z
axis direction. The gap is used to generate one wavelength of path
difference.
In the antenna reflector 22 as described above, the gap is
uniformly and linearly distributed from the one side 22B1 to the
one side 22B2 in the counterclockwise direction around the center O
in a 180 degree radius as viewed from the positive Z direction.
This means that a phase of the surface of the antenna reflector 22
progresses .lamda./2 (.pi.) in a 180 degree radius from the one
side 22B1 to the one side 22B2 in the counterclockwise direction
around the center O as viewed from the positive Z direction.
Similarly, the gap is uniformly and linearly distributed from the
other side 22C1 to the other side 22C2 in the counterclockwise
direction around the center O in a 180 degree radius as viewed from
the positive Z direction. This means that a phase of the surface of
the antenna reflector 22 progresses .lamda. (2.pi.) in a 180 degree
radius from the other side 22C1 to the other side 22C2 in the
counterclockwise direction around the center O as viewed from the
positive Z direction.
Accordingly, if the RF signal without OAM mode is transmitted from
the radiator 21 to the antenna reflector 22 in the negative Z
direction, the RF signal without OAM mode radiated from the
radiator 21 is mode-converted into the RF signal having OAM of mode
2 by the antenna reflector 22, and then the RF signal having OAM of
mode 2 propagates in a spiral manner in the positive Z
direction.
The RF signal having OAM of mode 2 which is reflected and
mode-converted by the antenna reflector propagates in a spiral
manner around the central axis. Herein, the central axis of the RF
signal having OAM of mode 2 is equal to the optical axis which
passes through the center O and is parallel to the Z axis. The RF
signal having OAM of mode 2 which is mode-converted by the antenna
reflector 22 has the same mode as the antenna 20.
On the contrary, if the RF signal having OAM mode 2 propagates in a
spiral manner to the antenna reflector 22 in a state where the
central axis of the RF signal having OAM mode 2 corresponds to the
optical axis which passes through the center O and is parallel to
the Z axis, the RF signal having OAM mode 2 is reversely converted
into the planar wave by the antenna reflector 22 and the planar
wave RF signal is received by the radiator 21.
The antenna 20 is a type of a parabola antenna which has a spiral
reflection surface corresponding to one cycle of the spiral
wavefront of the RF signal having OAM of mode 2.
Next, an antenna of the antenna apparatus 100 according to a
variation of the present embodiment will be described with
reference to FIG. 12.
FIG. 12 is a diagram illustrating the antenna apparatus 100
according to the variation of the present embodiment.
In (A) of FIG. 12, an antenna 30 according to the variation of the
present embodiment is illustrated. An antenna 30 includes a
radiator 31 and a transmission filter 32. The transmission filter
32 of mode 1 is illustrated in (B) of FIG. 12, and the transmission
filter 32 of mode 2 is illustrated in (C) of FIG. 12. In FIG. 12,
the XYZ coordinates system is defined in a similar manner to that
of FIG. 11.
The radiator 31 is similar to the radiators 11 and 21 as
illustrated in (A2) and (B2) of FIG. 11, respectively.
The transmission filter 32 is a type of a member which has a disk
shape and is made from insulating material. The transmission filter
32 can transmit the RF signal and is disposed in front of the
radiator 31. The transmission filter 32 is a kind of a phase
filter.
The transmission filter 32 as illustrated in (B) of FIG. 12 is
divided into eight transmission portions 32A1.about.32A8 that are
arranged in a radial fashion with respect to the center O1. The
transmission portions 32A1.about.32A8 have fan-like shapes having
45 degree center angles, respectively, as viewed from the positive
Z axis direction. The transmission portions 32A1.about.32A8 are
arranged in the counterclockwise direction in this order as viewed
from the positive Z direction. The transmission portion 32A1 and
the transmission portion 32A8 are arranged next to each other.
The transmission portions 32A1.about.32A8 have different
thicknesses. The transmission portion 32A1 is the thinnest and the
transmission portion 32A8 is the thickest among the transmission
portions 32A1.about.32A8. The transmission portions 32A1.about.32A8
have the different thicknesses so that the RF signal takes
different periods of time when the RF signal passes through the
transmission portions 32A1.about.32A8.
In a dielectric substance, propagation speed of the RF signal
decreases compared to in the atmosphere. Accordingly, it is
possible to set delay times that are given to the RF signal by the
transmission portions 32A1.about.32A8 based on the different
thicknesses of the transmission portions 32A1.about.32A8.
The delay time of the transmission portion 32A1 which is the
thinnest is the shortest, and the delay time of the transmission
portion 32A8 which is the thickest is the longest among the
transmission portions 32A1.about.32A8. Time difference between the
delay time of the transmission portion 32A1 and the delay time of
the transmission portion 32A8 corresponds to period of one cycle of
the RF signal radiated from the radiator 31.
Accordingly, it is possible to convert the mode of the RF signal
radiated from the radiator 31 and input to the transmission filter
32 into the RF signal having OAM of mode 1 by setting differences
of the thicknesses of the transmission portions 32A1.about.32A8
uniformly.
Herein, it is possible to reversely convert the RF signal having
OAM of mode 1 to which the mode conversion is performed by the
transmission filter 32 by using a transmission filter which has an
inverted phase (opposite phase) with respect to the phase of the
transmission filter 32.
In order to reversely convert the RF signal having OAM of mode 1 to
which the mode conversion is performed by the transmission filter
32 including the transmission portions 32A1.about.32A8 of which the
thicknesses become greater from the transmission portion 32A1 to
transmission portion 32A8 in this order in the counterclockwise
direction, a transmission filter including eight transmission
portions having thicknesses that become greater in the clockwise
direction in a manner opposite to that of transmission portions
32A1.about.32A8 may be used.
Accordingly, in a case where the antenna 30 including the
transmission filter 32 as illustrated in (B) of FIG. 12 is used as
the transmitting antenna Tx, an antenna including a transmission
filter having an inverted phase with respect to the transmission
filter 32 may be used as the corresponding receiving antenna
Rx.
The transmission filter 32 of mode 2 is illustrated in (C) of FIG.
12. The transmission filter 32 is divided into eight transmission
portions 32B1.about.32B8 that are arranged in a radial fashion with
respect to the center O2. The transmission portions 32B1.about.32B8
have fan-like shapes having 45 degree center angles, respectively,
as viewed from the positive Z axis direction. The transmission
portions 32B1.about.32B8 are arranged in the counterclockwise
direction in this order as viewed from the positive Z direction.
The transmission portion 32B1 and the transmission portion 32B8 are
arranged next to each other.
The transmission portions 32B1.about.32B8 have different
thicknesses. The transmission portions 32B1 and 32B5 are the
thinnest and the transmission portions 32B4 and 32B8 are the
thickest among the transmission portions 32B1.about.32B8. The
transmission portions 32B1.about.32B8 have the different
thicknesses so that the RF signal takes different periods of time
when the RF signal passes through the transmission portions
32B1.about.32B4 and 32B5.about.32B8.
In a dielectric substance, propagation speed of the RF signal
decreases compared to in the atmosphere. Accordingly, it is
possible to set delay times that are given to the RF signal by the
transmission portions 32B1.about.32B8 based on the different
thicknesses of the transmission portions 32B1.about.32B4 and
32B5.about.32B8.
The delay times of the transmission portions 32B1 and 32B5 that are
the thinnest are the shortest, and the delay times of the
transmission portions 32B4 and 32A8 that are the thickest are the
longest among the transmission portions 32B1.about.32B8.
Time difference between the delay time of the transmission portion
32B1 and the delay time of the transmission portion 32B4
corresponds to a period of one cycle of the RF signal radiated from
the radiator 31. Similarly, time difference between the delay time
of the transmission portion 32B5 and the delay time of the
transmission portion 32B8 corresponds to a period of one cycle of
the RF signal radiated from the radiator 31.
Herein, the thicknesses of the transmission portions 32B1 and 32B5
are the same, the thicknesses of the transmission portions 32B2 and
32B6 are the same, the thicknesses of the transmission portions
32B3 and 32B7 are the same, and the thicknesses of the transmission
portions 32B4 and 32B8 are the same.
Accordingly, it is possible to convert the mode of the RF signal
radiated from the radiator 31 and input to the transmission filter
32 into the RF signal having OAM of mode 2 by setting differences
of the thicknesses of the transmission portions 32B1.about.32A4 and
32B5.about.32B8 uniformly, respectively.
Herein, it is possible to reversely convert the RF signal having
OAM of mode 2 to which the mode conversion is performed by the
transmission filter 32 by using a transmission filter which has an
inverted phase (opposite phase) with respect to the phase of the
transmission filter 32.
Although, the transmission filter 32 divided into the eight
transmission portions 32A1.about.32A8 (see (B) of FIG. 12) and the
transmission filter 32 divided into the eight transmission portions
32B1.about.32B8 (see (C) of FIG. 12) are described, a number of
division of the transmission filter 32 may be an arbitrary number.
The more the divisional number of the transmission filter 32
becomes, the higher a resolution of the transmission filter 32
becomes. Accordingly, it becomes possible to obtain the RF signal
having OAM from the antenna 30 that is closer to the RF signal
having OAM obtained by the antennas 10 and 20 than the one obtained
by the transmission filter 32 having the divisional number of
eight.
Next, antenna apparatuses 100A and 100B according to variations of
the present embodiment will be described with reference to FIGS. 13
and 14. The antenna apparatuses 100A and 100B have configurations
in that the antennas 10 and 20 as illustrated in FIG. 11 and the
antenna 30 as illustrated in FIG. 12 are combined.
FIG. 13 is a diagram illustrating the antenna apparatus 100A
according to one variation of the present embodiment. FIG. 14 is a
diagram illustrating the antenna apparatus 100B according to
another variation of the present embodiment.
As illustrated in FIG. 13, the antenna apparatus 100A includes
antennas 130A, 130B, 140A and 140B and antenna reflectors 150A and
150B.
The antennas 130A, 130B, 140A and 140B correspond to the antenna 30
as illustrated in FIG. 12. The antennas 130A and 130B are used as
the transmitting antennas, and the antennas 140A and 140B are used
as the receiving antennas.
The antenna 130A includes a radiator 131A and a transmission filter
132A. The antenna 130B includes a radiator 131B and a transmission
filter 132B. The antenna 140A includes a radiator 141A and a
transmission filter 142A. The antenna 140B includes a radiator 141B
and a transmission filter 142B.
The antenna reflector 150A has a parabolic concaved cross section
truncated by a plane including the Z axis and is shaped in a circle
in plan view in a similar manner to the antenna reflector 12. The
antenna reflector 150B has a parabolic concaved cross section
truncated by a plane including the Z axis and is shaped in a circle
in plan view in a similar manner to the antenna reflector 12. The
reflector 150A has two optical axes as illustrated by solid lines.
The two optical axes correspond to optical axes of the transmission
filters 132A and 142A, respectively. Similarly, the reflector 150B
has two optical axes as illustrated by solid lines. The two optical
axes correspond to optical axes of the transmission filters 132B
and 142B, respectively.
The antennas 130A and 130B make a pair through the antenna
reflectors 150A and 150B. The optical axes of the antennas 130A and
130B correspond to each other via the antenna reflectors 150A and
150B as illustrated by the solid line in FIG. 13.
A total phase of a delay time (phase) which is given to the RF
signal by the transmission filter 132A of the antenna 130A and a
delay time (phase) which is given to the RF signal by the reflector
150A corresponds to a delay time which is used for converting the
planar wave RF signal radiated from the radiator 131A into the RF
signal having OAM of mode 1 on the optical axis between the
antennas 130A and 130B. Accordingly, the total phase corresponds to
.lamda. (2.pi.).
A total phase of a delay time (phase) which is given to the RF
signal by the transmission filter 132B of the antenna 130B and a
delay time (phase) which is given to the RF signal by the reflector
150B corresponds to a delay time which is used for reversely
converting the RF signal having OAM of mode 1 into the planar wave
RF signal which is input to the radiator 131B on the optical axis
between the antennas 130A and 130B. Accordingly, the total phase
corresponds to .lamda. (2.pi.).
Similarly, the antennas 140A and 140B make a pair through the
antenna reflectors 150A and 150B. The optical axes of the antennas
140A and 140B correspond to each other via the antenna reflectors
150A and 150B as illustrated by the solid line in FIG. 13.
A total phase of a delay time (phase) which is given to the RF
signal by the transmission filter 142A of the antenna 140A and a
delay time (phase) which is given to the RF signal by the reflector
150A corresponds to a delay time which is used for converting the
planar wave RF signal radiated from the radiator 141A into the RF
signal having OAM of mode 2 on the optical axis between the
antennas 140A and 140B. Accordingly, the total phase corresponds to
.lamda. (2.pi.).
A total phase of a delay time (phase) which is given to the RF
signal by the transmission filter 142B of the antenna 140B and a
delay time (phase) which is given to the RF signal by the reflector
150B corresponds to a delay time which is used for reversely
converting the RF signal having OAM of mode into the planar wave RF
signal which is input to the radiator 141B on the optical axis
between the antennas 140A and 140B. Accordingly, the total phase
corresponds to .lamda. (2.pi.).
The antenna apparatus 100A as described above can communicate
between the antennas 130A and 130B by using the RF signal having
OAM of mode 1, and can communicate between the antennas 140A and
140B by using the RF signal having OAM of mode 2.
Accordingly, it is possible to provide the antenna apparatus 100A
which can perform communications in the two channels. In the
antenna apparatus 100A, the communications in the two channels can
be performed in the same mode 1. The antenna apparatus 100A may
have a configuration in which the communications are performed in
more than two channels.
The reflectors 150A and 150B may be divided into reflectors 151A
and 151B and reflectors 152A and 152B included in the antenna
apparatus 100B, respectively, as illustrated in FIG. 14. In this
case, as illustrated in FIG. 14, the antenna apparatus 100B may not
include the transmission filters 132A, 132B, 142A and 142 that are
illustrated in FIG. 13.
In this case, the radiator 131A and the reflector 152A may
constitute an antenna used for mode 1 such as the antenna 10 as
illustrated in FIG. 11. Similarly, the radiator 131B and the
reflector 152B may constitute an antenna used for mode 1 such as
the antenna 10 as illustrated in FIG. 11.
Moreover, the radiator 141A and the reflector 152A may constitute
an antenna used for mode 2 such as the antenna 20 as illustrated in
FIG. 11. Similarly, the radiator 141B and the reflector 152B may
constitute an antenna used for mode 2 such as the antenna 20 as
illustrated in FIG. 11.
Each of optical axes of the reflectors 151A, 151B, 152A and 152B is
offset from the center axis of a parabolic cross section of a
parabola antenna. Accordingly, reflectors of offset parabola
antennas may be used as the reflectors 151A, 151B, 152A and
152B.
According to the present embodiment, it is possible to provide the
antenna apparatuses 100, 100A and 100B that have high channel
capacity regardless of the center-to-center distance d between the
transmitting antennas Tx1 and Tx2 and the receiving antennas Rx1
and Rx2.
Thus, it is possible to provide the antenna apparatuses 100, 100A
and 100B that can multiplex RF signal easily.
An antenna apparatus is provided, which is capable of multiplexing
RF signals easily.
The descriptions of the antenna apparatus of exemplary embodiments
have been provided heretofore. The present invention is not limited
to these embodiments, but various variations and modifications may
be made without departing from the scope of the present
invention.
The antenna apparatus is provided, which is capable of multiplexing
RF signals easily.
All examples and conditional language recited herein are intended
for pedagogical purposes to aid the reader in understanding the
invention and the concepts contributed by the inventors to
furthering the art, and are to be construed as being without
limitation to such specifically recited examples and conditions,
nor does the organization of such examples in the specification
relate to a showing of the superiority or inferiority of the
invention. Although the embodiments of the present invention have
been described in detail, it should be understood that the various
changes, substitutions, and alterations could be made hereto
without departing from the spirit and scope of the invention.
* * * * *
References