U.S. patent number 9,590,606 [Application Number 14/318,067] was granted by the patent office on 2017-03-07 for semiconductor device having duty correction circuit.
This patent grant is currently assigned to Micron Technology, Inc.. The grantee listed for this patent is MICRON TECHNOLOGY, INC.. Invention is credited to Katsuhiro Kitagawa, Hiroki Takahashi.
United States Patent |
9,590,606 |
Kitagawa , et al. |
March 7, 2017 |
Semiconductor device having duty correction circuit
Abstract
Disclosed herein is a device includes a duty correction circuit
adjusting a duty ratio of a first clock signal based on a duty
control signal to generate a second clock signal; a delay line
delaying the second clock signal to generate a third clock signal;
and a duty cycle detector detecting the duty ratio of the second
clock signal to generate the duty control signal in a first mode,
and detecting the duty ratio of the third clock signal to generate
the duty control signal in a second mode.
Inventors: |
Kitagawa; Katsuhiro (Tokyo,
JP), Takahashi; Hiroki (Tokyo, JP) |
Applicant: |
Name |
City |
State |
Country |
Type |
MICRON TECHNOLOGY, INC. |
Boise |
ID |
US |
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Assignee: |
Micron Technology, Inc. (Boise,
ID)
|
Family
ID: |
52114994 |
Appl.
No.: |
14/318,067 |
Filed: |
June 27, 2014 |
Prior Publication Data
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Document
Identifier |
Publication Date |
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US 20150002201 A1 |
Jan 1, 2015 |
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Foreign Application Priority Data
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Jun 27, 2013 [JP] |
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2013-134497 |
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Current U.S.
Class: |
1/1 |
Current CPC
Class: |
H03K
5/1565 (20130101) |
Current International
Class: |
H03K
5/156 (20060101) |
Field of
Search: |
;327/175 |
References Cited
[Referenced By]
U.S. Patent Documents
Foreign Patent Documents
Primary Examiner: Jager; Ryan
Attorney, Agent or Firm: Dorsey & Whitney LLP
Claims
What is claimed is:
1. A semiconductor device comprising: a duty correction circuit
adjusting a duty ratio of a first clock signal based on a duty
control signal to generate a second clock signal; an adjustable
delay line delaying the second clock signal by an adjustable delay
to generate a third clock signal, wherein the adjustable delay is
based on a phase of the first clock signal and a phase of the third
clock signal; and a duty cycle detector detecting the duty ratio of
the second clock signal to generate the duty control signal
indicative of a first mode, and detecting the duty ratio of the
third clock signal to provide the duty control signal indicative of
a second mode for adjusting the duty ratio of the third clock
signal, wherein the duty correction circuit adjusting the duty
ratio of the third clock signal based on the generated duty control
signal indicative of the second mode for adjusting the duty ratio
of the third clock signal.
2. The semiconductor device as claimed in claim 1, wherein the duty
cycle detector operates in the first mode in response to a reset
signal, and then shifts to the second mode.
3. The semiconductor device as claimed in claim 1, wherein the duty
control signal includes a plurality of control signals, the duty
correction circuit includes a plurality of clocked inverters that
are connected in parallel, and the plurality of clocked inverters
are independently controlled by the plurality of control
signals.
4. The semiconductor device as claimed in claim 3, wherein each of
the clocked inverters includes an input node, an output node, a
pull-up circuit that pulls up the output node based on a level of
the input node, and a pull-down circuit that pulls down the output
node based on a level of the input node, and at least one of the
pull-up circuit and the pull-down circuit is selectively activated
by a corresponding one of the control signals.
5. A semiconductor device comprising: a duty correction circuit
adjusting a duty ratio of a first clock signal based on a duty
control signal to generate a second clock signal; an adjustable
delay line delaying the second clock signal by an adjustable delay
to generate a third clock signal, wherein the adjustable delay is
based on a phase of the first clock signal and a phase of the third
clock signal; and a duty cycle detector detecting the duty ratio of
the second clock signal to generate the duty control signal in a
first mode, and detecting the duty ratio of the third clock signal
to generate the duty control signal in a second mode, wherein the
duty cycle detector operates in the first mode in response to a
reset signal, and then shifts to the second mode, and wherein the
duty cycle detector shifts from the first mode to the second mode
when the duty ratio of the second clock signal reaches a
predetermined value.
6. The semiconductor device as claimed in claim 5, wherein the
predetermined value is approximately 50%.
7. A semiconductor device comprising: a duty correction circuit
adjusting a duty ratio of a first clock signal based on a duty
control signal to generate a second clock signal; an adjustable
delay line delaying the second clock signal by an adjustable delay
to generate a third clock signal, wherein the adjustable delay is
based on a phase of the first clock signal and a phase of the third
clock signal; and a duty cycle detector detecting the duty ratio of
the second clock signal to generate the duty control signal in a
first mode, and detecting the duty ratio of the third clock signal
to generate the duty control signal in a second mode, wherein the
duty cycle detector updates the duty control signal in a first
cycle in the first mode, and updates the duty control signal in a
second cycle that is longer than the first cycle in the second
mode.
8. A semiconductor device comprising: a duty correction circuit
adjusting a duty ratio of a first clock signal based on a duty
control signal to generate a second clock signal; an adjustable
delay line delaying the second clock signal by an adjustable delay
to generate a third clock signal, wherein the adjustable delay is
based on a phase of the first clock signal and a phase of the third
clock signal; and a duty cycle detector detecting the duty ratio of
the second clock signal to generate the duty control signal in a
first mode, and detecting the duty ratio of the third clock signal
to generate the duty control signal in a second mode, wherein the
duty correction circuit adjusts the duty ratio of the first clock
signal by a first pitch when the duty cycle detector operates in
the first mode, and the duty correction circuit adjusts the duty
ratio of the first clock signal by a second pitch smaller than the
first pitch when the duty cycle detector operates in the second
mode.
9. A semiconductor device comprising: a duty correction circuit
adjusting a duty ratio of a first clock signal based on a duty
control signal to generate a second clock signal; a delay line
delaying the second clock signal to generate a third clock signal;
a duty cycle detector detecting the duty ratio of the second clock
signal to generate the duty control signal in a first mode, and
detecting the duty ratio of the third clock signal to generate the
duty control signal in a second mode; a replica circuit delaying
the third clock signal to generate a fourth clock signal; a phase
determination circuit comparing a phase of the first clock signal
with a phase of the fourth clock signal to generate a phase
determination signal; and a delay line control circuit updating a
count value based on the phase determination signal, wherein the
delay line controls an amount of delay in accordance with the count
value.
10. The semiconductor device as claimed in claim 9, further
comprising: an external terminal; and an output circuit driving the
external terminal in synchronization with the third clock signal,
wherein a signal waveform that emerges on the external terminal
substantially matches a signal waveform of the fourth clock
signal.
11. A semiconductor device comprising: a duty correction circuit
inserted into a propagation path of a clock signal and adjusting a
duty ratio of a clock signal based on a first duty control signal;
and a duty cycle detector detecting a duty ratio of the clock
signal output from the duty correction circuit to generate the
first duty control signal, wherein in a first mode, the duty cycle
detector detects the duty ratio of the clock signal that emerges on
a first node of the propagation path so that a feedback loop
containing the duty correction circuit and the duty cycle detector
has a first loop length, in a second mode, the duty cycle detector
detects the duty ratio of the clock signal that emerges on a second
node of the propagation path that is different from the first node
so that the feedback loop has a second loop length that is longer
than the first loop length, and wherein the duty cycle detector
generates a second duty control signal indicative of the second
mode for the duty correction circuit to adjust the duty ratio of
the clock signal that emerges on the second node; and a delay line
delaying the clock signal, the delay line includes a coarse delay
line for coarse adjustment and a fine delay line for fine
adjustment and the delay line being inserted between the first and
second nodes of the propagation path.
12. A semiconductor device comprising: a duty correction circuit
adjusting a duty ratio of a first clock signal based on a first
duty control signal to generate a second clock signal, wherein the
duty correction circuit adjusting the duty ratio of the first clock
signal based on the first duty control signal indicating that a
coarse adjustment circuit adjusts the ratio of the first clock
signal in a first mode; an adjustable delay line delaying the
second clock signal by an adjustable delay to generate a third
clock signal, wherein the adjustable delay is based on a phase of
the first clock signal and a phase of the third clock signal; and a
duty detection unit receiving the second clock signal and the third
clock signal, the duty detection unit providing a second duty
control signal indicative of the duty correction circuit adjusting
the duty ratio of the third clock signal, wherein the duty
correction circuit adjusting the duty ratio of the third clock
signal based on the second duty control signal indicating that a
fine adjustment circuit adjusts the duty ratio of the third clock
signal in a second mode.
13. The semiconductor device as claimed in claim 12, wherein the
duty detection unit includes a selection circuit that selects one
of the second clock signal and the third clock signal, and a duty
cycle detector that detects a duty ratio of selected one of the
second and third clock signals selected by the selection
circuit.
14. The semiconductor device as claimed in claim 13, wherein the
duty cycle detector starts detecting the duty of the second or
third clock signal in response to a reset signal.
15. The semiconductor device as claimed in claim 13, wherein the
selection circuit selects the third clock signal after selecting
the second clock signal.
16. The semiconductor device as claimed in claim 12, further
comprising a delay line control circuit comparing a phase of the
first clock signal with a phase of the third clock signal to
control a delay amount of the delay line.
17. A semiconductor device as claimed in claim 12, wherein the
delay line includes a coarse delay line for coarse adjustment and a
fine delay line for fine adjustment.
Description
BACKGROUND
Field of the Invention
The present invention relates to a semiconductor device, and
particularly to a semiconductor device that includes a duty
correction circuit for adjusting a duty ratio of a clock
signal,
Description of Related Art
The type called DDR (Double Data Rate) is the mainstream of DRAM
(Dynamic Random Access Memory), which is a typical semiconductor
memory device. The DDR-type DRAM is designed to input or output
data in synchronization with both rising and falling edges of the
clock signal. Therefore, the duty ratio of the clock signal needs
to be precisely kept at 50%. For that purpose, a duty correction
circuit is frequently used (See Japanese Patent Application
Laid-Open No. 2008-210436).
The duty correction circuit is usually incorporated into a DLL
(Delay Locked Loop) circuit that controls the phase of the clock
signal. The DLL circuit includes a delay line that delays the clock
signal. The duty ratio of the clock signal that has passed through
the delay line is detected by a duty cycle detector, and the
results thereof are fed back to the duty correction circuit, which
then adjust the duty ratio of the clock signal.
However, the delay line has a relatively large amount of inherent
delay. Therefore, the loop length of a feedback loop consisting of
the duty correction circuit and the duty cycle-detector is
relatively long. This leads to a decrease in feedback
responsiveness in duty-control. The problem is that it takes a long
time to reach a desired duty ratio.
SUMMARY
In one embodiment, there is provided a semiconductor device that
includes a duty correction circuit adjusting a duty ratio of a
first clock signal based on a duty control signal to generate a
second clock signal; a delay line delaying the second clock signal
to generate a third clock signal; and a duty cycle detector
detecting the duty ratio of the second clock signal to generate the
duty control signal in a first mode, and detecting the duty ratio
of the third clock signal to generate the duty control signal in a
second mode.
In another embodiment, there is provided a semiconductor device
that includes a duty correction circuit inserted into a propagation
path of a clock signal and adjusting a duty ratio of the clock
signal based on a duty control signal; and a duty cycle detector
detecting a duty ratio of the clock signal output from the duty
correction circuit to generate the duty control signal. In a first
mode, the duty cycle detector detects the duty ratio of the clock
signal that emerges on a first node of the propagation path so that
a feedback loop containing the duty correction circuit and the duty
cycle detector has a first loop length. In second mode, the duty
cycle detector detects the duty ratio of the clock signal that
emerges on a second node of the propagation path that is different
from the first node so that the feedback loop has a second loop
length that is longer than the first loop length.
In still another embodiment, there is provided a semiconductor
device that includes a duty correction circuit adjusting a duty
ratio of a first clock signal based on a duty control signal to
generate a second clock signal; a delay line delaying the second
clock signal to generate a third clock signal; and a duty detection
unit receiving the second clock signal and the third clock
signal.
According to the present invention, the configurations of the
feedback loop can be switched depending on the mode. Therefore, the
feedback responsiveness in duty-control can be increased.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a block diagram indicative of an embodiment of a general
configuration of a semiconductor device according to a preferred
embodiment of the present invention;
FIG. 2 is a block diagram indicative of an embodiment of a
configuration of the DLL circuit shown in FIG. 1;
FIG. 3 is a block diagram indicative of an embodiment of a
configuration of a duty correction circuit and a DCC control
circuit shown in FIG. 2;
FIG. 4 is a timing chart indicative of an embodiment of a duty
adjustment operation by the DLL circuit shown in FIG. 1;
FIG. 5 is a timing chart indicative of another embodiment of a duty
adjustment operation by the DLL circuit shown in FIG. 1
FIG. 6 is a block diagram indicative of an embodiment of a
configuration of the duty correction circuit shown in FIG. 2;
FIG. 7 is a circuit diagram of indicative of an embodiment of a
duty adjustment unit shown in FIG. 6;
FIG. 8 is a circuit diagram of indicative of an embodiment of a
clocked inverter according to a modified example;
FIG. 9 is a block diagram indicative of an embodiment of a circuit
that generates the fuse signals;
FIG. 10 is a circuit diagram of indicative of an embodiment of a
synthesis circuit 155 shown in FIG. 6;
FIG. 11 is a block diagram schematically indicative of an
embodiment of a configuration of the DCC control circuit shown in
FIG. 2;
FIG. 12 is a schematic diagram indicative of an embodiment of a
relationship between the values of bits of the duty detection
signal shown in FIG. 11 and drive capability when the duty ratio is
less than 50%;
FIG. 13 is a schematic diagram indicative of an embodiment of a
relationship between the values of bits of the duty detection
signal shown in FIG. 11 and drive capability when the duty ratio is
greater than 50%;
FIG. 14 is a schematic diagram for explaining adjustment amounts by
duty adjustment units shown in FIG. 6, when the duty ratio is less
than 50%;
FIG. 15 is a waveform diagram indicative of an embodiment of
changes in the duty ratio of the internal clock signals when the
duty ratio is less than 50%;
FIG. 16 is a schematic diagram for explaining adjustment amounts by
duty adjustment units shown in FIG. 6, when the duty ratio is
greater than 50%;
FIG. 17 is a waveform diagram indicative of an embodiment of
changes in the duty ratio of the internal clock signals when the
duty ratio is greater than 50%;
FIG. 18A is a waveform diagram indicative of an embodiment of
operation of the synthesis circuit when the duty ratio is less than
50%;
FIG. 18B is a waveform diagram indicative of an embodiment of
operation of the synthesis circuit, when the duty ratio is greater
than 50%;
FIG. 19 is a block diagram indicative of an embodiment of a
configuration of a duty correction circuit according to a first
modified example;
FIG. 20 is a block diagram indicative of an embodiment of a
configuration of a duty correction circuit according to a second
modified example; and
FIG. 21 is a block diagram indicative of an embodiment of a
configuration of a duty correction circuit according to a third
modified example.
DETAILED DESCRIPTION OF THE EMBODIMENTS
Preferred embodiments of the present invention will be explained
below in detail with reference to the accompanying drawings.
Referring now to FIG. 1, the semiconductor device 10 according to
the preferred embodiment of the present invention is a DRAM and
includes the memory cell array 11. In the memory cell array 11, a
plurality of word lines WL and a plurality of bit lines BL
intersecting with each other are provided and a plurality of memory
cells MC are arranged at intersections thereof, respectively.
Selection of a word line WL is performed by a row decoder 12 and
selection of a bit line BL is performed by a column decoder 13. The
bit lines BL are connected to corresponding sense amplifiers SA in
a sense circuit 14, respectively, and a bit line BL selected by the
column decoder 13 is connected to the amplifier circuit 15 through
the corresponding sense amplifier SA.
Operations of the row decoder 12, the column decoder 13, the sense
circuit 14, and the amplifier circuit 15 are controlled by an
access control circuit 20. An address signal ADD, a command signal
CMD, external clock signals CK and CKB, a clock enable signal CKE,
and the like are supplied to the access control circuit 20 through
external terminals 21 to 24. The external clock signals CK and CKB
are signals complementary to each other. The access control circuit
20 controls the row decoder 12, the column decoder 13, the sense
circuit 14, the amplifier circuit 15, and a data input/output
circuit 30 based on these signals.
Specifically, when the command signal CMD indicates the active
command, the address signal ADD is supplied to the row decoder 12.
In response thereto, the row decoder 12 selects a word line WL
indicated by the address signal ADD and accordingly corresponding
memory cells MC are connected to the corresponding bit lines BL,
respectively. The access control circuit 20 then activates the
sense circuit 14 in a predetermined timing.
On the other hand, when the command signal CMD indicates the read
command or the write command, the address signal ADD is supplied to
the column decoder 13. In response thereto, the column decoder 13
connects a bit line BL indicated by the address signal ADD to the
amplifier circuit 15. Accordingly, at the time of a read operation,
read data DQ that are read from the memory cell array 11 through
the corresponding sense amplifier SA are output to outside from the
data terminal 31 through the amplifier circuit 15 and the data
input/output circuit 30. At the time of a write operation, write
data DQ that are supplied from outside through the data terminal 31
and the data input/output circuit 30 are written into the
corresponding memory cells MC through the amplifier circuit 15 and
the sense amplifier SA.
The access control circuit 20 includes a DLL circuit 100. The DLL
circuit 100 generates an internal clock signal LCLK that is
phase-control led based on the external clock signals CK and CKB.
The DLL circuit 100 includes a delay line (DL) 110 that delays the
internal clock signal LCLK and a duty correction circuit (Dee) 150
that adjusts a duty ratio to 50%. The details of the DLL circuit
100 will be described later. The internal clock signal LCLK is
supplied to an output circuit 30a included in the data input/output
circuit 30. The read data DQ and a data strobe signal DQS are
respectively output from the data terminal 31 and a data strobe
terminal 32 in synchronism with the internal clock signal LCLK.
Each of the foregoing circuit blocks uses a predetermined internal
voltage as its operating power supply. Such internal power supplies
are generated by a power supply circuit 40. The power supply
circuit 40 receives an external potential VDD and a ground
potential VSS that are supplied through power supply terminals 41
and 42, respectively. Based on the potentials, the power supply
circuit 40 generates internal voltages VPP, VPERI, VARY, etc. The
internal potential VPP is generated by boosting the external
potential VDD. The internal potentials VPERI and VARY are generated
by stepping down the external potential VDD.
The internal voltage VPP is mainly used in the row decoder 12. The
row decoder 12 drives a word line WL selected based on the address
signal ADD to the VPP level, thereby making the cell transistors
included in the memory cells MC conductive. The internal voltage
VARY is mainly used in the sense circuit 14. The sense circuit 14,
when activated, drives either one of each pair of bit lines to the
VARY level and the other to the VSS level, thereby amplifying read
data that is read out. The internal voltage VPERI is used as the
operating voltage of most of the peripheral circuits such as the
access control circuit 20. Using the internal voltage VPERI lower
than the external voltage VDD as the operating voltage of the
peripheral circuits reduces power consumption of the semiconductor
device 10.
Turning to FIG. 2, the DLL circuit 100 includes a delay line 110
that, generates an internal clock signal LCLK by delaying an
internal clock signal PCLK1. The internal clock signal PCLK1 is a
signal which an internal clock signal PCLK0 output from a clock
receiver 25 which, receives the external clock signals CK and CKB
passed through coarse the duty correction circuit 150. The delay
line 110 has a constitution in which a coarse delay line (CDL) 111
having a coarse adjustment pitch of delay amount and a fine delay
line (FDL) 112 having a fine adjustment pitch of delay amount are
connected in series. The internal clock signal LCLK output from the
delay line 110 is supplied to the output circuit 30a via a buffer
113 and a clock tree 114 and as described above, used as a timing,
signal for defining an output timing of the read data DQ or the
data strobe signal DQS.
The internal clock signal LCLK is supplied to a replica circuit
120. The replica circuit 120 is a circuit having substantially the
same delay time as that of a circuit group which consists of the
buffer 113, the clock tree 114, and the output circuit 30a, and
receives the internal clock signal LCLK to output a replica clock
signal RCLK. Because the output circuit 30a outputs the read data
DQ and the data strobe signal DQS in synchronization with the
internal clock signal LCLK, the replica clock signal RCLK output
from the replica circuit 120 is accurately synchronized with the
read data DQ and the data strobe signal DQS. In the DRAM, the read
data DQ and the data strobe signal DQS needs to be accurately
synchronized with the external clock signals CK and CKB, and when
there is a phase shift between the read data DQ and the data strobe
signal DQS and the external clock signals CK and CKB, the phase
shift needs to be detected and corrected. The detection of the
phase shift is performed by the phase determination circuit 130,
and a result of the determination is output as a phase
determination signal PD.
The phase determination signal PD is supplied to a delay line
control circuit 140. The delay line control circuit 140 is a
circuit that counts up or down a count value CNT based on the phase
determination signal PD to control an amount of delay of the delay
line 110. More specifically, if the phase determination signal PD
indicates that the phase of the replica clock signal RCLK is behind
the phase of the internal clock signal PCLK0, the delay line
control circuit 140 counts down the count value CNT to decrease the
amount of delay of the delay line 110. If the phase determination
signal PD indicates that the phase of the replica clock signal RCLK
is ahead of the phase of the internal clock signal PCLK0, the delay
line control circuit 140 counts up the count value CNT to increase
the amount of delay of the delay line 110. The amount of delay of
the delay line 110 is adjusted through such an operation, so that
the replica clock signal RCLK and the internal clock signal PCLK0
are in phase with each other. When the replica clock signal RCLK
and the internal clock signal PCLK0 are in phase with each other,
the read data DQ and the data strobe signal DQS are synchronized
exactly with the external clock signals CK and CKB.
As shown in FIG. 2, the DLL circuit 100 includes the duty
correction circuit ISO that adjusts a duty ratio. In the present
embodiment, the duty correction circuit 150 is inserted before the
delay line 110. The duty correction circuit 150 adjusts the duty
ratio of the internal clock signal PCLK0 output from the clock
receiver 25 to generate the internal clock signal PCLK1.
According to the present embodiment, a selector 180 selects the
internal clock signal PCLKL1 or LCLK. The duty ratio of the
selected, internal clock signal PCLK1 or LCLK is detected by a duty
cycle detector (DCD) 160, which, thereby generates a duty detection
signal D1. A position where the internal clock signal LCLK is
detected by the duty cycle detector 160 is preferably placed closer
to the output circuit 30a. According to the present, embodiment,
the duty ratio of the internal clock signal LCLK that has passed
through the clock tree 114 is detected. However, the present
invention is not limited to that configuration. As indicated by
broken line in FIG. 2, the duty ratio of the internal clock signal
LCLK may be detected before the internal clock signal LCLK passes
through the clock tree 114.
The selection by the selector 180 is based on a reset signal RST
and a switch signal SEL. Although the details will be described
later, the internal clock signal PCLK1 is selected when the reset
signal RST is activated. Then, the internal clock signal LCLK is
selected when the switch, signal SEL is activated. The state where
the internal clock signal PCLK1 is selected is referred to as
"first mode"; the state where the internal clock signal LCLK is
selected is referred to as "second mode". The reset signal RST is a
signal that is activated in such cases as when the DLL circuit 100
is initialised. The reset signal RST is generated inside the access
control circuit 20 shown in FIG. 1. The switch signal SSL is
activated by the duty cycle detector 160 when the duty ratio
exceeds a predetermined value. More specifically, when the duty
ratio is changed from less than 50% to more than 50%, or when the
duty ratio is changed from more than 50% to less than 50%, the
switch signal SEL is activated.
The reset signal RST is also supplied to the duty cycle detector
160. Although the details will be described later, the duty cycle
detector ISO updates the duty detection signal D1 in a first cycle
when the first mode is selected in response to activation of the
reset signal RST. After that, when the second mode starts in
response to activation of the switch signal SEL, the duty cycle
detector 160 updates the duty detection signal D1 in a second
cycle, which is longer than the first cycle.
The duty detection signal D1 detected by the duty cycle detector
160 is supplied to a DCC control circuit 170. The DCC control
circuit 170 receives the duty detection signal D1, and generates a
duty control signal D2 based on the duty detection signal D1, and
supplies the duty control signal D2 to the duty correction circuit
150. The duty correction circuit 150 adjusts the duty ratio of the
internal clock signal PCLK0 based on the duty control signal D2,
and then outputs this signal as the internal clock signal
PCLK1.
Turning to FIG. 3, the duty correction circuit ISO has a structure
in which a coarse adjustment circuit 150X and a fine adjustment
circuit 150Y are connected in series. The coarse adjustment circuit
150X is a circuit that adjusts the duty ratio of the internal clock
signal PCLK0 with a relatively coarse pitch. The coarse adjustment
circuit 150X is controlled by a count value CMTX of a counter 170X
that is included in the DCC control circuit 170. The fine
adjustment circuit 150Y is a circuit that adjusts the duty ratio of
the internal clock signal PCLR0 with a relatively fine pitch. The
fine adjustment circuit 150Y is controlled by a count value CNTY of
a counter 170Y that is included in the DCC control circuit 170.
When the first mode is selected in response to activation of the
reset signal RST, the DCC control circuit 170 updates the count
value CNTX of the counter 170X based on the duty detection signal
D1. Therefore, in the first mode, the coarse adjustment circuit
150X is used in adjusting the duty ratio. Then, when the second
mode starts in response to activation of the switch signal SHL, the
DCC control circuit 170 updates the count value CNTY of the counter
170Y based on the duty detection signal D1. Therefore, in the
second mode, the fine adjustment circuit 150Y is used in adjusting
the duty ratio.
Incidentally, more detailed configuration of the duty correction
circuit 150 is disclosed in US Patent Application Publication No.
2013/0207701 A1, the entire contents of which are incorporated
herein by reference.
Turning to FIG. 4, at time t1, the reset signal RST is activated;
the first mode therefore is selected. In the example shown in FIG.
4, at time t1, the duty ratio of the internal clock signal PCLK1 is
less than 50%. Accordingly, the duty correction circuit 150
performs control so as to increase the duty ratio. In the first
mode, the duty ratio is adjusted by the duty correction circuit 150
in each first cycle T1. The first cycle T1 is equal to a 16-clock
cycle (16 tCK), for example.
In that manner, the duty ratio of the internal clock signal PCLK1
is increased, in each first cycle T1, and the value thereof
gradually approaches 50%. In the first mode, the coarse adjustment
circuit 150X shown in FIG. 3 is used for duty adjustment.
Therefore, the duty adjustment amount in each first cycle T1 is
PT1. At time t2, when the duty ratio of the internal clock signal
PCLK1 exceeds 50%, the switch signal SEL is activated, and the DLL
circuit 100 shifts to the second mode.
After the DLL circuit 100 shifts to the second mode, the selector
180 selects the internal clock signal LCLK. Therefore, the duty
cycle detector 160 detects the duty ratio of the internal clock
signal LCLK instead of the internal clock signal PCLK1. In the
second mode, the duty correction circuit 150 adjusts the duty ratio
in each second cycle T2 (>T1). The second cycle T2 is a 32-clock
cycle (32 tCK), for example. The reason the cycle T2 in the second
mode is set longer than the cycle T1 in the first mode is that the
loop length of a feedback loop
(150.fwdarw.110.fwdarw.113.fwdarw.114.fwdarw.180.fwdarw.160.fwdarw.170.fw-
darw.150) in the second mode is longer than the loop length of a
feedback loop (150.fwdarw.180.fwdarw.160.fwdarw.170.fwdarw.150) in
the first mode; the inherent delay of the feedback loop in the
second mode therefore is larger than the inherent delay of the
feedback loop in the first mode.
In the second mode, the fine adjustment circuit 150Y shown in FIG.
3 is used for duty adjustment. Therefore, the duty adjustment
amount in each second cycle T2 is PT2 (<PT1). Therefore, in each
second cycle T2, the duty ratio of the internal clock signal LCLK
is changed by the adjustment amount PT2 so as to approach 50%.
Finally, the duty ratio becomes stable at around 50%.
In that manner, according to the present embodiment, the DLL
circuit 100 operates in the first mode in an early stage of
duty-control. Then, when the duty ratio of the internal clock
signal PCLK1 has exceeded 50%, the DLL circuit 100 shifts to the
second mode. Therefore, in the early stage in which the duty ratio
likely would be far away from 50%, the duty ratio can be quickly
changed. Moreover, the internal clock signal PCLK1 whose duty ratio
is close to 50% can be input to the delay line 110. Therefore, it
is possible to prevent the pulse from being lost as the internal
clock signal passes through the delay line 110. After the DLL
circuit 100 shifts to the second mode, the duty ratio of the
internal clock signal LCLK, which is the output signal of the DLL
circuit 100, can be precisely controlled so as to be near 50%.
Incidentally, as the DLL circuit 100 shifts from the first mode to
the second mode, the duty-ratio detection target is shifted from
the internal clock signal PCLK1 to the internal clock signal LCLK.
Therefore, as shown in FIG. 5, the continuity of the duty ratio
detected might be lost immediately after the DLL circuit 100 shifts
to the second mode. However, at a time when the DLL circuit 100
shifts from the first mode to the second, mode, the duty ratio of
the internal clock signal PCLK1 input to the delay line 110 is
substantially equal to 50%. Therefore, immediately after the DLL
circuit 100 shifts to the second mode, the duty ratio of the
internal clock signal LCLK is expected to foe close to 50%.
However, if the duty ratio of the internal clock signal. LCLK is
far away from 50% immediately after the DLL circuit 100 shifts to
the second mode, first the operation of the coarse adjustment
circuit 150X may be performed, and then the operation of the fine
adjustment circuit 150Y may be performed.
A circuit example of the duty correction circuit 150 will foe given
in more detail. However, the circuit configuration of the duty
correction circuit 150 used in the present invention is not limited
to this configuration.
Turning to FIG. 5, the duty correction circuit 150 includes four
duty adjustment units 151 to 154 and a synthesis circuit 155. The
duty adjustment units 151 and 152 are connected in series, forming
a propagation path A. The duty adjustment units 153 and 154 are
connected in series, forming a propagation path B. The propagation
paths A and B run parallel to each other. The Internal clock signal
PCLKA1 output from the propagation path A, and the internal clock
signal PCLKB1 output from the propagation path B are input to the
synthesis circuit 155, which then outputs the internal clock signal
PCLK1. The duty adjustment units 151 to 154 are equivalent to the
coarse adjustment circuit 150X shown in FIG. 3, and the synthesis
circuit 155 is equivalent to the fine adjustment circuit 150Y shown
in FIG. 3.
The duty adjustment units 151 to 154 have the same circuit
configuration; each unit is designed to change the slew rate of
either the rising or failing edge of the internal clock signal.
Different control signals are used for the adjustment of slew rates
by the duty adjustment units 151 to 154. More specifically, control
signals P1 and N1 are used for the duty adjustment unit 151;
control signals P2 and N2 are used for the duty adjustment unit
152; control signals P3 and N3 are used for the duty adjustment
unit 153; and control signals P4 and N4 are used for the duty
adjustment unit 154. Those control signals P1 to P4 and N1 to K4
are part (e.g., count value CNTX) of the above-described duty
control signal D2.
Turning to FIG. 7, the duty adjustment unit 151 includes six
clocked inverters CV1, CV2, CV4, CV8, CV2F and CV4F, which are
connected in parallel; the duty adjustment unit 151 receives the
internal clock signal PCLK0 and then generates the internal clock
signal PCLKA0. Those clocked inverters have the same circuit
configuration; only the configuration of the clocked inverter CV1
therefore will be described. The clocked inverter CV1 includes
P-channel MOS transistors MP11 and MP12 and N-channel MOS
transistors MN12 and MN11, which are connected in series in that
order between a power supply wire VL, to which internal potential
VPERI is supplied, and a power supply wire SL, to which ground
potential VSS is supplied.
The gate electrodes of the transistors MP12 and MN12 are connected
in common, forming an input node n1 to which the internal clock
signal PCLK0 is supplied. The drains of the transistors MP12 and
MN12 are connected in common, forming an output node n2 from which
the internal clock signal PCLKA0 is output.
To the gate electrode of the transistor MP11, a control signal P11,
which is part of the control signal P1, is supplied. When the
control signal P11 is activated to low level, the clocked inverter
CV1 is therefore able to pull up the output node n2 based on the
level of the input node n1. When the control signal P11 is
inactivated to high level, the clocked inverter CV1 is unable to
pull up the output node n2. In this manner, the transistors MP11
and MP12 that are connected in series make up a pull-up circuit UP,
which is selectively activated by the control signal P11.
Similarly, to the gate electrode of the transistor MN11, a control
signal N11, which is part of the control signal N1, is supplied.
When the control signal M11 is activated to high level, the clocked
inverter CV1 is therefore able to pull down the output node n2
based on the level of the input node n1. When the control signal
N11 is inactivated to low level, the clocked inverter CV1 is unable
to pull down the output node n2. In this manner, the transistors
MN11 and MN12 that are connected in series make up a pull-down
circuit DN, which is selectively activated by the control signal
N11.
In that manner, the clocked inverter CV1 can separately control the
pull-up circuit UP and the pull-down circuit DN. This configuration
is different from that of a typical clocked inverter.
The other clocked inverters CV2, CV4, CV8, CV2F and CV4F have the
same configuration as the above clocked inverter CV1 except that
other corresponding control signals are input to the clocked
inverters CV2, CV4, CV8, CV2F and CV4P.
In this case, the drive capabilities of the clocked inverters CV1,
CV2, CV4 and CV8 are weighted by the power of 2. More specifically,
if the drive capability of the clocked inverter CV1 is 1 DC, the
drive capabilities of the clocked inverters CV2, CV4 and CV8 are 2
DC, 4 DC and 8 DC, respectively. Accordingly, based on the control
signals P11, P12, P14 and P18 that make up the control signal P1,
the pull-up capability can foe controlled in 16 stages (0 DC to 15
DC). Furthermore, based on the control signals N11, N12, N14 and
N18 that make up the control signal N1, the pull-down capability
can be controlled in 16 stages (0 DC to 15 DC). The control signals
P1 and N1 are generated by the DCC control circuit 170 based on the
duty detection signal D1 output from the duty cycle detector
160.
Incidentally, if restrictions in the process make it difficult to
make transistors whose drive capability is less than 2 DC, the
transistors MP11 and MN11 each may be made up of two transistors
that are connected in series, as shown in FIG. 8. In the example
shown in FIG. 8, the two P-channel MOS transistors MP11a and MP11b
that make up the transistor MP11 each have a drive capability of 2
DC; because the P-channel MOS transistors MP11a and MP11b are
connected in series, it is possible to obtain a drive capability of
IDC. Similarly, the two N-channel MOS transistors MN11a and MN11b
that make up the transistor MN11 each have a drive capability of 2
DC; because the N-channel MOS transistor's MN11a and MN11b are
connected in series, it is possible to obtain a drive capability of
IDC.
Meanwhile, the clocked inverters CV2F and CV4F are circuits that
offer fixed drive capabilities to the duty adjustment unit 151; the
drive capabilities of the clocked inverters CV2F and CV4F are 2 DC
and 4 DC, respectively. Fuse signals FP and FN are used to select
whether or not to activate the clocked inverters CV2P and CV4F. For
example, the fuse signals FP12 and FN12 are activated to activate
only the clocked inverter CV2F; the fuse signals FP14 and FN14 are
activated to activate only the clocked inverter CV4F.
As for the clocked inverters CV2F and CV4F, there is no need to
separately control the pull-up circuit UP and the pull-down circuit
DM; the pull-up circuit UP and the pull-down circuit DM may be
controlled in common as in the case of a typical clocked inverter.
In this case, in the activated clocked inverters CV2F and CV4F, it
is possible to both pull up and pull down. In the inactivated
clocked inverters CV2F and CV4F, the output is in a high impedance
state.
Turning to FIG. 9, the fuse signals FP and FN are stored in a fuse
circuit 181. The fuse circuit 181 is a nonvolatile storage circuit
that includes optical fuse elements, electric ail fuse elements
(anti-fuse elements), and the like. In a production stage,
programming of the fuse signals FP and FN is performed. The fuse
signals FP and FN that are output from the fuse circuit 181 are
supplied to the duty correction circuit 150 via a selector 183.
In order to make the fuse signals FP and FN variable during a test
operation, a test mode circuit 182 is provided. The test mode
circuit 182 is able to output any test fuse signals TFP and TFN. By
activating a test signal TEST, the test fuse signals TFP and TFN
can be supplied to the duty correction circuit 150 via the selector
183.
In that manner, whether or not to use the clocked inverters CV2F
and CV4F is fixed except during the test operation. Accordingly,
the switching of the pull-up and pull-down capabilities by the duty
adjustment unit 151 is conducted only in 16 stages in each case.
However, when the clocked inverters CV2F and CV4F are used, the
adjustment ratio of the pull-up and pull-down capabilities by the
duty adjustment unit 151 is changed. For example, when only the
clocked inverter CV2F is used, the drive capability of the duty
adjustment unit 151 can be adjusted within a range of 2 DC to 17
DC; when both the clocked inverters CV2F and CV4F are used, the
drive capability of the duty adjustment unit 151 can foe adjusted
within a range of 6 DC to 21 DC. In the former case, the adjustment
rate, or the rate of maximum drive capability to minimum drive
capability, stands at 8.5 (=17/2). In the latter case, the
adjustment rate is 3.5 (=21/6). The former is suitable for the case
where the duty adjustable range should be large, such as for
relatively-slow products, for example. The latter is suitable for
the case where the duty's minimum adjustment pitch should be finer,
such as for relatively-high-speed products, for example. In this
manner, according to the present embodiment, the duty adjustable
range and the minimum adjustment pitch can be easily changed.
According to the above-described configuration, the rising waveform
of the internal clock signal PCLKA0 output from the duty adjustment
unit 151 is controlled based on the control signals P1 and FP; the
falling waveform is controlled based on the control signals N1 and
FN.
The other duty adjustment units 152 to 154 have the same circuit
configuration as the above duty adjustment unit 151 except that
other corresponding control signals are input to the duty
adjustment units 152 to 154. The duty adjustment unit 152 receives
the internal clock signal PCLKA0 and then generates the internal
clock signal PCLKA1. The duty adjustment unit 153 receives the
internal clock signal PCLK0 and then generates the internal clock
signal PCLKB0. The duty adjustment unit 154 receives the Internal
clock signal PCLKB0 and then generates the internal clock signal
PCLKB1. Both the internal clock signals PCLKA1 and PCLKB1 are
supplied to the synthesis circuit 155.
Turning to FIG. 10, the synthesis circuit 155 includes four
inverter circuits IVA1 to IVA4, to which the internal clock signal
PCLKA1 is input; and four inverter circuits IVB1 to IVB4, to which
the internal clock signal PCLKB1 is input. The synthesis circuit
155 also includes pair's of transfer gates TG1 to TG4. One of each
pair of the transfer gates TG1 to TG4 is made conductive in
response to corresponding one of control signals IM1 to IM4.
Outputs of the inverter circuits IVA1 to IVA4 and IVB1 to IVB4 are
combined through the conductive sides of the transfer-gate pairs
TG1 to TG4.
More specifically, the output nodes of the inverter circuits IVA1
to IVA4 are short-circuited through the transfer gates TGA1 to
TGA4; the output nodes of the inverter circuits IVB1 to IVB4 are
short-circuited through the transfer gates TGB1 to TGB4. Of two
transfer gates (e.g., TGA1 and TGB1) that make up each of the
transfer-gate pairs TG1 to TG4, one transfer gate is made
conductive in response to corresponding control signals IM1 to IM4.
Therefore, the synthesis ratio of the internal clock signals PCLKA1
and PCLKB1 can be controlled according to the control signals IM1
to IM4.
For example, three of the transfer gates TGA1 to TGA4 are made
conductive, and one of the transfer gates TGB1 to TGB4 is made
conductive. In this case, the internal clock signals PCLKA1 and
PCLKB1 are combined with a synthesis ratio of 3:1, and the internal
clock signal PCLK1 is generated as a result. Alternatively, two of
the transfer gates TGA1 to TGA4 may be made conductive, and two of
the transfer gates TGB1 to TGB4 may be made conductive. In this
case, the internal clock signals PCLKA1 and PCLKB1 are combined
with a synthesis ratio of 1:1, and the internal clock signal PCLK1
is generated as a result.
Those control signals IM1 to IM4, too, are part (e.g., count value
CNTY) of the above-described duty control signal D2. This means
that the duty control signal D2 contains the control signals P1 to
P4, N1 to N4 and IM1 to IM4. As described above, the duty control
signal. D2 is generated by the DCC control circuit 170.
Turning to FIG. 11, the DCC control circuit 170 receives, for
example, an eight-bit duty detection signal D1 output from the duty
cycle detector 160, and decodes and performs a logic operation of
the duty detection signal D1, thereby generating a duty control
signal D2. Although not specifically limited, the duty detection
signal D1 of the present embodiment is an eight-bit binary signal:
the high six bits b7 to b2 of the signal are used to generate the
control signals P1 to P4 and N1 to N4, and the low two bits b1 and
b0 of the signal are used to generate the control signals IM1 to
IM4. In particular, the highest bit b7 is used as a signal
indicating whether the duty ratio is less than 50% or greater than
50%. This means that, if the value of the duty detection signal D1
is less than or equal to "01111111b", the duty ratio of the
internal clock signal LCLK is less than 50%; and that, if the value
of the duty detection signal D1 is greater than or equal to
"10000000b", the duty ratio of the internal clock signal LCLK is
greater than 50%. In this case, the above-described switch signal
SEL may be activated when the highest bit b7 is inverted.
As shown in FIG. 11, the DCC control circuit 170 includes a decoder
171, which decodes bits b6 to b2 of the duty detection signal D1; a
decoder 172, which decodes bits b1 and b0 of the duty detection
signal D1; and a logic circuit 173, which conducts a logic
operation based on output signals of the decoder 171 and the
highest bit b7 of the duty detection signal D1. If the highest bit
b7 is 0, or if the duty ratio of the internal clock signal LCLK is
less than 50%, the logic circuit 173 generates the control signals
P1 to P4 and N1 to N4 so that the drive capability of the duty
correction circuit 150 becomes smaller as the values of the bits b6
to b2 become smaller. If the highest bit b7 is 1, or if the duty
ratio of the internal clock signal LCLK is greater than 50%, the
logic circuit 173 generates the control signals P1 to P4 and N1 to
N4 so that the drive capability of the duty correction circuit 150
becomes smaller as the values of the bits b6 to b2 become larger.
Outputs of the decoder 172 are used as the control signals IM1 to
IM4.
In this case, the control signals P1, P3, N2 and N4 constitute a
first control signal; if the highest bit b7 is 0, or if the duty
ratio of the internal clock signal LCLK is less than 50%, the value
thereof is controlled according to the actual duty ratio. In this
case, the control signals P2, P4, N1 and N3 that constitute a
second control signal are fixed at maximum values. The control
signals P1, P3, N2 and N4 take values that are related to each
other. According to the present embodiment, P1=P3 and N2=N4; P1 and
P3 are inverted signals of N2 and N4. Therefore, the control
signals P1, P3, N2 and N4 can be generated so as to derive from one
type of control-signal.
Similarly, the control signals P2, P4, M1 and N3 constitute the
second control signal; if the highest bit b7 is 1, or if the duty
ratio of the internal clock signal LCLK is greater than 50%, the
value thereof is controlled according to the actual duty ratio. In
this case, the control signals P1, P3, N2 and N4 that constitute
the first control signal are fixed at maximum values. As described
later, the control signals P2, P4, N1 and N3 take values that are
related to each other. According to the present embodiment, P2=P4
and N1=N3; P2 and P4 are inverted signals of N1 and N3. Therefore,
the control signals P2, P4, N1 and N3 can be generated so as to
derive from one type of control signal.
Turning to FIGS. 12 and 13, FIG. 12 shows the case where the duty
ratio is less than 50% and FIG. 13 shows the case where the duty
ratio is over 50%.
Reference symbol 190 in FIGS. 12 and 13 represents the values of
bits b6 to b2 of the duty detection signal D1: there are 32 such
values in total. If the duty ratio is less than 50%, the duty ratio
becomes smaller as the values of bits b6 to b2 decrease. If the
duty ratio is greater than 50%, the duty ratio becomes larger as
the values of bits b6 to b2 increase. Reference symbol 191
represents the adjustment amount of the propagation path A, and
reference symbol 192 represents the adjustment amount of the
propagation path B.
In this case, the adjustment amounts A2 to A17 and B2 to B17 are
adjustment amounts corresponding to the above-described drive
capabilities 2 DC to 17 DC. However, the adjustment amounts A2 to
A17 of the propagation path A is so designed as to be 0.5 DC
smaller in drive capability than the adjustment amounts B2 to B17
of the propagation path B.
A process of setting the adjustment amounts of the propagation
paths A and B in accordance with the values of bits b6 to b2 is
performed in the following manner.
First, if the duty ratio is less than 50% and if the values of bits
b6 to b2 are "10000b" as indicated by reference symbol 133 in FIG.
12, then the adjustment amount of the propagation path A is set to
a corresponding A10. Meanwhile, the adjustment amount of the
propagation path B is set to B9, which is one pitch larger than the
adjustment amount A10. In this case, if the duty ratio is less than
50%, the drive capabilities of the pull-up circuits UP in the duty
adjustment units 151 and 153 are always adjusted by the control
signals P1 and P3, while the drive capabilities of the pull-down
circuits DN are fixed to maximum values. The drive capabilities of
the pull-down circuits DN in the duty adjustment units 152 and 154
are adjusted by the control signals N2 and N4, while the drive
capabilities of the pull-up circuits UP are fixed to maximum
values.
Therefore, in this example, as shown in FIG. 14, the drive
capabilities of the pull-up circuits UP in the duty adjustment
units 151 and 153 are set to 10 DC and 9 DC, respectively; the
drive capabilities of the pull-down circuits DN in the duty
adjustment units 152 and 154 are set to 10 DC and 9 DC,
respectively. The other pull-up circuits UP and pull-down circuits
DN are set to a maximum drive capability (17 DC). As a result, as
the internal clock signal PCLK0 is input, the rising edges of the
internal clock signals PCLKA0 and PCLKB0 become blunt, and the
falling edges of the internal clock signals PCLKA1 and PCLKB1
become blunt.
Turning to FIG. 15, solid line represents the actual waveform, and
broken line represents the waveform of the case where the duty
ratio is 50%. The same is true for FIG. 17, which will be described
later.
As described above, if the duty ratio is less than 50%, the pull-up
capability is adjusted by the first-stage duty adjustment units 151
and 153 so as to become smaller. Therefore, the rising edges of the
internal clock signals PCLKA0 and PCLKB0 become blunt in accordance
with the pull-up capability. In this case, the logic threshold
values of the next-stage duty adjustment units 152 and 154 have
been set to intermediate potential VM. Therefore, the timing at
which the input levels in the duty adjustment units 152 and 154 are
switched from low level to high level is delayed. This means that
the failing edges of the internal clock signal PCLK0 are delayed.
As a result, the duty ratio expands.
Furthermore, in the next-stage duty adjustment units 152 and 154,
the pull-down capability is so adjusted as to become smaller.
Therefore, the falling edges of the internal clock signals PCLKA1
and PCLKB1 become blunt in accordance with the pull-down
capability. In this case, the logic threshold value of the
next-stage synthesis circuit 155 has been set to intermediate
potential VM. Therefore, the timing at which the input level in the
synthesis circuit 155 is switched from high level to low level is
delayed. This means that the falling edges of the internal clock
signal PCLK0 are further delayed. As a result, the duty ratio
further expands. According to this principle, the duty ratio
expands to around 50%.
If the duty ratio is greater than 50%, and if the values of bits b6
to b2 are "10000b" as indicated by reference symbol 193 in FIG. 13,
then the adjustment amount of the propagation path A is set to a
corresponding A9. Meanwhile, the adjustment amount, of the
propagation path B is set to B9, which is one pitch larger than the
adjustment amount A9. In this case, if the duty ratio is greater
than 50%, the drive capabilities of the pull-down circuits DN in
the duty adjustment units 151 and 153 are always adjusted by the
control signals N1 and N3, while the drive capabilities of the
pull-up circuits UP are fixed to maximum values. The drive
capabilities of the pull-up circuits UP in the duty adjustment
units 152 and 154 are adjusted by the control signals P2 and P4,
while the drive capabilities of the pull-down circuits DN are fixed
to maximum values.
Therefore, in this example, as shown in FIG. 16, the drive
capabilities of the pull-down circuits DN in the duty adjustment
units 151 and 153 are set to 9 DC; the drive capabilities of the
pull-up circuits UP in the duty adjustment units 152 and 154 are
set to 9 DC. The other pull-up circuits UP and pull-down circuits
DN are set to a maximum drive capability (17 DC). As a result, as
the internal clock signal PCLK0 is input, the falling edges of the
internal clock signals PCLKA0 and PCLKB0 become blunt, and the
rising edges of the internal clock signals PCLKA1 and PCLKB1 become
blunt.
Turning to FIG. 17, as described above, if the duty ratio is
greater than 50%, the pull-down capability is adjusted by the
first-stage duty adjustment units 151 and 153 so as to become
smaller. Therefore, the falling edges of the internal clock signals
PCLKA0 and PCLKB0 become blunt in accordance with the pull-down
capability. In this case, the logic threshold values of the
next-stage duty adjustment units 152 and 154 have been set to
intermediate potential VM. Therefore, the timing at which the
input, levels in the duty adjustment units 152 and 154 are switched
from high level to low level is delayed. This means that the rising
edges of the internal clock signal PCLK0 are delayed. As a result,
the duty ratio decreases.
Furthermore, in the next-stage duty adjustment units 152 and 154,
the pull-up capability is so adjusted as to become smaller.
Therefore, the rising edges of the internal clock signals PCLKA1
and PCLKB1 become blunt in accordance with the pull-up capability.
In this case, the logic threshold value of the next-stage synthesis
circuit 155 has been set to intermediate potential VM. Therefore,
the timing at which the input level in the synthesis circuit 155 is
switched from low level to high level is delayed. This means that
the rising edges of the internal clock signal PCLK0 are further
delayed. As a result, the duty ratio further decreases. According
to this principle, the duty ratio decreases to around 50%.
In that manner, the logic circuit 173 in the DCC control circuit
170 generates the control signals P1 to P4 and N1 to N4 based on
the values of bits b to b2 of the duty detection signal D1, thereby
controlling the drive capabilities of the duty adjustment units 151
to 154 and generating the two internal clock signals PCLKA1 and
PCLKB1. As described above, the difference between the adjustment
amount of the propagation path A and the adjustment amount of the
propagation path B is 0.5 DC when measured in drive capability.
Therefore, the difference between the duty ratio of the internal
clock signal PCLKA1 and the duty ratio of the internal clock signal
PCLKB1 is equal to a minimum pitch, which is equivalent to 0.5 DC
in drive capability. The internal clock signals PCLKA1 and PCLKB1
having the above duty difference are input to the synthesis circuit
155.
Turning to FIG. 18A, when the duty ratio is less than 50%, the
falling edges of the internal clock signals PCLKA1 and PCLKB1 are
delayed with respect to the internal clock signal PCLK0. Moreover,
the falling edge of the internal clock signal PCLKA1 is delayed by
an amount equivalent to a drive capability of 0.5 DC with respect
to the falling edge of the internal clock signal PCLKB1. If these
two internal clock signals PCLKA1 and PCLKB1 are combined by the
synthesis circuit 155, one of three intermediate phases M1, M2 and
M3 can be obtained depending on the values of the control signals
IM1 to IM4.
Turning to FIG. 18B, when the duty ratio is greater than 50%, the
rising edges of the internal clock signals PCLKA1 and PCLKB1 are
delayed with respect to the internal clock signal PCLK0. Then, the
rising edge of the internal clock signal PCLKA1 is delayed, by an
amount equivalent to a drive capability of 0.5 DC with respect to
the rising edge of the internal clock signal PCLKB1. If these two
internal clock signals PCLKA1 and PCLKB1 are combined by the
synthesis circuit 155, one of three intermediate phases M1, M2 and
M3 can be obtained depending on the values of the control signals
IM1 to IM4.
The intermediate phases M1 to M3 shown in FIG. 18A each represent
the falling edge of the internal clock signal PCLK1 that is
obtained when the internal clock signals PCLKA1 and PCLKB1 are
combined with a synthesis ratio of 3:1, 1:1 and 1:3, respectively.
The intermediate phases M1 to M3 shown in FIG. 18B each represent
the rising edge of the internal clock signal PCLK1 that is obtained
when, the internal clock signals PCLKA1 and PCLKB1 are combined
with a synthesis ratio of 3:1, 1:1 and 1:3, respectively. The
synthesis ratio is selected by the control signals 1M1 to IM4 based
on bits b1 and b0 of the duty detection signal D1.
Incidentally, if the synthesis ratio is set to 1:0, the waveform of
the internal clock signal PCLK1 is determined based only on the
internal clock signal PCLKA1. If the synthesis ratio is set to 0:1,
the waveform of the internal clock signal PCLK1 is determined based
only on the internal clock signal PCLKB1. In this manner, the
synthesis circuit 155 is able to directly output the waveform that
is not an intermediate value. Therefore, the adjustment pitch of
the duty ratio can be made highly accurate to 1/4 (or the
resolution can be quadrupled).
The adjustment of the duty ratio is made by the duty adjustment
units 151 to 154 in 32 stages; the resolution is quadrupled by the
synthesis circuit 155. Therefore, the duty correction circuit 150
of the present embodiment can ensure 128 stages of adjustment
pitches in total. If a duty correction circuit of a type that is
designed to fine-tune a bias level of a transistor is used, the
duty correction circuit needs to generate 128 levels of bias
potential with high precision; a slight noise can cause a large
error in the duty ratio. According to the present embodiment, the
duty ratio is completely digitally-controlled and is changed
without the use of bias potential. Therefore, the noise immunity is
high, and the duty adjustment operation can be performed in a
stable manner.
Moreover, according to the present embodiment, in the first-stage
duty adjustment units 151 and 153, the drive capability of one of
the P-channel and N-channel MOS transistors is controlled to adjust
the duty ratio. In the next-stage duty adjustment units 152 and
154, the drive capability of the other one of the P-channel and
N-channel MOS transistors is controlled to adjust the duty ratio.
Therefore, even if there is a difference between the threshold
value of the P-channel MOS transistor and the threshold value of
the N-channel MOS transistor due to process conditions and the
like, a difference in the adjustments of the duty ratio can be
offset.
Turning to FIG. 19, the duty correction circuit 150A of the first
modified example is different from the duty correction circuit 150
shown in FIG. 6 in that only the propagation path A is used.
Accordingly, the synthesis circuit 155 is not used. In this
configuration, compared with the duty correction circuit 150 shown
in FIG. 6, the adjustment pitch becomes coarser. However, the
occupied area can be reduced. Moreover, as in the case of the duty
correction circuit 150 shown in FIG. 6, it is possible to offset a
difference in the adjustments of the duty ratio, which is
attributable to a difference between the threshold values. If the
duty correction circuit 150A of the first modified example is used,
the minimum adjustment pitch in the first mode is equal to the
minimum adjustment pitch in the second mode. That is, such aspects
are also included in the present invention.
Turning to FIG. 20, the duty correction circuit 150B of the second
modified example is different from the duty correction circuit 150
shown in FIG. 6 in that the duty adjustment units 152 and 154 are
omitted. In this configuration, it is impossible to offset a
difference in the adjustments of the duty ratio, which, is
attributable to a difference between the threshold values. However,
the occupied area can be reduced, and, as in the case of the duty
correction circuit 150 shown in FIG. 6, the fine adjustment pitch
can be obtained.
Turning to FIG. 21, the duty correction circuit 150C of the third
modified example is different from the duty correction circuit 150
shown in FIG. 6 in that only the duty adjustment unit 151 is used.
In this configuration, it is possible to dramatically simplify the
circuit configuration. If the duty correction circuit 150C of the
third modified example is used, the minimum adjustment pitch in the
first mode is equal to the minimum adjustment pitch in the second
mode.
It is apparent that the present invention is not limited to the
above embodiments, but may be modified and changed without
departing from the scope and spirit of the invention.
For example, in the above embodiments, several specific examples of
the duty correction circuit have been described with reference to
FIGS. 6 to 21. However, according to the present invention, the
configuration of the duty correction circuit is not specifically
limited. Therefore, instead of using the duty correction circuit
that includes clocked inverters, a duty correction circuit that
includes phase interpolators (interpolators) may be used.
Even if the duty correction circuit that includes clocked inverters
is used, a specific configuration thereof is not limited to the
above-embodiments. For example, in the above embodiments, the
control signals P1 to P4 and N1 to N4 are generated based on the
values of bits b7 to b2 of the duty detection signal D1, and the
control signals IM1 to IM4 are generated based on the values of
bits b1 and b0. However, the bits that are used to generate those
control signals P1 to P4, N1 to N4 and IM1 to IM4 are not limited
to the above bits.
In the above embodiments, the drive capabilities of a plurality of
clocked inverters in the duty adjustment units 151 to 154 are
weighted by the power of 2. However, this configuration is not
necessarily required in the present invention. Therefore, the duty
adjustment units can be made by connecting a plurality of clocked
inverters having the same drive capability in parallel.
Furthermore, in the above embodiments, there is no difference in
drive capability between a plurality of inverter circuits in the
synthesis circuit 155. However, those drive capabilities may be
weighted by the power of 2.
Moreover, in the above embodiments, the duty ratio of the internal
clock signal is increased or decreased in the process of being
adjusted to 50%. However, the target duty ratio is not limited to
50%. Furthermore, it is unnecessary to be able to both increase and
decrease the duty ratio of the internal clock signal. For example,
if it is known beforehand that the duty ratio of the input internal
clock signal is smaller than a target value, the function of
decreasing the duty ratio is unnecessary, and having the function
of increasing the duty ratio is sufficient. In this case, as for
the pull-down circuits DN in the duty adjustment units 151 and 153
and the pull-up circuits UP in the duty adjustment units 152 and
154, the drive capabilities are not required to be adjustable. The
drive capabilities may be fixed.
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