U.S. patent number 3,739,255 [Application Number 05/208,880] was granted by the patent office on 1973-06-12 for high frequency ferroresonant transformer.
This patent grant is currently assigned to North Electric Company. Invention is credited to Dale V. Leppert.
United States Patent |
3,739,255 |
Leppert |
June 12, 1973 |
HIGH FREQUENCY FERRORESONANT TRANSFORMER
Abstract
A high frequency ferroresonant regulator circuit having a
saturable core structure comprised of a first core of a square loop
magnetic material and a second core; the first core having a first
permeability region which provides low reluctance to the flux
generated during the initial part of the period between resonant
pulses of the ferroresonant circuit, and a second permeability
region of different values upon saturation; the second core having
a permeability which is less than the first permeability of the
first core and which is greater than the second permeability of the
first core, and which is of a value which does not saturate at the
values of mmf provided by the ferroresonant circuit; which
structure increases the width and decreases the amplitude of the
resonant pulse provided by the ferroresonant transformer therein
during the resonant period to provide increased circuit efficiency
and more stable operation at all values of output load.
Inventors: |
Leppert; Dale V. (Worthington,
OH) |
Assignee: |
North Electric Company (Galion,
OH)
|
Family
ID: |
22776407 |
Appl.
No.: |
05/208,880 |
Filed: |
December 16, 1971 |
Current U.S.
Class: |
363/75; 336/212;
323/248 |
Current CPC
Class: |
G05F
3/06 (20130101); H01F 38/06 (20130101); H01F
2003/106 (20130101) |
Current International
Class: |
H01F
38/06 (20060101); H01F 38/00 (20060101); G05F
3/04 (20060101); G05F 3/06 (20060101); G05f
003/08 (); G05f 001/32 () |
Field of
Search: |
;323/6,44R,48,60,61
;321/16,18,25 ;336/212,229 |
References Cited
[Referenced By]
U.S. Patent Documents
Primary Examiner: Pellinen; A. D.
Claims
I claim:
1. In a ferroresonant regulator circuit for high frequency
application, input means over which input signals of a given
operating range of voltages and frequencies are received,
inductance means, saturable core means including a first magnetic
core of a square-loop material having a first permeability region
prior to saturation and a second substantially lower permeability
region during saturation, and a second magnetic core having a
permeability which is less than the value of the first permeability
region of said first core and greater than the value of said second
permeability region of said first core, whereby with saturation of
the first core responsive to said input signals in said given
operating range said second core will absorb the further mmf, input
and output winding means wound on said saturable core means, the
core areas, the number of turns of said winding means, and the
material of said first and second magnetic cores being of a value
to effect saturation of the first magnetic core and to prevent
saturation of the second core as a result of the flux generated in
response to said input signals, means connecting said input winding
means in series with said inductance means to said input means,
resonant capacitor means, means coupling said resonant capacitor
means to said input winding means, and means coupling said output
winding means to an associated load.
2. A ferroresonant regulator circuit as set forth in claim 1 in
which the permeability of said first magnetic core is of a value to
absorb substantially all of the flux until saturation, and the
permeability of said second magnetic core is of a value to absorb
substantially all of the further flux generated after said first
magnetic core has saturated.
3. A ferroresonant regulator circuit as set forth in claim 1 in
which said first magnetic core comprises a tape-wound core of a
nickel-iron alloy.
4. A ferroresonant regulator circuit as set forth in claim 1 in
which said second magnetic core comprises a sintered powdered core
of soft ferrite material.
5. A ferroresonant regulator circuit set forth in claim 1 in which
said first and second magnetic cores are toroid cores secured to
one another with the center aperture thereof in aligned relation to
provide a unitary core structure and in which said input and output
windings are wound on said unitary core structure.
6. A ferroresonant regulator circuit as set forth in claim 1 in
which said means for coupling said resonant capacitor to said input
winding means comprises a further winding wound on said saturable
core means.
7. A ferroresonant regulator circuit as set forth in claim 1 in
which said first magnetic core comprises a laminated section of a
square loop material and said second magnetic core comprises a
pressed granular section of a ferrite material.
8. A ferroresonant regulator circuit as set forth in claim 7 in
which said first and second magnetic cores have an upper leg, a
lower leg, two outer legs and a center leg, and in which said input
and output windings are wound on said center leg.
9. A ferroresonant regulator circuit as set forth in claim 1 in
which said output winding comprises a center-tapped winding, and
said means for coupling said output winding means to an associated
load includes rectifier means for connecting the ends of said
output winding to one side of said load, and means for connecting
said center tap to the other side of said load.
10. In a high frequency ferroresonant regulator circuit for high
frequency application, input means over which input signals of a
given operating range of voltages and frequencies are received,
inductance means, saturable core means including a magnetic core of
a square-loop material having a first permeability region prior to
saturation and a second lower permeability during saturation, a
first and a second winding wound on said first core and a second
magnetic core having a relatively uniform permeability which is
less than the value of the first permeability region of said first
core and greater than the value of said second permeability region
of said first core, whereby with saturation of the first core
responsive to the input signals in said given operating range said
second core will absorb the further mmf, a third and fourth winding
wound on said second core, means connecting said first and third
windings on said first and second cores to said input means in
series with said inductance means, the areas, the number of turns
of said winding means, and the material of said first and second
magnetic cores being of a value to effect saturation of the first
magnetic core and to prevent saturation of the second core as a
result of the flux generated in response to said input signals,
resonant capacitor means, means coupling said resonant capacitor
means to said first and third windings, and means coupling said
second and fourth windings to an associated load.
11. A regulator circuit as set forth in claim 10 in which said
means coupling said second and fourth windings to an associated
load comprises a rectifier full wave bridge circuit.
12. In a high frequency ferroresonant regulator circuit, input
means over which input signals of a given operating range of
voltages and frequencies are received, inductance means having a
first and second winding, saturable core means including a first
magnetic core of a square-loop material having a first permeability
region prior to saturation and a second magnetic core having a
relatively uniform permeability which is less than the value of the
first permeability region of said first core and greater than the
value of said second permeability region of said first core,
whereby with saturation of the first core responsive to the input
signals in said given operating range said second core will absorb
the further mmf, an input winding wound on said saturable core
means, first and second output means wound on said saturable core
means, the areas, the number of turns of said winding means, and
the material of said first and second magnetic cores being of a
value to effect saturation of the first magnetic core and to
prevent saturation of the second core as a result of the flux
generated in response to said input signals, means connecting the
first winding of said inductance means and said input winding of
said saturable core means to said input means, resonant capacitor
means, means coupling said resonant capacitor to said input winding
means on said saturable core means, and means coupling said first
output winding means on said saturable core means to an associated
load, and means connecting the second winding of said inductance
means and the second output means of said saturable core means to
provide an isolated output voltage proportional to the input
voltage.
13. A unitary saturable core for a ferroresonant transformer
circuit comprising a first magnetic core section of a square-loop
high currie temperature magnetic material having a first
permeability region prior to saturation and a second substantially
lower permeability region during saturation, and a second section
of a magnetic material secured to said first section having a
permeability which is of a substantially lower value than the
values of the first permeability region of said first core and
greater than the values of the second permeability region of said
first core.
14. A saturable core as set forth in claim 13 in which said first
magnetic core section comprises a toroid-shaped, tape-wound core of
nickel-iron alloy.
15. A saturable core as set forth in claim 13 in which said second
magnetic core section comprises a toroid-shaped powdered core of a
soft ferrite material.
16. A saturable core as set forth in claim 13 in which said first
and second magnetic core sections are toroidal in form, and which
includes input and output windings wound thereon.
17. A saturable core as set forth in claim 13 in which said first
magnetic core section comprises a plurality of laminations of
square loop material, and said second magnetic core section
comprises a section of pressed granular material in contacting
relation therewith.
18. A saturable core as set forth in claim 17 in which said first
and second magnetic core sections have an upper and lower leg, two
outer legs and a center leg, and which have input and output
windings wound on said center leg.
19. A saturable core as set forth in claim 18 in which said first
and said second magnetic core sections comprise a plurality of E, I
laminations of square loop material joined to provide a rectangular
shaped unitary structure with a center leg and two windows, and in
which the E, I laminations of the second magnetic core section are
assembled with predetermined air gaps between the adjacent portions
of the E, I laminations, the distance of the air gap being adjusted
to provide the desired permeability of the second core.
Description
BACKGROUND OF THE INVENTION
The use and application of ferroresonant regulator circuits in the
provision of regulated DC power derived from a 60 cycle source has
become widespread and is well known in the field. In addition to
being extremely reliable in operation, ferroresonant regulator
circuits provide excellent voltage regulation with static and
dynamic input line voltages, and have good efficiency and input
power factor.
In addition to these operational advantages, the geometry of a
conventional ferroresonant regulator is basically relatively
simple. In its more basic form, the regulator comprises an input
ballast inductance L effectively connected in series with the input
winding of a saturable core T.sub.s across a 60 cycle supply
source. A resonant capacitor C is connected across the saturable
core input winding, and the output winding of the saturable core
T.sub.s is connected to an output load. In operation, each half
cycle of the input alternating current effects saturation of the
saturable core T.sub.s after a fixed volt time integral. That is,
the product of the voltage across the primary winding and time for
saturation remains constant. When the core saturates, the resonant
capacitor C discharges and recharges to the opposite polarity. The
saturable core then comes out of saturation and begins to measure a
new volt time integral for the next half cycle.
While the known ferroresonant regulator circuits have been most
successful in the provision of regulated outputs for large power
sources which operate at relatively low order frequencies, such as
50 and 60 cycles, the attempted use of the known ferroresonant
techniques and structures to regulate current derived from a high
frequency source, such as for example 10-20 kilohertz, has not been
particularly successful. It has been found, for example, that if a
ferroresonant regulator circuit using a ferrite saturable core is
used in high frequency applications, the circuit is extremely
sensitive to ambient temperature changes, and in many instances
variations in the B-H saturation characteristics of the material in
the amount of 20-30 percent may be experienced. Obviously a circuit
arrangement having such order of variation would have limited
commercial application.
It has also been observed that if a saturable core of a material
conventionally used in high frequency applications is provided, the
saturable core is driven to saturation in each half cycle of the
input voltage, the resultant current pulse through the resonant
capacitor is of extremely narrow width (in the order of 5-10
percent of one cycle of the input waveform), and excessively high
peak current values are experienced. The high peak current values
result in high core and winding losses and, in most cases,
instability at light load inputs is experienced.
SUMMARY OF THE INVENTION
It is an object of the present invention therefore to provide a
novel ferroresonant transformer circuit for regulating high
frequency circuits which is stable at all load values, and
particularly a ferroresonant regulator circuit of such type which
is of compact size, low component count, and which provides
regulated outputs of acceptable values.
It is a specific object of the invention to provide an inexpensive
ferroresonant transformer structure for use in ferroresonant
regulator circuits in which the width or duration of the output
pulse provided by the ferroresonant transformer during the resonant
period is increased, and the current amplitude reduced to provide
increased circuit efficiency and more stable operation at all
values of output loads.
The novel ferroresonant transformer circuit, which is so operative,
basically comprises an input ballast inductor L, which may be, for
example, of the pot or toroid core type, connected across an
alternating current high frequency input source in series with the
input winding of a saturable core structure T.sub.s L.sub.s, which
has multi-flux paths. A resonant capacitor C is coupled to the
saturable core structure input winding. The output winding of the
saturable core structure T.sub.s L.sub.s is in turn connected via
associated circuitry to a load.
The saturable core structure T.sub.s L.sub.s in one embodiment of
the invention comprises a unitary structure including a first core
element comprised of a tape-wound, square-loop magnetic alloy, and
a second core element comprised of sintered powdered core material,
such as ferrite, molypermalloy or the like. In such embodiment, the
two cores are of a toroid configuration and are held in aligned
contact relation with each other by suitable means, such as epoxy,
glue, tape or the like, to provide a unitary core structure upon
which the input and output windings of the saturable core structure
T.sub.s L.sub.s are wound. If desired, such unitary structure may
be encased by conventional potting methods. The saturation
inductance thereby includes a first component comprising the air
inductance of the saturable core input winding and a second
component which is provided by the powdered core in conjunction
with the input winding. The sum of these two components makes up
the saturation inductance of the T.sub.s L.sub.s core
structure.
The unitary saturable core structure as thus wound and constructed
is operative to provide an increased flux change during the
resonant period to thereby effect the desired increase in width of
the output pulse. That is, the tape-wound core of square loop
material has a first permeability region prior to saturation in
each half cycle of the input voltage which is of a higher value
than the permeability of the second core. The second core has a
relatively uniform permeability which is substantially less than
the permeability of the first core prior to saturation of the first
core. During the period prior to saturation of the first core (the
second core is of a material which will not saturate at the value
of mmf provided in the ferroresonant transformer) the first core
absorbs most of the flux, and continues to absorb most of the flux
until such time as the first core is driven to saturation. At such
time, the permeability of the first core decreases to a value which
is substantially less than that of the relatively uniform
permeability of the second core, and the major portion of the
further flux generated is absorbed by the second core.
As a result of the ability of the unitary core structure to conduct
the further flux, the width of the capacitor current pulse provided
in the ferroresonant circuit is correspondingly increased. With an
increase in the current pulse width, the high peak value currents
are reduced and a more efficient and stable operating circuit is
provided. In addition to achieving such improved mode of operation,
the square loop, high-curie temperature magnetic material which has
excellent temperature characteristics as used in the first core,
results in a unitary core structure which minimizes output voltage
shift.
BRIEF DESCRIPTION OF THE DRAWINGS
FIG. 1 is a schematic illustration of a novel ferroresonant
regulator circuit including a first embodiment of a novel
ferroresonant transformer structure;
FIG. 2 illustrates a physical configuration of a novel saturable
core structure which is utilized in the ferroresonant regulator
circuit of FIG. 1;
FIG. 3 illustrates the B-H curves for the T.sub.s core and L.sub.s
cores of FIG. 2, and the composite B-H curve for the novel unitary
core structure of FIG. 2;
FIG. 4 illustrates another embodiment of a novel saturable core
structure for use in the ferroresonant regulator circuit;
FIG. 5 is yet another embodiment of a novel saturable core
structure schematically shown in a ferroregulator circuit;
FIGS. 6 and 7 set forth further novel ferroresonant circuit
arrangements;
FIG. 8 illustrates a ferroresonant regulator circuit of the type
shown in FIG. 1 with a frequency feedback control;
FIG. 9 is a schematic drawing related to FIG. 1, with designations
identifying the voltages and currents which occur therein; and
FIGS. 10a-10i comprise a set of curves which when taken with FIG. 9
illustrate the steady state voltages, currents and fluxes in the
ferroresonant transformer circuit of the invention.
DETAILED DESCRIPTION
With reference to FIG. 1, there is shown thereat a novel
ferroresonant regulator circuit including a DC source 10 which may
comprise a battery, a regulated or unregulated direct current
source, or the output of a commercial alternating current source as
rectified and filtered. The output E.sub.i of the DC source 10 is
fed to a DC to AC inverter 12 which provides a high frequency
output e.sub.i (i.e. over 1 KHz). DC to AC inverters are well known
in the field, and inverter 12, in one operative embodiment to be
described, provided a 21-27 volt square wave output at a frequency
of 8.922 KHz. The output of DC to AC inverter 12 is connected over
input ballast inductor 16 to terminals A, B of the input winding 18
of the T.sub.s L.sub.s saturable core 20. A resonant capacitor 22
is connected across the saturable core input winding 18.
An output winding 24 for the T.sub.s L.sub.s saturable core
transformer circuit 14 is connected via rectifier and filter
circuit 25 to a load 32. That is, the starting and terminating
terminals E, C of output winding 24 are connected via rectifiers
26, 28 respectively to one side of load 32 and the center tap D of
output winding 24 is connected to the other side of load 32. Filter
capacitor 30 is connected across the rectified output of winding
24.
The input ballast inductor 16 may be wound on a powdered core
toroid, such as a ferrite or molypermalloy core or the like (or pot
core, made of manganese-zinc material or the like). In the event
that the unit is to be used for lower operating frequencies, as for
example in the order of 1 KHz, silicon steel lamination cores may
be used.
Capacitor 22 is coupled as shown to the input winding 18 on the
saturable core structure 20 to operate therewith and with inductor
16 in a ferroresonant mode during each half cycle of the voltage
input from inverter 12. Dipped mica capacitors, film capacitors,
and metalized film capacitors may be used as the resonant capacitor
22.
One embodiment of a novel core structure T.sub.s L.sub.s is shown
in FIG. 2, and as there shown comprises a first toroid core
T.sub.s, which may be of a tape-wound core of a square loop, high
curie-temperature magnetic material (such as nickel-iron alloy or
the like) which is secured by suitable means, such as epoxy, etc.,
in aligned contacting relation as shown with a second toroid core
element L.sub.s, which may comprise a sintered powdered core made
of ferrite, molypermalloy or the like having a filler material
added in amounts to provide the desired permeability. In the
arrangement of FIG. 2, the two toroid cores T.sub.s and L.sub.s are
secured in aligned contacting relation as shown to form a unitary
core structure about which the input winding 18 and output winding
24 are wound. In use, the terminal ends A, B of the input winding
18 are serially connected with ballast inductor 16 to the output of
inverter circuit 12 (FIG. 1) with the capacitor 22 coupled as shown
to winding 18, and the terminal ends E, C, and center tap D of
winding 24 are connected over rectifier and filter circuit 25 to
load 32.
In one successful embodiment of the circuit shown in FIG. 1, the
inverter circuit 12 provided a square wave output having a voltage
variable between 21-27 volts peak and at a frequency of 8.922 KHz
over a potted core inductance 16 comprised of a 26mm by 16mm pot
core of a manganese zinc material having an effective permeability
in the order of 51, with a winding of 57 turns of 22 gauge
insulated magnet wire wound thereon.
Capacitor 22 in such arrangement comprised a 0.47 microfarad, 100
volt DC mylar capacitor. T.sub.s L.sub.s core 20 comprised a
tape-wound core T.sub.s of nickel-iron alloy, as available from
Magnetics, Inc., Butler, Pa., No. 52061-1R, having a first
permeability region prior to saturation in the order of 140 to
200,000, and a second permeability region after saturation which is
near zero.
The L.sub.s core was made of sintered powdered material, Magnetic
Inc. No. 55932-A2, which is a nickel-iron alloy with filler added
to provide a permeability in the order of 26. The cross-sectional
area of the core L.sub.s is selected to be of sufficient value to
prevent saturation at the values of mmf generated during each
cycle.
The core T.sub.s in such embodiment had 1.0 inch OD; 0.75 inch ID;
0.25 inch thickness; and the core L.sub.s had an 1.06 inch OD, 0.58
inch ID and 0.44 inch thickness.
The cores T.sub.s L.sub.s were secured together, and an input
winding 18 made up of 42 turns of 18 gauge insulated magnet wire
equally distributed and wound tight on the unitary core structure
T.sub.s L.sub.s with the terminating ends A, B being brought out as
indicated in FIG. 2 for connection in the ferroresonant transformer
circuit 14 in the manner shown in FIG. 1. The output winding 24
which was also wound around the unitary core structure T.sub.s
L.sub.s comprised 20 turns of 18 gauge insulated magnetic wire
equally distributed about and wound tight on the unitary core
structure with the terminal ends E and C and center tap D being
brought out as shown in FIG. 2 for connection to the ferroresonant
circuit 14 as shown in FIG. 1.
The rectifiers 26, 28 in circuit 25 comprised 3 amp DC,
fast-recovery rectifiers available from Semtech, Calif., as 35F2;
and the filter capacitor 30 was a 1,300 microfarad, 20 volt DC
capacitor. The ferroresonant circuit of FIG. 1 provided regulated 5
volts DC voltage, and was designed to supply output current to a
load at 1.5 amperes DC.
OPERATION
With the application of the square-wave output of the DC to AC
inverter 12 over the input ballast inductor 16 to the input winding
18 of the T.sub.s L.sub.s saturable core 20, the saturable core
structure T.sub.s L.sub.s, capacitor 22, and the inductor 16 of
ferroresonant transformer circuit 14 are operative in a
ferroresonant action to provide a regulated output. Representative
waveforms of the operation of the novel ferroresonant regulator
circuit at the points identified in FIG. 9 are shown in FIGS.
10a-10i, which waveforms are representative of the circuit
operation for a nominal input voltage and with the output load 32
at approximately full load.
With reference to FIG. 10a, the waveform thereshown represents the
voltage waveform e.sub.i of FIG. 9, output from the DC to AC
inverter 12 of FIG. 1, each cycle of the waveform having a time
period of T.sub.o =(1/f.sub.o) (see FIG. 10a), wherein f.sub.o is
the input operation frequency to the ferroresonant transformer
circuit 14. With reference to FIG. 10b, the voltage e.sub.c which
occurs across capacitor C (FIG. 9) follows the input waveform (FIG.
10a), the capacitor C being charged in the positive direction with
the occurrence of the leading edge of the positive rectangular
waveform which is output from inverter 12, and reaching a constant
potential level which is maintained until the occurrence of the
trailing edge of the rectangular waveform e.sub.i output from
inverter 12. At such time, the voltage e.sub.c across the capacitor
C decreases to zero, as shown, and increases in the opposite
direction as charging of the capacitor C in the negative direction
occurs. The time period for such changing condition of the voltage
on capacitor C is expressed as T.sub.p =(1/f.sub.p). As shown in
FIG. 10, T.sub.p is the total time period of the resonant pulse and
f.sub.p is the frequency of the resonant pulse.
The voltage e.sub.L across inductance L during the corresponding
half cycle as shown in FIG. 10c reflects the changing voltage on
the capacitor C. That is, during the period capacitor C charges,
the voltage across the inductance L decreases and reaches a
constant negative value as the steady state, positive charge is
reached on capacitor C. During the period (T.sub.p /2 )
=(1/2f.sub.p) (see FIG. 10b), as the capacitor C begins to
discharge, the voltage across inductance L (FIG. 10c) drops to a
maximum negative value, and then changes (at the rate of change of
the capacitor voltage e.sub.c) towards zero, and further increases
to a steady state positive voltage value. The voltage e.sub.L
across inductance L remains at such level until the capacitor C
once more discharges and recharges in the positive direction.
The current waveforms i.sub.i, i.sub.c, i.sub.w for the
ferroresonant regulator circuit (see FIG. 9) are shown in FIGS.
10d-10f. With reference first to FIG. 10d, a representative current
input i.sub.i is shown for the assumed full-load condition, and as
there illustrated, as the current i.sub.i increases toward a
maximum positive value, capacitor C charges in a positive direction
as shown in FIG. 10b. After the capacitor C is fully charged, the
current i.sub.i decreases toward zero (i.e. the remaining period of
the positive pulse input from inverter 12). As capacitor C
recharges in the opposite direction, the current i.sub.i drops to a
maximum negative value, and then slowly proceeds in the direction
of zero during the remaining period of the negative half cycle of
the input pulse.
The current i.sub.c through capacitor C (FIG. 9) is illustrated by
the waveform in FIG. 10e, and as there shown, current flow occurs
during the periods of charge and discharge of capacitor C, which
periods are identified by (T.sub.P /2 ) =(1/2f.sub.p).
Current through input winding 18 of saturable core 20 is shown in
FIG. 10f. It will be apparent that such waveform comprises the sum
of the waveforms shown in FIGS. 10d and 10e (i.e., the sum of the
current flow over the capacitor C and the inductance L).
With reference now to FIGS. 10g-10i, the manner in which the flux
is developed in the unitary core structure T.sub.s L.sub.s to
effect the desired operation will become more apparent. With
specific reference to FIG. 10g, it will be seen that until
saturation of core T.sub.s in each half cycle, nearly all flux
(.phi..sub.T) generated flows in core T.sub.s. After .phi..sub.T
reaches the saturation level (.phi..sub.S) of the T.sub.s core the
permeability of the magnetic path provided by core T.sub.s becomes
less than the permeability of core L.sub.s and the further flux
generated by i.sub.w during the remaining portion of the half cycle
flows in core L.sub.s (.phi..sub.L, FIG. 10h). Since the material
and size of core L.sub.s has been selected so that flux .phi..sub.L
in the core L.sub.s will never reach the saturation level, the
width of the resonant pulse (T.sub.p /2 ) is basically determined
by the permeability of the core L.sub.s, the value of capacitor C
and the number of turns in winding N (FIG. 9) on the core and the
leakage inductance of the winding N.
With reference to FIG. 3, the resultant operation of the novel core
is further set forth. As there shown, the solid lines represent the
B-H curve for the T.sub.s core. It is noted that the extreme end
portions of such curves are essentially flat, which is
characteristic of nickel-iron alloy material such as used for the
tape wound core T.sub.s (i.e., prior to saturation, as represented
by the vertical portion of the BH curve, the permeability of core
T.sub.s is high--in the order of 140 to 200,000--and after
saturation the permeability of core T.sub.s as represented by the
flat horizontal portions of the curve decreases to almost zero).
The broken line L.sub.s in FIG. 3 represents the BH curve of the
second core L.sub.s, and as there indicated the core L.sub.s has a
relatively linear permeability (in the order of 26). The dot-dash
line in FIG. 3 represents the BH characteristic of the unitary core
structure 20, and it will be seen from such showing that as the
core T.sub.s approaches saturation, the permeability across core
T.sub.s decreases to a value which is less than that of the core
L.sub.s, whereby the further flux generated in the half cycle is
absorbed by the core L.sub.s.
As a result of the conduction of the further flux by core L.sub.s
(FIG. 10h) the unitary core structure 20 provides a capacitor pulse
i.sub.c (FIG. 10e) of increased width and reduced amplitude (i.e.,
the pulse width which would be obtained by the use of core T.sub.s
alone would be in the order of one-fourth to one-third the width
achieved with the novel unitary core structure). With the increase
in the pulse width, lower peak resonant discharge currents occur
and the capacitor root-mean-square current value is minimized to
effect reduced winding conductor losses. This also results in a
reduction of core losses and the possibility of instability and
generally yields a smaller size ferroresonant transformer.
In addition, the novel hybrid core arrangement of the disclosure
has the temperature characteristics of square loop magnetic core
materials which substantially minimizes variation of the regulating
characteristics in variable ambient temperature environments.
With reference to FIG. 4, a further embodiment of a unitary core
structure which may be used for the T.sub.s L.sub.s saturable core
in the described ferroresonant regulator circuit is set forth
thereat. As there shown, a plurality of E-shaped laminations are
interleaved with I laminations in known manner to provide a first
laminated core section T.sub.s of a rectangular configuration which
has a first and a second window 31,33. The E, I laminations may be
made from nickel-iron alloy material having a permeability region
prior to saturation in the order of 140 - 200,000 and a thickness
in the order of 4 mils, for operation at 1 KHz, for example, it
being apparent that for higher frequencies a thinner material may
be used. The unitary core structure 29 further includes a second
rectangular-shaped core section L.sub.s made of a sintered ferrite
having an effective permeability in the order of 26 and which
dimensionally conforms to the first section T.sub.s. The second
section L.sub.s is fastened by suitable means to the first section
T.sub.s with the window and outer edges of section L.sub.s in
aligned relation with the corresponding edges of the section
T.sub.s. The core windings 18 and 24 are wound through the windows
31, 33 and around the center leg 35 which is located therebetween
(FIG. 4--only winding 24 being shown for purposes of clarity). The
unitary core structure 29 as connected in a ferroresonant regulator
circuit, such as shown in FIG. 1, will operate in the manner of the
unitary core structure shown in FIG. 2. Moreover, adjustment of the
permeability of the structure 29 may be effected by grinding an air
gap laterally between the two windows 31, 33 of the L.sub.s core to
thereby permit corresponding adjustment of the effective
permeability of core L.sub.s and thereby the width of the pulse
output therefrom to correspondingly different values in an
economical manner.
In a further embodiment the section L.sub.s may comprise E and I
laminations of nickel-iron alloy stacked in a butt jointed
configuration with suitable insulation placed between the adjacent
portions of the E and I laminations to provide the desired
effective permeability.
Whereas the embodiments of FIGS. 1 and 2 illustrate arrangements in
which the T.sub.s L.sub.s cores are mounted in contacting location,
in certain applications it may be desirable to separate the T.sub.s
and L.sub.s cores and their associated windings. With reference to
FIG. 5, there is shown thereat a circuit arrangement in which a
T.sub.s core (which may be similar to the T.sub.s core of FIG. 2),
is wound with an input winding 34 and an output winding 36. The
second core L.sub.s, which may be a toroid core similar to the
L.sub.s core of FIG. 2 (or a pot core), is wound with a separate
input winding 38 and an output winding 40. The input windings 34,
38 of the T.sub.s and L.sub.s cores are connected in series with
one another (with the polarity indicated by the dots adjacent
thereto) and further are serially connected with the ballast
inductor 16 to the output circuit of inverter 12. Resonant
capacitor 22 is serially connected across windings 34, 38.
In like manner, the output winding 36 of the core T.sub.s and the
output winding 40 of core L.sub.s are connected in series with the
indicated polarities and over bridge rectifiers 26, 26A, 28, 28A,
to the load circuit 32. The filter capacitor 30 is connected across
the load circuit 32.
FIG. 6 illustrates an arrangement wherein separate core windings
16A and 24A on the input ballast inductor and T.sub.s L.sub.s core
20 are serially connected to provide an isolated AC voltage
proportional to and with the wave shape shown in FIG. 10a. The load
winding 24 is wound on saturable reactor core 20 as shown in FIG. 1
and is connected to the load 32 in like manner. The circuit of FIG.
5 can be similarly modified.
With reference to FIG. 7, there is shown thereat a further circuit
arrangement in which a separate winding 42 is wound on the T.sub.s
L.sub.s unitary core structure 20 of the type shown in FIG. 1 and
capacitor 22 is connected across the separate winding 42 for the
purpose of isolating the capacitor 22 from the series circuit which
includes the input winding 18 of the hybrid core T.sub.s
L.sub.s.
It will be apparent from the foregoing examples that most circuit
modifications and connections which are possible with known low
frequency power ferroresonant transformer circuits may also be used
with the novel high frequency ferroresonant transformer circuits
disclosed herein.
FIG. 8 illustrates in block diagram a further regulating
arrangement in which the high frequency ferroresonant transformer
may be used. Specific selection of the various regulating circuits
possible will, of course, depend on the application and
input-output requirements. In the arrangement shown in FIG. 8, a DC
source 10 is connected in the manner of FIG. 1 to the input of a DC
to AC inverter 12 which in turn provides a pulse output at a high
frequency rate (in the order of 10-20 KHz) to the high frequency
ferroresonant transformer 14. The output of the transformer 14 is
fed over the output rectifier filter 25 to a load (not shown). In
addition, a feedback sensing circuit 48 is connected to the output
of rectifier filter circuit 25 and a sensed voltage is fed by a
circuit 48 to a comparator circuit 50 which compares such voltage
output with a reference voltage input over path 52. A control
signal representing the difference in values of the compared
signals is fed back to adjust the output frequency of the inverter
12 in a direction to eliminate the difference in voltage output by
means of the high frequency resonant transformer 14. Thus any
variation of the voltage from the predetermined regulating value
will result in an adjustment of the frequency input to high
frequency ferroresonant transformer 14 to thereby adjust the
voltage output of the transformer 14 in the direction of the
desired voltage.
It is also apparent that the output of the circuit of FIG. 1 may be
connected over a conventional series regulator for use in providing
a highly regulated DC output in known manner.
The novel circuit can also be used for AC regulation by omitting
the rectifier stage.
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