U.S. patent number 3,594,663 [Application Number 05/019,668] was granted by the patent office on 1971-07-20 for dual-polarized dual-frequency coupler.
This patent grant is currently assigned to Maremont Corporation. Invention is credited to Daniel C. Allen.
United States Patent |
3,594,663 |
Allen |
July 20, 1971 |
DUAL-POLARIZED DUAL-FREQUENCY COUPLER
Abstract
A waveguide transition coupler having a coaxial waveguide and a
first circular waveguide formed inside the center conductor of the
coaxial waveguide for coupling with a second circular waveguide.
Two frequencies of two orthogonally polarized waves in the TE 11
mode are propagated together through the second circular waveguide
while each frequency is propagated separately by the first circular
and coaxial waveguides. Isolation of the two frequencies is secured
in the coaxial and first circular waveguide by dimensioning the
first circular waveguide so that it is beyond cutoff for the lower
frequency, and by placing a distributed choke-transformer in the
coaxial waveguide to attenuate the higher frequency electromagnetic
waves. Unwanted mode conversion is inhibited in the energy transfer
by a tapered pin inserted through both circular waveguides and
impedance-matching elements are provided.
Inventors: |
Allen; Daniel C.
(Kennebunkport, ME) |
Assignee: |
Maremont Corporation (Saco,
ME)
|
Family
ID: |
21794418 |
Appl.
No.: |
05/019,668 |
Filed: |
March 16, 1970 |
Current U.S.
Class: |
333/1; 333/26;
333/135; 333/206; 333/21R; 333/33; 333/251 |
Current CPC
Class: |
H01P
1/16 (20130101); H01P 5/12 (20130101) |
Current International
Class: |
H01P
5/12 (20060101); H01P 1/16 (20060101); H01p
005/12 (); H03h 007/04 (); H01p 001/16 () |
Field of
Search: |
;333/1,6,8,21,26,98,97,73 |
References Cited
[Referenced By]
U.S. Patent Documents
|
|
|
3265993 |
August 1966 |
Davidson et al. |
|
Primary Examiner: Saalbach; Herman Karl
Assistant Examiner: Nussbaum; Marvin
Claims
What I claim is:
1. A four-channel TE 11 mode microwave system having a coupling
between one waveguide where the four channels are propagated as two
frequencies of orthogonally polarized waves and two other
waveguides where the four channels are propagated as two
orthogonally polarized waves of a different single frequency in
each waveguide comprising:
a. a coaxial waveguide carrying electromagnetic waves of a first
frequency;
b. a first circular waveguide carrying electromagnetic waves of a
second frequency, said first circular waveguide being contained
within the inner conductor of said coaxial waveguide and coaxial
therewith with a termination to said inner conductor and said first
circular waveguide;
c. a second circular waveguide capable of carrying TE 11 mode waves
from said first circular and said coaxial waveguides and enclosing
the region beyond the termination of said first circular waveguide
and the inner conductor of said coaxial waveguide, the outer
conductor of said second circular waveguide formed by an extension
of the outer conductor of said coaxial waveguide;
d. means for attenuating waves at said first frequency in said
first circular waveguide; and
e. means for attenuating waves at said second frequency in said
coaxial waveguide.
2. A waveguide coupler for coupling electromagnetic energy of
arbitrary polarization at two frequencies in the TE 11 mode between
a common waveguide carrying both frequencies and two waveguides
carrying each frequency separately comprising:
a. a coaxial single frequency waveguide carrying electromagnetic
waves of a first frequency;
b. first circular single frequency waveguide carrying
electromagnetic waves of a second frequency said first circular
waveguide being contained within the inner conductor of said
coaxial waveguide with a termination to said inner conductor which
terminates said first circular and coaxial waveguides;
c. cutoff means within the single frequency waveguide carrying the
higher of said first and second frequencies, said cutoff means
supporting TE 11 mode propagations of said higher frequency in that
single frequency waveguide but being beyond cutoff for the TE 11
mode of the lower frequency;
d. a filter in the single frequency waveguide carrying the lower of
said first and second frequencies, said filter attenuating the
transmission in that single frequency waveguide of the
electromagnetic waves at said higher frequency; and
e. a second circular waveguide capable of carrying TE 11 mode waves
from said first circular and said coaxial waveguides and enclosing
the region beyond the termination of said first circular waveguide
and the inner conductor of said coaxial waveguide, the outer
conductor of said second circular waveguide formed by an extension
of the outer conductor of said coaxial waveguide.
3. An apparatus for coupling electromagnetic waveguided energy of
arbitrary polarization in the TE 11 mode for two waveguides
carrying different frequencies into one waveguide and from one
waveguide carrying both frequencies into said two waveguides
carrying different frequencies comprising:
a. a coaxial waveguide carrying electromagnetic wave of a desired
frequency;
b. a first circular waveguide carrying electromagnetic wave of a
desired frequency which is higher than those in said coaxial
waveguide, said first circular waveguide being contained within the
inner conductor of said coaxial waveguide, with a termination to
said inner conductor which terminates said first circular and
coaxial waveguides;
c. cutoff means within said first circular waveguide extending for
a distance up to said termination, said cutoff means supporting TE
11 mode transmissions of said higher frequency energy but being
beyond cutoff for the TE 11 mode of the lower frequency energy;
d. a filter in said coaxial waveguide placed around said inner
conductor, said filter attenuating in said coaxial waveguide the
electromagnetic waves carried by said first circular waveguide;
and
e. a second circular waveguide capable of carrying TE 11 mode waves
from said first circular and said coaxial waveguides and enclosing
the region beyond the termination of said first circular waveguide
and the inner conductor of said coaxial waveguide, the outer
conductor of said second circular waveguide formed by an extension
of the outer conductor of said coaxial waveguide.
4. The apparatus of claim 3 further comprising launching means for
lowering mode conversion in the transfer of energy in said second
circular waveguide with said first circular and coaxial
waveguides.
5. The apparatus of claim 4 wherein:
a. said cutoff means includes a pin axially supported within said
first circular waveguide, the ratio of the radii of said pin and
said first circular waveguide's outer conductor defining a cutoff
frequency above the frequency carried by said coaxial
waveguide;
b. said launching means includes an extension of said pin beyond
the termination of said inner conductor, said extension having a
radius which in cooperation with the radius of said second circular
waveguide's outer conductor defines a TM 11 mode cutoff frequency
above both frequencies carried by said apparatus, said extension
ending in a taper which at a point has a radius which permits TM 11
modes of at least one frequency carried by said apparatus but which
taper substantially inhibits their generation; and
c. the polarization of said waveguided energy at each frequency is
dual orthogonal polarization.
6. The apparatus of claim 3 wherein said filter further comprises a
filter transformer having a stack of alternating metallic and
dielectric annuli which are thin with respect to either wavelength
carried and which said inner conductor passing through them.
7. The apparatus of claim 6 wherein said filter transformer
commences approximately one-half wavelength of the higher frequency
back from the terminations of said inner conductor, and extends
back approximately one wavelength of the higher frequency for every
35 db. attenuation of the high frequency desired, and has a
metallic sleeve disposed between said inner conductor and said
stack, said stack appearing as a series of short circuited radial
transmission lines with an impedance of infinity to the higher
frequency at their outside diameter.
8. The apparatus of claim 6 further comprising:
a. a reactive groove cut into the outer conductor of said coaxial
and second circular waveguides, said groove cut in approximately an
odd multiple of a quarter wavelength of the higher frequency, and
said groove providing impedance-matching reactance at the lower
frequency;
b. impedance-matching means disposed on the end of said pin within
said first circular waveguide to match the impedance of said first
circular waveguide to the impedance of its termination containing
said pin; and
c. a conducting ring disposed between said pin and the inner
conducting surface of said inner conductor at its termination said
ring contacting said inner conductor but not contacting said
pin.
9. The apparatus of claim 8 further comprising: 1
a. a first set of at least one impedance-matching ring for said
coaxial waveguide; and
b. a second set of at least one impedance-matching ring for said
first circular waveguide, said first and second sets of impedance
matching rings arranged within their respective waveguides to
reduce reflections in waves carried by said coaxial and first
circular waveguides.
10. A waveguide coupler for coupling two frequencies of
electromagnetic waveguided energy of dual orthogonal polarization
in the TE 11 mode from two separate frequency waveguides into one
combined frequency waveguide and from one combined frequency
waveguide into two separate frequency waveguides comprising:
a. a coaxial waveguide carrying electromagnetic waves of a first
frequency; and
b. a first circular waveguide carrying electromagnetic waves of a
second and higher frequency, said first circular waveguide being
contained within the inner conductor of said coaxial waveguide,
with a termination to said inner conductor, said first circular
waveguide and said coaxial waveguide;
c. a pin axially supported within said first circular waveguide and
having an extension to said pin extending beyond the termination of
said inner conductor the portion of said pin and its support within
said first circular waveguide forming a coaxial termination thereto
with a cutoff frequency between the higher and lower frequencies,
the end of said pin within said first circular waveguide having
means matching the impedance of said coaxial termination of said
first circular waveguide to the remainder of said first circular
waveguide;
d. a filter transformer comprising a stack of alternating metal and
dielectric annuli in said coaxial waveguide surrounding said inner
conductor a distance from its termination said annuli being thin
with respect to a wavelength at either frequency and providing an
attenuation varying with stack length to the higher frequency waves
in said coaxial waveguide, but appearing as lumped reactances to
the lower frequency waves in said coaxial waveguide;
e. a second circular waveguide capable of carrying the TE 11 mode
waves from said first circular and coaxial waveguides and enclosing
the region beyond the termination of said first circular waveguide
and said inner conductor, the outer conductor of said second
circular waveguide formed by an extension of the outer conductor of
said coaxial waveguide, the extension of said pin beyond the
termination of said inner conductor extending into said second
circular waveguide and ending in a taper, the region of said second
circular waveguide surrounding the extension of said pin being
cutoff for the TM 11 mode of both frequencies carried, but the
region surrounding the tapered ending being able at some point in
the taper to support TM 11 modes of at least one frequency carried
but having the taper substantially inhibiting their generation;
and
f. a reactive groove cut into the outer conductors of said coaxial
and second circular waveguides, said groove cut in approximately an
odd multiple of a quarter wavelength of the higher frequency wave,
said groove providing impedance-matching reactance at the lower
frequency.
Description
BACKGROUND OF THE INVENTION
TE 11 mode dual-frequency dual-polarization waveguide couplers that
I am familiar with from the prior art have cost and performance
disadvantages which this coupler overcomes. The known prior art
couplers are fabricated as square or rectangular multiple slot
couplers with each band and polarization tandemly mounted. This
makes the entire assembly in excess of 15 feet in length as
compared to about 2 feet of length for the coupler of this
invention operating over the same frequencies. With prior art
square designs the squareness and straightness of the waveguide is
harder to maintain than the circularities and concentricities of
the present invention's circular design. A further defect of the
prior art multiple slot tandem couplers is their tendency to
resonate at certain frequencies. These resonances cause phase-delay
distortion which is bothersome in modern FM systems. In the present
design the improved waveguide isolation and lack of multiple slots
reduces the possibilities of resonant frequencies.
It is thus an object of this invention to provide a TE 11 mode
waveguide coupler having a high degree of isolation between the
waveguides carrying separate frequencies.
It is a further object of this invention to reduce the number of
input or output waveguides for each polarization and frequency
being carried in a coupler and thus to reduce resonance and
phase-delay distortion in the microwave coupler for TE 11
modes.
SUMMARY OF THE INVENTION
In the preferred embodiment of this invention a first circular
waveguide is formed within the inner conductor of a coaxial
waveguide. Beyond a termination of the inner conductor a second
circular waveguide extends within an extension of the outer
conductor of the coaxial waveguide. The coaxial and first circular
waveguides each propagate a different frequency of TE 11 mode
microwave energy with two orthogonally polarized waves propagated
at each frequency. Both frequencies are propagated together in the
second circular waveguide.
In the preferred embodiment coupling of the energy in the second
circular waveguide with the energy in the coaxial and first
circular waveguides is facilitated by a conductive pin axially
supported within the end region of the first circular waveguide and
extending into the second circular waveguide. The presence of the
pin extension beyond the first circular waveguide lessens the
abruptness of the impedance change for the waves carried by the
coaxial waveguide and converts the TE 11 circular mode waves in the
first circular waveguide to the TE 11 coaxial mode. The portion of
the pin extending into the second circular waveguide is dimensioned
to suppress propagation of the TM 11 modes of both frequencies. The
pin ends in a taper in the second circular waveguide which insures
that as the TE 11 coaxial mode waves at both frequencies change to
the TE 11 circular mode the generation of TM 11 modes will be
minimized.
Maximum isolation is achieved between the coaxial and first
circular waveguides with a distributed choke-transformer in the
waveguide carrying the lower frequency to attenuate higher
frequency energy from the other of these two waveguides, and by
dimensioning the termination of the other of these two waveguides
so that it is beyond the cutoff for and thus attenuates the lower
frequency. In the preferred embodiment the higher frequency waves
are carried by the first circular waveguide while the lower
frequency waves are carried in the coaxial waveguide.
Further features of the preferred embodiment include a reactive
groove formed in the outer conductors of the coaxial and second
circular waveguides where they join. This reactive groove which is
effectively a short-circuited radial transmission line improves the
impedance matching for the lower frequency waves between the
coaxial waveguide and second circular waveguide. A conductive ring
in the first circular waveguide contacting its outer conducting
surface at its termination increases the cutoff isolation of the
first circular waveguide to the lower frequency waves. Finally,
various impedance matching rings are placed in the first circular
and coaxial waveguides by empirical design techniques to eliminate
wave reflections in the coupler.
The present invention will be more fully understood by considering
the following detailed description of the preferred embodiment
accompanied by the drawing which is a longitudinal sectional view
of the coupler at any plane passing through and including its axis,
the structure being radially symmetrical.
DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT
In the preferred embodiment of the present invention a first
circular waveguide 2 is formed coaxially within an inner conductor
4 of a coaxial waveguide 1. The coaxial waveguide 1 is formed
between an inner conductive wall of an outer conductor 3 and an
outer conductive wall of the inner conductor 4. A low loss
dielectric spacer 5 centers the inner conductor 4 within the outer
conductor 3. The first circular waveguide 2 is coaxial with the
coaxial waveguide 1 and is bounded by an inner wall of the inner
conductor 4.
The inner conductor 4 terminates at a point of transition 23 for
the coaxial and first circular waveguides 1 and 2. Beyond this
point of transition 23 of the coaxial and first circular waveguides
a second circular waveguide 18 extends coaxially, defined by the
inner conductive wall of an outer conductor 16 which is formed by
an extension of the outer conductor 3 of the coaxial waveguide.
Four channels of TE 11 mode microwave energy are carried by the
preferred embodiment of this invention. Two channels are carried by
the coaxial waveguide 1 as two orthogonally polarized waves in a
first frequency band. Two other channels are carried by the first
circular waveguide 2 as two orthogonally polarized waves in a
second frequency band which in the preferred embodiment is roughly
twice the first frequency. In the second circular waveguide 18 both
polarizations and both frequencies providing the four channels are
carried together in superimposed relationship.
A conductive pin 17 extends within the first and second circular
waveguides and has at opposite ends of a cylindrical center portion
a stepped-down cylindrical projection 19 and a tapered section 8.
Pin 17 is coaxially centered within the first circular waveguide by
a low loss dielectric 6 filling the space between the pin 17 and
the interior wall of inner conductor 4 giving a coaxial transition
to the first circular waveguide 2. The radius of the pin 17, the
inside radius of the inner conductor 4 and the dielectric constant
of the dielectric 6 cooperate to make the cutoff frequency of the
first circular waveguide in the region surrounding the pin 17 above
the frequency of the wave carried in the coaxial waveguide 1. The
length of the cylindrical center portion of pin 17 within the first
circular waveguide 2 and its surrounding dielectric 6 is not
critical so long as the length is great enough to substantially
inhibit transmission of all waves at the frequency carried by the
coaxial waveguide 1.
The isolation of the first circular waveguide 2 from the
frequencies carried by the coaxial waveguide 1 is further increased
by the presence of a conductive ring 21 contacting the inner wall
of the inner conductor 4 at its termination 23. The effective
spacing 22 between the pin 17 and the inner conductor 4 is
decreased by the ring 21 to further increase the cutoff effect and
consequently further inhibit the transmission into the first
circular waveguide 2 of frequencies carried by the coaxial
waveguide 1. The axial length of the ring 21 is not critical and in
the preferred embodiment it is substantially less than a wavelength
at either frequency.
An impedance-matching conductive ring 26 is disposed around the pin
17 and spaced back into the first circular waveguide 2 from the
termination 23 approximately a quarter wavelength of the higher
frequency wave carried by the first circular waveguide 2. This
impedance matching ring 26 compensates for the effects of the ring
21 on the higher frequency wave carried by the first circular
waveguide and its dimension and location for this purpose are
empirically determined.
The projection 19 is coaxially disposed on the end of pin 17 facing
into the first circular waveguide 2 away from its termination at
23. The projection 19 matches the impedance of the first circular
waveguide 2 to its coaxial termination containing the pin 17 and
dielectric 6.
A portion 7 formed as a continuation of the pin 17 extends beyond
the termination at point 23 of the first circular waveguide 2 into
a region 24 of the second circular waveguide 18. The portion 7
joins the taper 8 which converges in a region 25 of the second
circular waveguide 18 to zero radius. In the first region 24, the
radius of the pin extension 7, the inner radius of the outer
conductor 16 of the second circular waveguide 18, and the gas
dielectric cooperate to give a cutoff frequency above TM 11 modes
for either frequency. The length of the pin extension, portion 7,
and the first region 24 is preferably approximately one wavelength
of the higher frequency wave. The taper 8 may converge linearly,
but is preferably slightly concave to produce a narrower taper
beyond the point in the region 25 where the radius of the taper 8
has diminished enough to allow the TM 11 modes to exist. The
narrower the taper 8 the less will be the mode conversion to TM 11
modes in the second region 25. It has been found that for a taper
approximately three to six wavelengths of the upper frequency in
length mode conversion is substantially inhibited.
Surrounding the inner conductor 4 a distance back from its
termination is a filter indicated at 9 which surrounds and contacts
the inner conductor 4 but does not contact the outer conductor 3.
The filter 9 is composed of a stack of alternate metallic and
dielectric annuli around the inner conductor 4 and a metallic
sleeve 20 fitting between the stack and inner conductor 4.
Proceeding back from the termination 23 of the inner conductor 4, a
first metallic annulus 12 is somewhat thicker than the other annuli
and is directly in contact with the inner conductor 4. Behind the
first annulus 12 is a thinner dielectric annulus 13 directly
contacting the inner conductor 4.
Beyond this point the metallic sleeve 20 surrounds and contacts the
inner conductor 4 for the entire length of the rest of the stack.
Beginning from dielectric annulus 13 two metallic annuli 14 and 14'
surround the sleeve 20. The metallic annuli 14 and 14' increase the
outside diameter of the stack in two steps. The outside diameter of
the metallic annulus 14' is maintained by all subsequent annuli 10
and 11 in the rest of the stack of filter 9. Beyond metallic
annulus 14' dielectric annuli 10 and metallic annuli 11 alternate
making up the remainder of the stack. The annuli 12, 13, 14, and
14' differ from the annuli 10 and 11 only for impedance-matching
considerations.
The end of the stack butts against the dielectric spacer 5
centrally supporting the inner conductor 4 in the coaxial waveguide
1. In the preferred embodiment the first metallic annulus 12 is
placed approximately one-half wavelength of the higher frequency
back from the termination 23 of the inner conductor 4.
The dimensions and number of the annuli in the stack of filter 9
may be adjusted. These dimensions are arrived at by accounting for
impedance-matching considerations for the lower frequency and
attenuation considerations for the upper frequency. The greater the
length of the filter 9, the greater will be the isolation for the
higher frequency. It is thus desirable to use a matching technique
for the lower frequency which will allow a maximum length to the
filter 9. It has been found that approximately 35 db. of
attenuation in the upper frequency is achieved fore every
wavelength of the upper frequency that the stack extends. For the
intended uses of this preferred embodiment an attenuation of 30 or
35 db. has been found sufficient. The length of the stack of filter
9 is accordingly adjusted.
The characteristic impedance of the filter 9 can be adjusted in
several ways and still maintain its attenuation for the higher
frequency. With the proper selection of dielectric material as well
dimensional sizes, i.e., diameters and thicknesses, the
characteristic impedance can be made to match the impedance of the
region to the left of dielectric 5 to the impedance of the region
to the right of annulus 12. This is not necessarily desirable,
however, since the impedance mismatch at the lower frequency
between the coaxial waveguide 1 at its termination at 23 and the
first region 24 of the second circular waveguide 18 is quite large
and require correspondingly large reactive impedances elsewhere to
counteract it. In the design established the filter impedance at
the lower frequency is lower than both the characteristic impedance
of the region of the coaxial waveguide 1 to the left of the
dielectric support 5 and the characteristic impedance of the region
to the right of the first metallic annulus 12 up to the termination
of the inner conductor 4. It appears as a lumped reactance to the
lower frequency.
In general the thickness of the annuli in the stack of filter 9
will be much smaller than a wavelength. The stack of alternating
metallic and dielectric annuli appear as a series of radial short
circuited transmission lines. The outer diameters of the metallic
and dielectric annuli are chosen so that each radial section has an
input impedance of infinity at the center of the upper frequency.
The higher the dielectric constant of the dielectric annuli 10 the
smaller can be the outside diameter of both metallic and dielectric
annuli 10 and 11.
At the point where the outer conductors 3 and 16 of the coaxial
waveguide 1 and second circular waveguide 18 join, and in the same
transverse plane as is the termination point 23, a reactive groove
15 is cut into these outer conductors 3 and 16. The reactive groove
is circular and approximately one-quarter wavelength deep at the
upper frequency band. It is effectively a short circuited radial
transmission line whose impedance transforms to infinity at the
upper frequency and has little effect on that upper frequency. At
the lower frequency, it is, however, an apparent series inductance
which in part compensates for a capacitive series reactance due to
the dielectric support 6 and in part compensates for impedance
mismatches between the coaxial waveguide 1 and the second circular
waveguide 18. The groove is thin with respect to a wavelength at
either frequency.
A set of metallic matching rings 27 and 28 may be placed around and
in contact with the inner conductor 4 of the coaxial waveguide 1.
The size and placement of these rings 27 and 28 are empirically
determined so that they function to minimize reflections of the low
frequency waves carried by the coaxial waveguide 1.
In operation this waveguide coupler is designed to couple four
channels of electromagnetic microwave energy between a common
circular waveguide and two orthogonally polarized ports of one
frequency and two orthogonally polarized ports of a second
frequency band. This coupling is accomplished with a maximum degree
of isolation between all the ports, produced by orthogonality,
cutoff phenomena and filtration. This coupling is also reciprocal
allowing energy to be coupled between the common circular waveguide
and the ports in either direction. For simplicity the following
description of the operation of the coupler will be in terms of
coupling from the ports into the common circular waveguide. It
should at this point be emphasized that the coupler operates
equally well in reverse to couple energy from the common circular
waveguide to the port of the proper frequency and polarization.
Furthermore the microwave energy in each polarization in each
frequency is independent of the energy in the other three waves so
that coupling can occur in both directions simultaneously between
the common waveguide and different ports.
When operating to propagate two frequencies into a common circular
waveguide the lower frequency band of two orthogonal waves is
introduced into the coaxial waveguide 1, while the higher frequency
band of two orthogonal waves is introduced into first circular
waveguide 2. The mode in both input waveguides is the TE 11 mode
coaxially and circularly oriented in the coaxial and first circular
waveguides respectively. These modes are introduced from the ports
by standard waveguide couplers.
The energy in the first circular waveguide is transferred into the
coaxial termination of the first circular waveguide formed by the
pin 17 and its dielectric support 6. In this transfer the mode
changes from TE 11 circular to TE 11 coaxial. The energy in this
coaxial termination is coupled into the first region 24 of the
second circular waveguide 18 along the pin extension 7.
Likewise the electromagnetic wave energy in the coaxial waveguide 1
passes through the dielectric support 5 which centers the inner
conductor 4 within the outer conductor 3 of the coaxial waveguide
1. This lower frequency wave passes through the filter 9 which acts
as a filter transformer or distributed choke-transformer to the
higher frequency wave but as a lumped reactance to the lower
frequency. The lower frequency wave finally makes the step
transition from the inner conductor 4 to the pin extension 7 in the
first region 24. There, it joins the higher frequency energy wave
from the first circular waveguide and together they are launched
into the second circular waveguide along the pin 17. They make the
transition from the TE 11 coaxial mode in the first region 24 along
the taper 8 in the second region 25 to the circular portion of the
second circular waveguide 18 to become TE 11 circular mode waves.
The first region 24 beyond cutoff for the TM 11 modes for both
frequencies, and the taper 8 on the pin extension 7 inhibits the
generation of TM 11 modes as the waves at both frequencies from the
coaxial first region 24 are transformed into the circular TE 11
modes in the circular region of the second circular waveguide
18.
The lower frequency microwave energy in the first region 24 is kept
out of the first circular waveguide 2 by having its coaxial
termination with the pin 17, ring 21 and dielectric support 6
beyond cutoff for all lower frequency modes. The higher frequency
wave in the first region 24 is inhibited from entering the coaxial
waveguide 1 by the filter 9 placed around the inner conductor 4
approximately a quarter wavelength of the lower frequency or
one-half a wavelength of the higher frequency back from the
termination 23 of the inner conductor 4 in the coaxial waveguide
1.
To compensate for the effect of the filter 9 upon the lower
frequency wave transmitted by the coaxial waveguide 1,
impedance-matching devices are used in the coaxial waveguide 1.
These include rings 27 and 28 placed around the inner conductor 4,
the reactive groove 15 and the shape and position of the dielectric
annuli 10, 11, 12, 13 and 14 as well as the thickness of the sleeve
20 between the stack of annuli and the inner conductor 4.
It is apparent that the coupler of this invention can be designed
with the higher frequency carried by the coaxial waveguide 1 and
the lower frequency carried by the first circular waveguide 2 in
which case the filter 9 is placed around the pin 17 while the
coaxial waveguide 1 is maintained beyond cutoff for the lower
frequency wave in the first circular waveguide 2.
Because all elements of the coupler are circular, the polarization
of the electromagnetic microwave energy may be of an arbitrary
linear or circular polarization though the specific use for the
coupler is with dual orthogonally polarized waves.
It is also intended to cover all other modifications and
alternatives to the above-described preferred embodiment which do
not depart from the scope and spirit of this invention.
* * * * *